Implementing an LCD TV Power Supply with NCP1396A, NCP1605 & NCP1027

AND8293/D
Implementing an LCD TV
Power Supply with the
NCP1396A, NCP1605, and
NCP1027
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Prepared by Roman Stuler
Introduction
Timer Based Fault Protection
This document provides a detailed description of the
implementation of an LCD TV power supply. The LDC TV
supply unit exhibits high efficiency, low EMI noise and a low
profile construction. The board contains DCM/CCM PFC
front stage, 210 W LLC power stage and 12.5 W standby
flyback converter.
The design requirements for our LCD TV power unit are
as follows:
The converter stops operation after a programmed delay
when the protection is activated. This protection can be
implemented as a cumulative or integrating characteristic.
Thus, under transient load conditions the converter output
will not be turned off, unless the extreme load condition
exceeds the timeout.
Min
Max
Unit
Input Voltage
Requirement
90
265
Vac
Output Voltage 1
-
12
Vdc
Output Current 1
0
3
A
Output Voltage 2
-
24
Vdc
Output Current 2
0
6
A
Output Voltage 3
-
30
Vdc
Output Current 3
0
1
A
Output Voltage Standby Output
-
5
Vdc
Output Current Standby Output
0
2.5
A
Total Output Power
0
222.5
W
Total No Load Consumption for
0.5W Load on the Standby Output
-
1
W
NOTE:
Common Collector Optocoupler Connection
The open collector output allows multiple inputs on the
feedback pin i.e. over current sensing circuit, over
temperature sensor, etc. The additional input can pull up the
feedback voltage level and take over the voltage feedback
loop.
600 V High Voltage Floating Driver
The high side driver features a traditional bootstrap
circuitry, requiring an external high-voltage diode for the
capacitor refueling path. The device incorporates an upper
UVLO circuitry that guarantees enough Vgs is available for
the upper side MOSFET.
Adjustable Dead-Time (DT)
Due to a single resistor wired between DT pin and ground,
the user has the option to include needed dead- time, helping
to fight cross- conduction between the upper and the lower
transistor.
Only 24 V output is regulated in this version of the board.
Additional output(s) regulation can be assured by adding
feedback resistors to desired output (or outputs for
percentage weight).
Adjustable Minimum and Maximum Frequency
Excursion
Using a single external resistor, the designer can program
its lowest frequency point, obtained in lack of feedback
voltage (during the startup sequence or in short- circuit
conditions). Internally trimmed capacitors offer a $3%
precision on the selection of the minimum switching
frequency. The adjustable maximum frequency is less precise
($15%). Please refer to the NCP1396A/B data sheet for
detailed description of all mentioned and additional features.
The NCP1396A resonant mode controller has been
selected for this application because the soft- start absence on
the fast fault input offers an easy implementation of the skip
cycle mode. This helps to assure regulation of the resonant
converter under no load conditions. The NCP1396A offers
many other features that are advantageous for our application.
Brown-Out (BO) Protection Input
The input voltage of the resonant converter, when divided
down, is permanently monitored by the Brownout pin. If the
voltage on the bulk capacitor falls outside of the desired
operating range, the controller drive output will be shut off.
This feature is necessary for an LLC topology that uses PFC
stage without PFC OK control output. In our case the BO
input is used as an enabling input and is fully controlled by the
front stage controller output (PFC OK).
© Semiconductor Components Industries, LLC, 2007
June, 2007 - Rev. 1
Detailed Demo Board Connection Description
A schematic of the proposed LCD TV power supply is
shown in Figure 1. As already mentioned, the supply contains
three blocks: a PFC front stage, an LLC converter and an
auxiliary flyback converter that powers a TV set during
standby and provides bias power for PFC and LLC control
circuits during normal operation.
1
Publication Order Number:
AND8293/D
AND8293/D
Figure 1. Schematic of the NCP1396A LCD TV Application
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AND8293/D
PFC Front Stage
voltage range is restricted by the Brown Out sensing
network R64, R68, R70, R77 and C48. The NCP1027 switcher
features adjustable ramp compensation capability - resistor
R78. Feedback loop is accomplished in the standard way: the
output voltage level is regulated by the IC6 to the value
which is defined by resistors R74 and R80. Bias current for
optcoupler OK3 and regulator is provided from the standby
supply output using resistors R72 and R73. Resistors R75 and
R79 are used to stabilize the maximum output power level
with bulk voltage evaluation (CS comparator delay
compensation). A standard RCD voltage clamp (R66, R67,
C41, D21) is installed on the switcher drain to limit its voltage
to safe level. There is an optional layout on the board so the
TVS (D19) can be used instead of the RCD clamp. This
solution further decreases standby power consumption,
however, price is slightly higher. Voltage from auxiliary
winding, which is used to power the switcher is also used to
feed up the PFC front stage and the main LLC converter
control circuits. This voltage is limited by a simple zener
regulator (D22, Q7, R76 and C46) and can be inhibited by the
OK2 action. Standby mode can be activated either by
positive or negative logic signals (Q5 or Q6 assembled).
Please refer to the application note AND8241/D for a
detailed explanation on how to design a Standby flyback
converter using the NCP1027 switcher.
The NCP1605 (IC1) PFC controller is used for PFC front
stage control. This front stage works either in fixed
frequency discontinues mode or critical conduction mode
depends on the line and load conditions. Capacitors C42,
C30, CY1, CY2 with common mode choke L9, inductors L6,
L7 and varistor R28 form the EMI filter, which suppresses
noise conducted to the mains. A bridge rectifier B1 is used
to rectify the input AC line voltage. Capacitor C5 filters the
high frequency ripple current, which is generated by the PFC
operation. In this application a classical PFC boost topology
is used. The PFC power stage is formed by inductor L2,
MOSFET switch Q2, diode D4, bulk capacitors C6, C7 and
inrush current bypassing diode D2. The current in the PFC
stage is monitored by current sense network R13, R14 and
R15. Right input voltage operating range is adjusted by the
Brown Out sensing network R2, R5, R10, R16, R36 and C21.
Output voltage of the PFC stage is regulated to a nominal
395 Vdc via the feedback network R3, R6, R11, R22, R29 and
R30. Sensing network described above is also used to
monitor an overvoltage condition on the PFC output using
the NCP1605 OVP pin. PFC regulation loop bandwidth is
limited by the capacitor C22. The sensitivity of the zero
current detection circuitry is given by the resistor R39 value.
Capacitor C19 and resistor R40 are used to control the
maximum Q2 switch on-time. Capacitor C24 dictates the
DCM operating frequency. Skip mode of the PFC front stage
is initiated by the NCP1605 controller when the voltage on
the STBY pin is lower than 0.3 V. Since the LLC stage
voltage feedback and also bulk capacitor voltage have
opposing reaction function (increasing when output load
decreases), the divided (R35, R43 and C25) LLC stage
primary current information has been used to trigger the
PFC skip mode during light load conditions.
The controller receives the VCC voltage from standby
stage when standard operation mode is enabled by the TV set
application.
Please refer to the application note AND8281/D for a
detailed explanation on how to design a PFC front stage
using the NCP1605 controller.
LLC Power Stage
As previously mentioned, the NCP1396A (IC3) resonant
mode controller is used to control the main SMPS unit. The
power stage of the LLC converter is formed by bulk
capacitors C6, C7, MOSFETs Q1, Q3, transformer TR1 and
resonant capacitor C11. MOSFETs are driven directly by the
controller. Resistors R19 and R20 damp the gate charging
circuit to suppress overshoots on the gates and regulate EMI
noise. Bootstrap diode D14 is charging the bootstrap
capacitor C28 via resistor R42. The bootstrap capacitor
powers a floating driver when high side MOSFET is turned
on. Safety resistors R4 and R12 are used to protect MOSFETs
(during the experiments on the bench, for instance, when IC3
is removed).
Center-tapped windings on 12 V and 24 V outputs
increase the converter efficiency. A bridge rectifier is used
for 30 V output. Different shottky diode types (D3 with D5,
D6 through D10 and D11) are used for secondary rectification
according to output voltage, power losses and also short
circuit capability (not to damage diode during hard short on
the output). The low ESR, high temperature electrolytic
capacitors C1 through C4, C8 through C10, C12 through C16,
together with inductors L1, L4, and L5 serve as filters for
corresponding outputs. The secondary voltage regulator IC2
regulates the output voltage to 24 V, which is value adjusted
by resistor divider composed by R24, R48 and R49. If needed,
there can be optionally used feedback from other secondary
output(s) (R26 and R27 are included in the board layout). On
the primary side, the optocoupler works in the connection
with a common collector which also allows an easy
implementation of the current regulation loop. Maximum
Standby Supply
An ON Semiconductor NCP1027 monolithic switcher
(IC5) is used for auxiliary (or standby) power stage provide
a cost effective solution, needed output power and low
standby consumption, since this switcher offers skip mode
capability under light load conditions. The nominal output
power of this converter is 12.5 W. The unit is connected
directly to the bulk capacitors so during standby conditions
it operates from rectified mains. During normal operating
conditions the switcher is energized by higher voltage (PFC
front stage is working). After the start (that is assured by
internal current supply) the switcher is powered from the
auxiliary winding. Diode D23 is used for rectification and
capacitor C47 to filter auxiliary voltage. Resistor R71 limits
the ICC current so the auto-recovery OVP is not activated for
the correct VCC voltage. The appropriate operating bulk
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AND8293/D
converters, offers extra high leakage inductance value
thanks to a special windings arrangement (see demo board
photo in Figure 24). The leakage inductance serves as a
resonant inductance, which results in a cost effective
solution since no additional inductor is needed to form a
resonant tank. Specified parameters of the mentioned
transformer are as follows:
current through the optocoupler transistor is adjusted by a
resistor R33. To speed up the regulation response, resistor
R47 is connected to the feedback pin.
Capacitor C34 defines the soft start length. Note that the
current regulation loop is used in this power stage so it takes
control during the startup and affects the soft start action.
Resistors R53, R55 and R57 define maximum operating
frequency, minimum operating frequency and dead time.
The operation/fault time period during the overload is
dictated by C35 and R54 values.
The LLC power stage operation is conditioned to the
correct PFC front stage operation indicated by the PFC OK
signal. This signal, divided down by resistors R32 and R56,
enables the NCP1396A controller when the bulk voltage is
in the right range (PFC stage reached regulation).
Resistor divider R51 and R58 with bypass capacitor C37
are used to prepare skip mode during light or no load
conditions on the power stage output. This skip mode limits
the maximum needed operating frequency of the converter
and improves no load efficiency of the LLC stage.
As already mentioned, the current feedback loop is used
in this design. It limits the primary current of the power stage
during overload and helps to implement hick-up mode.
Primary current is sensed using charge pump R17, C18, D12,
D13. Output of this charge pump is divided and filtered by
R31, R18 and C17. Maximum value of this voltage (and thus
also the primary current) is regulated to 1.24 V by IC4
regulator. The compensation of current regulation loop is
accomplished by C31 capacitor. Zener diode D15 is used to
lower maximum voltage on IC4. Since we need to bring up
the NCP1396 feedback pin to increase the operating
frequency during overload, transistor Q4 with resistors R38
and R44 are used to perform inversion. Output voltage on the
Q4 collector is limited by zener diode D18 to 7.5 V
maximally. This voltage divided down by resistors R52 and
R59 triggers the slow fault input in case of an overload and
also drives the NCP1396A feedback pin via diode D17. This
diode assures that the slow fault input is not triggered during
light load conditions and in skip mode when the IC3
feedback pin voltage is pushed up by the voltage feedback
loop.
Controller IC3 receives the VCC voltage from standby
stage during normal operation mode. Auxiliary winding of
the resonant transformer W7 (when half wave rectified by
D1) helps to power the control circuits when load on the
standby supply output is too low and there is a lack of voltage
on the standby auxiliary winding due to pure flyback
transformer coupling. Please note that all outputs of the
converter (including standby stage) are referenced to one
secondary ground (S_GND).
Leakage (Resonant) Inductanc
Magnetizing Inductance
Primary Turns Count
24 V Output Turns Count
12 V Output Turns Count
30 V Output Turns Count
Auxiliary Winding Turns Count
Lm/Ls Ratio
Ls = 115 mH
Lm = 450 mH
38
4
2
5
3
450/115 = 3.9
Low value of the Lm/Ls ratio together with high turns
ratio of the transformer will result in the high gain values.
Note that the manufacturer specifies the LS inductance in
a standard way - all secondary windings are shorted during
the Ls measurements. This approach is OK for a transformer
that has one secondary winding, but in our case we have
three different secondary windings and two of them are
center taped so only one of the corresponding winding
participates on the resonance during one half of the
switching period. As a result, the real leakage inductance
that participates on the resonance is higher. Due to this fact,
the simulation results of gain characteristics that are
accomplished based on the transformer datasheet values, are
not accurate enough to determine operating frequency range
of the proposed converter.
The most accurate method how to obtain gain
characteristics of the LLC converter that uses integrated
transformer solution with multiple outputs, is to use a
gain-phase analyzer. To do so it is necessary to load
measured transformer outputs by equivalent AC resistances
before measurements (first fundamental approximation see [5] and [6]). For the center taped windings connect the
AC resistance only to one of the windings of the pair - this
will happen in reality - only one diode conducts the current
during one half of the switching period. The AC resistance
for corresponding output can be calculated using
Equation 1.
R ac +
8 V out ) V f
p2
(eq. 1)
I out
Where:
Vout
is the DC output voltage for given output
Vf
is the rectifier forward voltage
Iout
is the DC output current from given output
The output current has to be selected based on what type
of gain characteristics one wants to obtain - full load, 10%
load etc. Connection of the transformer during the gain
characteristics measurements can be seen in Figure 2.
LLC Transformer and Resonant Tank
A transformer from the standard production of the Pulse
engineering company has been used for this design. This
transformer, which is specially designed for LLC
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AND8293/D
• The minimum needed operating frequency to assure
low line regulation is 79 kHz
• The maximum needed operating frequency to assure
high line regulation is 106 kHz
• The converter will operate in the calculated series
resonant frequency for Vbulk = 360 VDC
As demonstrated, the converter will operate above the
calculated theoretical series resonant frequency for nominal
bulk voltage and full load. The ZCS capability is thus not
achieved on the secondary diodes. Also the needed
operating frequency range of this converter is very narrow,
which is beneficial for LCD TV application - EMI radiation
and filtering.
Gain characteristic of this converter for Iload = 0.10 * Imax
and same parameters as above is in Figure 4.
0.21
0.19
Figure 2. Transformer Connection During Gain
Characteristics Measurements
GAIN (-)
0.17
The resonant tank quality factor of Q = 4.3 (that
corresponds to resonant capacitor Cr = 33 nF) has been
selected for this design in order to narrow operating
frequency range of the converter.
The measured full load gain characteristic for the selected
resonant tank components and 24 V output can be observed
in Figure 3.
The gains that are needed to assure line regulation can be
calculated using Equations 2 through 4:
G nom +
G max +
V inmax
2ǒV out ) V fǓ
V innom
2ǒV out ) V fǓ
V inmax
+
+
2(24 ) 0.6)
425
2(24 ) 0.6)
395
+ 0.116
(eq. 2)
+ 0.125
(eq. 3)
+
Gmax
0.125
0.11
Gmin
0.07
0.05
2.0E+04
6.0E+04
1.0E+05
1.4E+05
1.8E+05
FREQUENCY (Hz)
Figure 3. FLLC Converter Gain Characteristic
for Full Load and Q = 4.3 (Cr = 33 nF)
2
1.8
1.6
+
2(24 ) 0.6)
350
1.4
+ 0.141
(eq. 4)
Theoretical series resonant frequency can also be
calculated based on the Equation 5:
f r1 +
0.13
Operating Point for
Vbulk = 395 V and
Full Load
0.09
GAIN (-)
G min +
2ǒV out ) V fǓ
0.15
1.2
1
0.8
1
0.6
2 @ p @ ǸL r @ C r
0.4
(eq. 5)
1
2 @ 3.14 @ Ǹ115 @ 10 - 6 @ 33 @ 10 - 9
0.2
+ 81.7kHz
0.125
0
2.E+04
Now, when looking back to the gain characteristic in
Figure 3, the operating conditions of the full loaded LLC
power stage can be read:
• The nominal operating frequency of such converter is
94.6 kHz (for nominal bulk voltage)
6.E+04
Operating Point for
Vbulk = 395 V and
Full Load
100kHz
1.E+05
1.E+05
2.E+05
FREQUENCY (Hz)
Figure 4. LLC Converter gain Characteristic
for 10 % Load Conditions
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AND8293/D
This characteristic shows that the operating frequency has
to be increased above 100 kHz to maintain regulation under
light load conditions. Skip mode for the LLC stage can thus
be easily implemented when maximum frequency is limited
by Fmax adjust resistor value.
Please refer to the application notes AND8255/D and
AND8257/D for further information about the LLC
converter resonant tank components design.
Standby (PFC and LLC disabled) consumption
characteristic with line voltage for 0.5 W load on the standby
output is in Figure 7. The consumption is below 1 W for any
input voltage so today's energy agency's needs are easily
met thanks to this design.
950
900
Results Summarization
PIN (mW)
Operating frequency of real LLC stage is 96.1 kHz for full
load and Vbulk = 395 VDC, which is very close to the
theoretical expectations. Output current level during which
the skip mode takes place (LLC stage) has been set
approximately to 8 W by R50, R57 divider. The PFC stage
enters skip mode for output power lower than 25 W and
leaves it for Pout > 30 W.
Measured efficiency for different input voltages and load
conditions can be seen in Figures 5 and 6.
850
800
750
700
85
0.92
EFFICIENCY (-)
EM 230
0.88
EM 110
0.86
0.84
0.82
0.8
40
60
80
100 120 140 160 180 200 220
TOTAL OUTPUT POWER (W)
Figure 5. Total Efficiency versus Output Power and
Line
0.915
FULL LOAD EFFICIENCY (-)
0.91
0.905
0.9
0.895
0.89
0.885
0.88
0.875
0.87
0.865
0.86
90
110
130
125
145
165 185 205
VIN (VAC)
225
245
265
Figure 7. Standby Consumption versus Line Voltage
- 0.5 W Load on STB Output
0.9
0.78
20
105
150 170 190 210
INPUT VOLTAGE (VAC)
230
250
Figure 6. Total Full Load Efficiency versus Input
Voltage
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AND8293/D
Figure 8. LLC Converter Waveforms During Skip
Mode (1 - Bridge Voltage, 2 - Output Ripple on
12 V Output, 3 - Feedback Pin of the NCP1396)
Figure 9. Output Ripple on Each LLC Stage
Output for Full Load Conditions (1 - 24 V Output,
2 - 30 V Output, 3 - 12 V Output)
Figure 10. LLC Stage Load Regulation for 230 V
Input Voltage (2 - Output Voltage on the 24 V Output,
4 - Output Current from the 24 V Output)
Figure 11. LLC Stage Operating Under Short
Circuit (1 - Ctimer Voltage, 2 - Feedback Voltage,
4 - Primary Current)
Figure 12. LLC Stage Full Load Operation
(1 - Bridge Voltage, 4 - Primary Current)
Figure 13. Detail of the ZVS Condition on the
Bridge - Rising Edge (1 - Bridge Voltage,
4 - Primary Current)
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AND8293/D
Figure 14. Detail of the ZVS Condition on the
Bridge - Falling Edge (1 - Bridge Voltage,
4 - Primary Current)
Figure 15. Standby Power Supply Waveforms Full Loaded (1 - NCP1027 Drain Voltage,
4 - Drain Current)
Figure 16. Standby Power Supply Waveforms No Load Conditions (1 - NCP1027 Drain Voltage)
Figure 17. PFC Stage Skip Mode
(1 - Q2 Drain Voltage, 2 - Bulk Voltage)
Layout Consideration
6. Application note AND8257/D
7. Application note AND8281/D
8. Bo Yang - Topology Investigation for Front End
DC-DC Power Conversion for Distributed Power
System
9. M. B. Borage, S. R. Tiwari and S. Kotaiah Design Optimization for an LCL - Type Series
Resonant Converter
10. Pulse Engineering - Transformer specification,
No: 2652.0017A
11. Pulse Engineering - Transformer specification,
No: 2362.0031B
12. Pulse Engineering - PFC inductor specification,
No: 2702.0012A
Please contact Pulse Engineering Company regarding
literature 10 - 12:
Pulse European Headquarters
Einsteinstrasse 1
71083 Herrenberg
Germany
TEL: 49 7032 7806 0
FAX: 49 7032 7806 12
Leakage inductance on the primary side is not very critical
for the LLC converter compared to other topologies, because
it will only slightly modify the resonant frequency. However
it is well to keep the areas of each power loop as small as
possible due to radiated EMI noise. A two- sided PCB with
one side ground plane helps (see Figures 21 and 23).
Thanks
I would like to thank the PULSE engineering company for
provided samples and support for magnetic components
used in this board.
I would also like to thank the COILCRAFT company for
providing samples of the filtering inductors.
CAUTION
This demo board is intended for demonstration and
evaluation purposes only and not for the end customer.
Literature
1. NCP1396A/B data sheet
2. NCP1605 data sheet
3. NCP1027 data sheet
4. Application note AND8241/D
5. Application note AND8255/D
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AND8293/D
EN50081-1 (Domestic) Conducted Emissions
EN50081-1 (Domestic) Conducted Emissions
90
80
80
70
70
60
60
LEVEL (dBmV)
LEVEL (dBmV)
90
50
40
30
50
40
30
20
20
10
10
0
0
100k
500k
1
5
10
30
100k
500k
1
5
10
FREQUENCY (mHz)
FREQUENCY (mHz)
Figure 18. Conducted EMI Signature of the
Board for Full Load and 230 VAC Input
Figure 19. Conducted EMI Signature of the
Board for Full Load and 110 VAC Input
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AND8293/D
Figure 20. Component Placement on the Top Side (Top View)
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AND8293/D
Figure 21. Top Side (Top View)
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AND8293/D
Figure 22. Component Placement on the Bottom Side (Bottom View)
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Figure 23. Bottom Side (Bottom View)
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Figure 24. Photo of the Designed Prototype (Real Dimensions are 200 x 130 mm)
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AND8293/D
BILL OF MATERIAL
Designator
Qty
Description
Value
Toleranc
e
Footprint
Manufacturer
Manufacturer
Part Number
B1
1
Bridge Rectifier
KBU8M
KBU
Fairchild
KBU8M
C1, C2, C3,
C8, C9, C12,
C13, C14,
C15, C43,
C44
11
Electrolytic
Capacitor
470mF/35V
20%
CPOL-EUE5-10.5
Rubycon
35ZL470M10X20
C10
1
Electrolytic
Capacitor
220mF/63V
10%
CPOL-EUE5-10.5
Rubycon
63 YXA220M 10x16
C11
1
MKP Capacitor
33nF/630Vdc
20%
C-EU150-084X183
Arcotronics
R73-0.033 mF 15 630V
C16
1
Electrolytic
Capacitor
220mF/35V
20%
CPOL-EUE5-10.5
Rubycon
35 RX30220M 10x12.5
C17, C48
2
Ceramic
Capacitor SMD
10n
10%
C-EUC1206
Epcos
B37872A5103K060
C18
1
Ceramic
Capacitor
220p
10%
C-EU050-045X075
Panasonic
ECKA3A221KBP
C19
1
Ceramic
Capacitor SMD
8n2
10%
C-EUC1206
Epcos
B37872A5822K060
C20, C23,
C32, C33,
C36, C52
6
C21
1
Ceramic
Capacitor SMD
150n
10%
C-EUC1206
Epcos
B37872A5154K060
C22
1
Ceramic
Capacitor SMD
220n
10%
C-EUC1206
Epcos
B37872A5224K060
C24
1
Ceramic
Capacitor SMD
390p
5%
C-EUC1206
Epcos
B37871K5391J060
C25
1
Ceramic
Capacitor SMD
1n2
10%
C-EUC1206
Epcos
B37872A5122K060
C26, C28,
C38, C40,
C51
5
Ceramic
Capacitor SMD
100n
10%
C-EUC1206
Epcos
B37872A5104K060
C27
1
Ceramic
Capacitor SMD
1n
10%
C-EUC1206
Epcos
B37872A5102K060
C29
1
Ceramic
Capacitor SMD
22n
10%
C-EUC1206
Epcos
B37872A5223K060
C31
1
Ceramic
Capacitor SMD
68n
10%
C-EUC1206
Epcos
B37872A5683K060
C34
1
Ceramic
Capacitor SMD
1mF
10%
C-EUC1206
Epcos
B37872K0105K062
C35
1
Electrolytic
Capacitor
4m7/35V
20%
CPOL-EUE2-5
Rubycon
35 MH54.7M 4x5
C37
1
Ceramic
Capacitor SMD
2n2
10%
C EUC1206
Epcos
B37872A5222K060
Rubycon
25 NXA220M 10x12.5
NU
C-EUC1206
C39
1
C4, C45
2
Electrolytic
Capacitor
220mF/25V
20%
CPOL-EUE5-10.5
C41
1
MKP Capacitor
10nF/630Vdc
20%
C-EU075-032X103
Epcos
B32560J8103M000
C46
1
Electrolytic
Capacitor
1u
20%
CPOL-EUE2-5
Rubycon
50 MH51M 4x5
C47
1
Electrolytic
Capacitor
100uF/35V
20%
CPOL-EUE5.5-8
Rubycon
50 PK100M 8x11.5
C49
1
Electrolytic
Capacitor
10mF/35V
20%
CPOL-EUE2.5-6
Rubycon
50 MH710M 6.3x7
C5, C30,
C42
3
MKP Capacitor
1mF/275Vac
20%
C-EU225-108X268
Arcotronics
R46KM410000N1M
C50
1
Ceramic
Capacitor SMD
100p
20%
C-EUC1206
Epcos
B37871K5101J060
NOTE:
NU
C-EU150-064X183
Please see the NCP1396A/B product folder on www.onsemi.com for PCB Gerber files and other collateral information
regarding this demo board.
http://onsemi.com
15
AND8293/D
BILL OF MATERIAL
Designator
Qty
Description
Value
Toleranc
e
Footprint
Manufacturer
Manufacturer
Part Number
C6
1
Electrolytic
Capacitor
100mF/450V
20%
EC18L40'22L35'
Rubycon
450 VXG100M 22x30
C7
1
Electrolytic
Capacitor
100mF/450V
20%
EC18L40'22L35_90'
Rubycon
450 VXG100M 22x30
CY1, CY2,
CY3
3
Ceramic
Capacitor
2n2/Y1
20%
CYYC10B4
Murata
DE1E3KX222MA5B
D1, D8, D12,
D13, D17
5
Diode
MMSD4148
SOD-123
ON Semiconductor
MMSD4148T1G
D11
1
Dual Diode
MBRF20100CT
TO-220
ON Semiconductor
MBRF20100CTG
D14, D21,
D23
3
Diode
MURA160SMD
SMA
ON Semiconductor
MURA160T3G
D15
1
Zener Diode
3V3
SOD-123
ON Semiconductor
MMSZ3V3T1G
D16
1
D18
1
ON Semiconductor
MMSZ7V5T1G
D19
1
D2
1
D20
5%
NU
Zener Diode
7V5
SOD-123
5%
SOD-123
NU
SMA
Diode
1N5408
Axial Lead
9.50x5.30mm
ON Semiconductor
1N5408G
1
Diode
MBRS340T3
SMC
ON Semiconductor
MBRS320T3G
D22
1
Zener Diode
18V
SOD-123
ON Semiconductor
MMSZ18T1G
D3, D5, D6,
D7, D9, D10
6
Diode
MBRS4201T3G
5%
SMC
ON Semiconductor
MBRS4201T3G
D4
1
Diode
MSR860
TO-220
ON Semiconductor
MSR860G
F1
1
FUSEHOLDER
, 20X5MM
SH22, 5A
SH22, 5A
Multicomp
MCHTC-15M
1
COVER, PCB
FUSEHOLDER
Multicomp
MCHTC-150M
1
FUSE,
MEDIUM
DELAY 4A
4A
BUSSMANN
TDC 210-4A
HEATSING_
1
1
Heatsing
SK 454 150 SA
SK454/150_GND
Fischer Elektronik
SK 454 150 SA
HEATSING_
2
1
Heatsing
SK 454 100 SA
SK454/100_GND
Fischer Elektronik
SK 454 100 SA
IC1
1
PFC Controller
NCP1605
SOIC 16
ON Semiconductor
NCP1605DR2G
IC2, IC6
2
Programmable
Precision
Reference
TL431SO8
SOIC-8
ON Semiconductor
NCV431AIDR2G
IC3
1
Resonant
Controller
NCP1396A
SOIC 16
ON Semiconductor
NCP1396ADR2G
IC4
1
Programmable
Precision
Reference
TLV431A
SOT-23
ON Semiconductor
TLV431ASN1T1G
IC5
1
HV Switcher for
Medium Power
Offline SMPS
NCP1027
PDIP (8 Minus Pin 6)
ON Semiconductor
NCP1027P065G
J1, J3
2
Connector
22-23-2071
MOLEX-7PIN
Molex
22-23-2071
J2
1
Connector
22-23-2101
MOLEX-10PIN
Molex
22-23-2101
J4
1
Connector
22-23-2051
MOLEX-5PIN
Molex
22-23-2051
J5
1
Connector
LP7.5/2/903.2 OR
Weidmueller
Weidmueller
LP7.5/2/903.2 OR
L1, L4, L5,
L10
4
Inductor
2m2
20%
RFB0807
Coilcraft
RFB0807-2R2L
L2
1
Inductor
2702.0012A
(260mH)
15%
Pulse_2702
Pulse
2702.0012A
L3
1
L6, L7
2
20%
DO5040H_100
Coilcraft
DO5040H-104MLB
NOTE:
NU
Inductor
100m
2722.0005A
Please see the NCP1396A/B product folder on www.onsemi.com for PCB Gerber files and other collateral information
regarding this demo board.
http://onsemi.com
16
AND8293/D
BILL OF MATERIAL
Designator
Qty
L8
1
L9
Toleranc
e
Footprint
Value
1
EMI Filter
7mH
TLBI
Pulse
6001.0069
OK1, OK2,
OK3
3
Opto-Coupler
PC817
PC817SMD
Avago
Technologies
HCPL-817-300E
Q1, Q3
2
MOSFET
Transistor
STP12NM50FP
TO-220
STMicroelectronics
STP12NM50FP
Q2
1
MOSFET
Transistor
STP20NM60FP
TO-220
STMicroelectronics
STP12NM50FP
Q4
1
PNP General
Purpose
Transistor
BC856-16L T1
SOT-23
ON Semiconductor
BC856-16L T1G
Q5, Q7
2
NPN General
Purpose
Transistor
BC817-16L T1
SOT-23
ON Semiconductor
BC817-16L T1G
Q6
1
NU
SOT-23
R1, R8, R19,
R20
4
Resistor SMD
10R
1%
R-EU_R1206
Vishay
RCA120610R0FKEA
R13
1
Resistor
Trough Hole
0.1R
1%
R-EU_0617/22
Vishay
PAC300001007FAC000
NU
Manufacturer
Manufacturer
Part Number
Description
TLBI
15%
R14
1
Resistor SMD
7k5
1%
R-EU_R1206
Vishay
RCA12067K50FKEA
R15, R51
2
Resistor SMD
8k2
1%
R-EU_M1206
Vishay
RCA12068K20FKEA
R17
1
Resistor SMD
47k
1%
R-EU_M1206
Vishay
RCA120647K0FKEA
R18
1
Resistor SMD
1k6
1%
R-EU_M1206
Vishay
RCA12061K60FKEA
R2, R5, R10,
R16
4
Resistor SMD
1M8
1%
R-EU_M1206
Vishay
RCA12061M80FKEA
R21, R25,
R26, R27,
R37, R46,
R50
7
Resistor SMD
NU
1%
R-EU_M1206
Vishay
R22
1
Resistor SMD
1k1
1%
R-EU_M1206
Vishay
RCA12061K10FKEA
R23, R33,
R34, R38,
R41, R73
6
Resistor SMD
1k
1%
R-EU_M1206
Vishay
RCA12061K00FKEA
R24, R77
2
Resistor SMD
18k
1%
R28
1
Varistor
VDRH10S275TSE
R-EU_M1206
Vishay
RCA120618K0FKEA
VARISTOR10K300
Vishay
2381 584 T271S
R29
1
Resistor SMD
33k
1%
R-EU_M1206
Vishay
RCA120633K0FKEA
R3, R6, R11
3
Resistor SMD
1M3
1%
R-EU_R1206
Vishay
RCA12061M30FKEA
R30
1
Resistor SMD
91k
1%
R-EU_M1206
Vishay
RCA120691K0FKEA
R31, R48
2
Resistor SMD
3k3
1%
R-EU_M1206
Vishay
RCA12063K30FKEA
R32, R39,
R55
3
Resistor SMD
15k
1%
R-EU_R1206
Vishay
RCA12061K50FKEA
R36
1
Resistor SMD
62k
1%
R-EU_M1206
Vishay
RCA120662K0FKEA
R4, R9, R12,
R35, R43,
R44, R52,
R57, R61,
R74, R79,
R80
12
Resistor SMD
10k
1%
R-EU_M1206
Vishay
RCA120610K0FKEA
R40
1
Resistor SMD
150R
1%
R-EU_R1206
Vishay
RCA1206150RFKEA
R42
1
Resistor SMD
18R
1%
R-EU_R1206
Vishay
RCA120618R0FKEA
R45
1
Resistor SMD
2k7
1%
R-EU_M1206
Vishay
RCA12062K70FKEA
R47
1
Resistor SMD
2k2
1%
R-EU_R1206
Vishay
RCA12062K20FKEA
R49
1
Resistor SMD
5k6
1%
R-EU_M1206
Vishay
RCA12065K60FKEA
R53
1
Resistor SMD
24k
1%
R-EU_R1206
Vishay
RCA120624K0FKEA
NOTE:
Please see the NCP1396A/B product folder on www.onsemi.com for PCB Gerber files and other collateral information
regarding this demo board.
http://onsemi.com
17
AND8293/D
BILL OF MATERIAL
Designator
Qty
Description
Value
Toleranc
e
Footprint
Manufacturer
Manufacturer
Part Number
R54
1
Resistor SMD
150k
1%
R-EU_R1206
Vishay
RCA1206150KFKEA
R56
1
Resistor SMD
6k8
1%
R-EU_R1206
Vishay
RCA12066K80FKEA
R58
1
Resistor SMD
1k5
1%
R-EU_R1206
Vishay
RCA12061K50FKEA
R59
1
Resistor SMD
6k2
1%
R-EU_R1206
Vishay
RCA12066K20FKEA
R60, R62,
R63
3
Resistor SMD
820R
1%
R-EU_R1206
Vishay
RCA1206820RFKEA
R64, R68
2
Resistor SMD
1M2
1%
R-EU_R1206
Vishay
RCA12061M20FKEA
R65
1
Resistor SMD
4k7
1%
R-EU_R1206
Vishay
RCA12064K70FKEA
R66
1
Resistor
Trough Hole
150k
1%
R-EU_0207/10
Vishay
MRS25000C1503FCT
R67
1
Resistor
Trough Hole
47R
1%
R-EU_0207/10
Vishay
MRS25000C4709FCT
R69
1
Option for
Thermistor
0R0
R7
1
Resistor SMD
0R0
1%
R-EU_M1206
Vishay
RCA12060000FKEA
R70
1
Resistor SMD
180k
1%
R-EU_M1206
Vishay
RCA1206180KFKEA
R71
1
Resistor SMD
3k9
1%
R-EU_M1206
Vishay
RCA12063K90FKEA
R72
1
Resistor SMD
100R
1%
R-EU_M1206
Vishay
RCA1206100RFKEA
R75
1
Resistor SMD
360k
1%
R-EU_M1206
Vishay
RCA1206360KFKEA
R76
1
Resistor SMD
470k
1%
R-EU_R1206
Vishay
RCA1206470KFKEA
R78
1
Resistor SMD
75k
1%
R-EU_M1206
Vishay
RCA120675K0FKEA
R81
1
Resistor
Trough Hole,
High Voltage
4M7
5%
R-EU_0414/15
Vishay
VR37000004704JA100
TR1
1
Resonant
Transformer
2652.0017A
15%
2652
Pulse
2652.0017A
TR2
1
Standby
Transformer
2362.0031B
15%
2362
Pulse
2362.0031B
P594
B1
1
Bridge Rectifier
KBU8M
KBU
Fairchild
KBU8M
C1, C2, C3,
C8, C9, C12,
C13, C14,
C15, C43,
C44
11
Electrolytic
Capacitor
470mF/35V
20%
CPOL-EUE5-10.5
Rubycon
35ZL470M10X20
C10
1
Electrolytic
Capacitor
220mF/63V
10%
CPOL-EUE5-10.5
Rubycon
63 YXA220M 10x16
C11
1
MKP Capacitor
33nF/630Vdc
20%
C-EU150-084X183
Arcotronics
R73-0.033uF 15 630V
C16
1
Electrolytic
Capacitor
220mF/35V
20%
CPOL-EUE5-10.5
Rubycon
35 RX30220M 10x12.5
C17, C48
2
Ceramic
Capacitor SMD
10n
10%
C-EUC1206
Epcos
B37872A5103K060
NOTE:
Please see the NCP1396A/B product folder on www.onsemi.com for PCB Gerber files and other collateral information
regarding this demo board.
ON Semiconductor and
are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice
to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability
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“Typical” parameters which may be provided in SCILLC data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All
operating parameters, including “Typicals” must be validated for each customer application by customer's technical experts. SCILLC does not convey any license under its patent rights
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AND8293/D