MAX15014, MAX15015, MAX15016, MAX15017
19-0734; Rev 0; 1/07
KIT
ATION
EVALU
E
L
B
AVAILA
1A, 4.5V to 40V Input Buck Converters with
50mA Auxiliary LDO Regulators
Features
The MAX15014–MAX15017 combine a step-down DCDC converter and a 50mA, low-quiescent-current lowdropout (LDO) regulator. The LDO regulator is ideal for
powering always-on circuitry in automotive applications.
The DC-DC converter input voltage range is 4.5V to 40V
for the MAX15015/MAX15016, and 7.5V to 40V for the
MAX15014/MAX15017.
Combined DC-DC Converters and Low-QuiescentCurrent LDO Regulators
1A DC-DC Converters Operate from 4.5V to 40V
(MAX15015/MAX15016) or 7.5V to 40V
(MAX15014/MAX15017)
Switching Frequency of 135kHz
(MAX15014/MAX15016) or 500kHz
(MAX15015/MAX15017)
50mA LDO Regulator Operates from 5V to 40V
Independent of the DC-DC Converter
47µA Quiescent Current with DC-DC Converter
Off and LDO On
6µA System Shutdown Current
Frequency Synchronization Input
Shutdown/Enable Inputs
Adjustable Soft-Start Time
Active-Low Open-Drain RESET Output with
Programmable Timeout Delay
Thermal Shutdown and Output Short-Circuit
Protection
Space-Saving (6mm x 6mm) Thermally Enhanced
36-Pin TQFN Package
The DC-DC converter output is adjustable from 1.26V to
32V and can deliver up to 1A of load current. These
devices utilize a feed-forward voltage-mode control
scheme for good noise immunity in the high-voltage
switching environment and offer external compensation
allowing for maximum flexibility with a wide selection of
inductor values and capacitor types. The switching
frequency is internally fixed at 135kHz and 500kHz,
depending on the version chosen. Moreover, the
switching frequency can be synchronized to an external clock signal through the SYNC input. Light load efficiency is improved by automatically switching to a
pulse-skip mode. The soft-start time is adjustable with
an external capacitor. The DC-DC converter can be
disabled independent of the LDO, thus reducing the
quiescent current to 47µA (typ).
The LDO linear regulators operate from 5V to 40V and
deliver a guaranteed 50mA load current. The devices
feature a preset output voltage of 5V (MAX1501_A) or
3.3V (MAX1501_B). Alternatively, the output voltage
can be adjusted from 1.5V to 11V by using an external
resistive divider. The LDO section also features a
RESET output with adjustable timeout period.
Protection features include cycle-by-cycle current limit,
hiccup-mode output short-circuit protection, and thermal
shutdown. All devices are available in a space-saving,
high-power (2.86W), 36-pin TQFN package and are
rated for operation over the -40°C to +125°C automotive
temperature range.
Ordering Information
PART
TEMP RANGE
PINPACKAGE
PKG
CODE
MAX15014AATX+ -40°C to +125°C 36 TQFN-EP*
T3666-3
MAX15014BATX+
-40°C to +125°C 36 TQFN-EP*
T3666-3
MAX15015AATX+ -40°C to +125°C 36 TQFN-EP*
T3666-3
MAX15015BATX+
-40°C to +125°C 36 TQFN-EP*
T3666-3
MAX15016AATX+ -40°C to +125°C 36 TQFN-EP*
T3666-3
-40°C to +125°C 36 TQFN-EP*
T3666-3
MAX15017AATX+ -40°C to +125°C 36 TQFN-EP*
T3666-3
Car Radios
MAX15017BATX+
T3666-3
Automotive Body Control Modules
+Denotes a lead-free package.
*EP = Exposed pad.
Applications
Automotive Instrument Cluster
MAX15016BATX+
-40°C to +125°C 36 TQFN-EP*
Navigation Systems
________________________________________________________________ Maxim Integrated Products
For pricing, delivery, and ordering information, please contact Maxim/Dallas Direct! at
1-888-629-4642, or visit Maxim’s website at www.maxim-ic.com.
1
MAX15014–MAX15017
General Description
MAX15014–MAX15017
1A, 4.5V to 40V Input Buck Converters with
50mA Auxiliary LDO Regulators
ABSOLUTE MAXIMUM RATINGS
LDO_OUT Output Current.................................Internally Limited
Switch DC Current (DRAIN and LX pins combined)
TJ = +125°C.......................................................................1.9A
TJ = +150°C.....................................................................1.25A
RESET Sink Current ..............................................................5mA
Continuous Power Dissipation (TA = +70°C)
36-Pin TQFN (derate 26.3mW/°C above +70°C)
Single-Layer Board .....................................................2105mW
36-Pin TQFN (derate 35.7mW/°C above +70°C)
Multilayer Board ..........................................................2857mW
Operating Temperature Range .........................-40°C to +125°C
Maximum Junction Temperature .....................................+150°C
Storage Temperature Range ............................-60°C to +150°C
Lead Temperature (soldering, 10s) ................................+300°C
IN_SW, IN_LDO, DRAIN, EN_SYS, EN_SW
to SGND ..............................................................-0.3V to +45V
IN_LDO to IN_SW ..................................................-0.3V to +0.3V
LX to SGND ...........................................-0.3V to (VIN_SW + 0.3V)
LX to PGND ...........................................-0.3V to (VIN_SW + 0.3V)
BST to SGND ..........................................-0.3V to (VIN_SW + 12V)
BST to LX................................................................-0.3V to +12V
PGND to SGND .....................................................-0.3V to +0.3V
REG, DVREG, SYNC, RESET, CT to SGND............-0.3V to +12V
FB, COMP_SW, SS to SGND....................-0.3V to (VREG + 0.3V)
SET_LDO, LDO_OUT to SGND ..............................-0.3V to +12V
C+ to PGND
(MAX15015/MAX15016 only)................(VDVREG - 0.3V) to 12V
C- to PGND
(MAX15015/MAX15016 only) ............-0.3V to (VDVREG + 0.3V)
Stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress ratings only, and functional
operation of the device at these or any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to
absolute maximum rating conditions for extended periods may affect device reliability.
ELECTRICAL CHARACTERISTICS
(VIN_SW = VIN_LDO = VDRAIN = 14V, VEN_SYS = VEN_SW = 2.4V, VREG = VDVREG, VSYNC = VSET_LDO = VSGND = VPGND = 0V, CREG =
1µF, CIN_SW = 0.1µF, CIN_LDO = 0.1µF, CLDO_OUT = 10µF, CDRAIN = 0.22µF, TA = TJ = -40°C to +125°C, unless otherwise noted.
Typical values are at TA = +25°C.) (Note 1)
PARAMETER
System Supply Current (Not
Switching)
Switching System Supply Current
LDO Quiescent Current
System Shutdown Current
System Enable Voltage
SYMBOL
CONDITIONS
MIN
VFB = 1.3V,
MAX15014/MAX15017
ISYS
ISW
ILDO
ISHDN
MAX
0.7
1.8
VFB = 1.3V,
MAX15015/MAX15016
0.85
VFB = 0V,
MAX15014/MAX15017
5.6
VFB = 0V,
MAX15015/MAX15016
8.6
ILDO_OUT = 100µA
47
63
ILDO_OUT = 50mA
130
200
6
10
1.8
mA
No load
VEN_SYS = 14V,
VEN_SW = 0V
VEN_SYS = 0V, VEN_SW = 0V
VEN_SYSH
EN_SYS = high, system on
VEN_SYSL
EN_SYS = low, system off
2.4
0.8
220
IEN_SYS
UNITS
mA
No load
System Enable Hysteresis
System Enable Input Current
TYP
µA
µA
V
mV
VEN_SYS = 2.4V
0.5
2
VEN_SYS = 14V
0.6
2
µA
BUCK CONVERTER
Input Voltage Range
2
VIN_SW
MAX15014/MAX15017
7.5
40.0
MAX15015/MAX15016
4.5
40.0
_______________________________________________________________________________________
V
1A, 4.5V to 40V Input Buck Converters with
50mA Auxiliary LDO Regulators
(VIN_SW = VIN_LDO = VDRAIN = 14V, VEN_SYS = VEN_SW = 2.4V, VREG = VDVREG, VSYNC = VSET_LDO = VSGND = VPGND = 0V, CREG =
1µF, CIN_SW = 0.1µF, CIN_LDO = 0.1µF, CLDO_OUT = 10µF, CDRAIN = 0.22µF, TA = TJ = -40°C to +125°C, unless otherwise noted.
Typical values are at TA = +25°C.) (Note 1)
PARAMETER
Undervoltage Lockout Threshold
SYMBOL
UVLOTH
Undervoltage Lockout
Hysteresis
UVLOHYST
Output Voltage Range
VOUT
Output Current
MIN
TYP
MAX
VIN_SW and IN_LDO rising,
MAX15014/MAX15017
CONDITIONS
6.7
7.0
7.4
VIN_SW and IN_LDO rising,
MAX15015/MAX15016
3.90
4.08
4.25
V
MAX15014/MAX15017
0.54
MAX15015/MAX15016
0.3
Minimum output
1.26
Maximum output
32
IOUT
EN_SW Input Voltage Threshold
V
V
1
VEN_SWH
EN_SW = high, switching power supply is on
VEN_SWL
EN_SW = low, switching power supply is off
A
2.4
0.8
EN_SW Hysteresis
220
Switching Enable Input Current
IEN_SW
UNITS
V
mV
VEN_SW = 2.4V
0.5
2
VEN_SW = 14V
0.6
2
µA
INTERNAL VOLTAGE REGULATOR
Output Voltage
VREG
Line Regulation
MAX15014/MAX15017, VIN_SW = 9V to 40V
7.6
8.4
MAX15015/MAX15016,
VIN_SW = 5.5V to 40V
4.75
5.25
VIN_SW = 9.0V to 40V, MAX15014/MAX15017
1
VIN_SW = 5.5V to 40V, MAX15015/MAX15016
1
V
mV/V
Load Regulation
IREG = 0 to 20mA
0.25
V
Dropout Voltage
VIN_SW = 7.5V (MAX15014/MAX15017),
VIN_SW = 4.5V (MAX15015/MAX15016),
IREG = 20mA
0.5
V
OSCILLATOR
Frequency Range
fCLK
Maximum Duty Cycle
Minimum LX Low Time
SYNC High-Level Voltage
SYNC Low-Level Voltage
DMAX
VSYNC = 0V, MAX15014/MAX15016
122
136
150
VSYNC = 0V, MAX15015/MAX15017
425
500
575
VSYNC = 0V, VIN_SW = 7.5V, MAX15014
(135kHz)
90
98
VSYNC = 0V, VIN_SW = 4.5V, MAX15016
(135kHz)
90
98
kHz
%
VSYNC = 0V, VIN_SW = 4.5V, MAX15015
(500kHz)
90
96
VSYNC = 0V, VIN_SW = 7.5V, MAX15017
(500kHz)
90
98
VSYNC = 0V
94
ns
2.2
0.8
V
_______________________________________________________________________________________
3
MAX15014–MAX15017
ELECTRICAL CHARACTERISTICS (continued)
MAX15014–MAX15017
1A, 4.5V to 40V Input Buck Converters with
50mA Auxiliary LDO Regulators
ELECTRICAL CHARACTERISTICS (continued)
(VIN_SW = VIN_LDO = VDRAIN = 14V, VEN_SYS = VEN_SW = 2.4V, VREG = VDVREG, VSYNC = VSET_LDO = VSGND = VPGND = 0V, CREG =
1µF, CIN_SW = 0.1µF, CIN_LDO = 0.1µF, CLDO_OUT = 10µF, CDRAIN = 0.22µF, TA = TJ = -40°C to +125°C, unless otherwise noted.
Typical values are at TA = +25°C.) (Note 1)
PARAMETER
SYNC Frequency Range
SYMBOL
fSYNC
CONDITIONS
MIN
TYP
MAX
MAX15014/MAX15016
100
200
MAX15015/MAX15017
400
600
Ramp Level Shift (Valley)
0.3
UNITS
kHz
V
ERROR AMPLIFER
Soft-Start Reference Voltage
VSS
1.210
1.260
V
µA
Soft-Start Current
ISS
7
12
17
FB Regulation Voltage
VFB
1.210
1.235
1.260
V
FB Input Range
VFB
0
1.5
V
FB Input Current
IFB
VFB = 1.244V
-250
+250
nA
ICOMP = -500µA to +500µA
0.25
4.5
COMP Voltage Range
VSS = 0V
1.235
Open-Loop Gain
Unity-Gain Bandwidth
PWM Modulator Gain
V
80
dB
1.8
MHz
fSYNC = 500kHz, MAX15015/MAX15017
10
fSYNC = 135kHz, MAX15014/MAX15016
10
V/V
CURRENT-LIMIT COMPARATOR
Pulse Skip Threshold
IPFM
100
200
300
mA
Cycle-by-Cycle Current Limit
IILIM
1.3
2
2.6
A
Number of Consecutive ILIM
Events to Hiccup
Hiccup Timeout
7
—
512
Clock
periods
POWER SWITCH
Switch On-Resistance
VBST - VLX = 6V
Switch Gate Charge
VBST - VLX = 6V
Switch Leakage Current
VIN_SW = VIN_LDO = VLX = VDRAIN =
40V, VFB = 0V
BST Quiescent Current
VBST = 40V, VDRAIN = 40V, VFB = 0V,
DVREG = 5V
BST Leakage Current
VBST = VDRAIN = VLX = VIN_SW =
VIN_LDO = 40V, EN_SW = 0V
0.15
0.4
0.80
4
400
Ω
nC
10
µA
600
µA
1
µA
CHARGE PUMP (MAX15015/MAX15016)
C- Output Voltage Low
Sinking 10mA
0.1
V
C- Output Voltage High
Relative to DVREG, sourcing 10mA
0.1
V
DVREG to C+ On-Resistance
Sourcing 10mA
10
Ω
LX to PGND On-Resistance
Sinking 10mA
12
Ω
40
V
4.25
V
LDO
Input Voltage Range
VIN_LDO
Undervoltage Lockout Threshold
UVLO_LDOTH
Undervoltage Lockout Hysteresis
UVLO_LDOHYST
4
5
VIN_LDO rising
3.90
4.1
0.3
_______________________________________________________________________________________
V
1A, 4.5V to 40V Input Buck Converters with
50mA Auxiliary LDO Regulators
(VIN_SW = VIN_LDO = VDRAIN = 14V, VEN_SYS = VEN_SW = 2.4V, VREG = VDVREG, VSYNC = VSET_LDO = VSGND = VPGND = 0V, CREG =
1µF, CIN_SW = 0.1µF, CIN_LDO = 0.1µF, CLDO_OUT = 10µF, CDRAIN = 0.22µF, TA = TJ = -40°C to +125°C, unless otherwise noted.
Typical values are at TA = +25°C.) (Note 1)
PARAMETER
Output Current
SYMBOL
IOUT
CONDITIONS
VIN = 6V (Note 2)
SET_LDO = SGND,
MAX1501_A
Output Voltage
VLDO_OUT
SET_LDO = SGND,
MAX1501_B
Adjustable Output Voltage Range
VADJ
∆VDO
Dropout Voltage
SET_LDO Input Leakage Current
Power-Supply Rejection Ratio
Short-Circuit Current
ISET_LDO
PSRR
ISC
UNITS
200
mA
4.90
5
5.06
ILDO_OUT = 1mA
4.90
5
5.06
6V ≤ VIN_LDO ≤ 40V,
ILDO_OUT = 1mA
4.85
5
5.15
1mA ≤ IOUT ≤ 50mA,
VIN_LDO = 14V
4.85
5
5.15
ILDO_OUT = 100µA
3.22
3.3
3.35
ILDO_OUT = 1mA
3.22
3.3
3.35
6V ≤ VIN_LDO ≤ 40V,
ILDO_OUT = 1mA
3.2
3.3
3.4
1mA ≤ ILDO_OUT ≤
50mA, VIN_LDO =
14V
3.2
3.3
3.4
1.5
11.0
IOUT = 10mA
0.6
IOUT = 50mA
0.82
IOUT = 10mA
0.1
IOUT = 50mA
0.4
VSET_LDO
Minimum SET_LDO Threshold
MAX
ILDO_OUT = 100µA
From EN_SYS high to LDO_OUT rise,
RL = 500Ω, SET_LDO = SGND
Startup Response Time
SET_LDO Reference Voltage
VIN_LDO = 4.0V,
MAX1501_B
TYP
65
VSET_LDO > 0.25V
VIN_LDO = 5V,
MAX1501_A
MIN
400
1.220
1.241
(Note 3)
185
VSET_LDO = 11V
0.5
IOUT = 10mA, f = 100Hz, 500mVP-P,
VLDO_OUT = 5V
78
IOUT = 10mA, f = 1MHz, 500mVP-P,
VLDO_OUT = 5V
24
V
V
V
µs
1.265
V
mV
100
nA
dB
125
185
300
mA
_______________________________________________________________________________________
5
MAX15014–MAX15017
ELECTRICAL CHARACTERISTICS (continued)
MAX15014–MAX15017
1A, 4.5V to 40V Input Buck Converters with
50mA Auxiliary LDO Regulators
ELECTRICAL CHARACTERISTICS (continued)
(VIN_SW = VIN_LDO = VDRAIN = 14V, VEN_SYS = VEN_SW = 2.4V, VREG = VDVREG, VSYNC = VSET_LDO = VSGND = VPGND = 0V, CREG =
1µF, CIN_SW = 0.1µF, CIN_LDO = 0.1µF, CLDO_OUT = 10µF, CDRAIN = 0.22µF, TA = TJ = -40°C to +125°C, unless otherwise noted.
Typical values are at TA = +25°C.) (Note 1)
PARAMETER
SYMBOL
CONDITIONS
MIN
TYP
MAX
UNITS
90
92.5
95
%VOUT
0.4
V
1
µA
RESET OUTPUT
RESET Threshold
V RESET
RESET goes high after rising VLDO_OUT
crosses this threshold
RESET Output Low Voltage
VRL
(VLDO_OUT – V RESET) / IRESET = 4kΩ
RESET Output High Leakage
Current
IRH
V RESET = 3.3V (For MAX15_ _ _B),
V RESET = 5V (For MAX15_ _ _A)
RESET Output Minimum Timeout
Period
When LDO_OUT reaches RESET threshold,
CT = unconnected
50
µs
ENABLE to RESET Minimum
Timeout Period
When EN_SYS goes high, CLDO_OUT =
10µF, ILDO_OUT = 50mA, VLDO_OUT = 3.3V,
CT = unconnected
650
µs
Delay Comparator Threshold
(Rising)
VCT-TH
Delay Comparator Threshold
Hysteresis
VCTTH-
CT Charge Current
ICT-CHQ
CT Discharge Current
ICT-DIS
1.220
1.241
1.265
100
HYST
VCT = 0V
1.5
2
V
mV
3
µA
18
mA
+160
°C
20
°C
THERMAL SHUTDOWN
Thermal Shutdown Temperature
Thermal Shutdown Hysteresis
Temperature rising
Note 1: Limits at -40°C are guaranteed by design and not production tested.
Note 2: Maximum output current is limited by package power dissipation.
Note 3: This is the minimum voltage needed at SET_LDO for the system to recognize that the user wants an adjustable LDO_OUT.
6
_______________________________________________________________________________________
1A, 4.5V to 40V Input Buck Converters with
50mA Auxiliary LDO Regulators
MAX15014–MAX15017
Typical Operating Characteristics
(VIN_SW = VIN_LDO = VDRAIN =14V, VEN_SYS = VEN_SW = 2.4V, VREG = VDVREG, VSYNC = VSET_LDO = VSGND = VPGND = 0V, CREG =
1µF, CIN_SW = 0.1µF, CIN_LDO = 0.1µF, CLDO_OUT = 10µF, CDRAIN = 0.22µF, see Figures 6 and 7, TA = +25°C, unless otherwise noted.)
6
5
4
3
2
MAX15016A
139
1
138
137
136
135
134
133
132
0
50
100
TEMPERATURE (°C)
150
96
95
94
93
ERROR AMPLIFIER OPEN-LOOP GAIN
AND PHASE vs. FREQUENCY
98
96
92
90
88
86
84
91
82
0
5
10
15 20 25 30
INPUT VOLTAGE (V)
35
0
40
340
5
10
15
20
25
30
35
40
70
60
50
40
30
260
220
180
140
PHASE
100
60
0.1
INPUT VOLTAGE (V)
OUTPUT CURRENT LIMIT
vs. INPUT VOLTAGE
1
10
100 1k 10k 100k 1M 10M
FREQUENCY (Hz)
TURN-ON/-OFF WAVEFORM
TURN-ON/-OFF WAVEFORM
MAX15014 toc09
MAX15014 toc08
MAX15014 toc07
2.5
TA = 0°C
TA = +25°C
2.0
ILOAD = 1A
ILOAD = 100mA
EN_SW
2V/div
0V
1.5
TA = +85°C
1.0
300
GAIN
20
10
0
-10
80
90
MAX15014 toc06
110
100
90
80
94
92
470
MAXIMUM DUTY CYCLE
vs. INPUT VOLTAGE (MAX15015A)
GAIN (dB)
97
480
-60 -40 -20 0 20 40 60 80 100 120 140 160
TEMPERATURE (°C)
MAX15014 toc05
98
490
450
100
MAXIMUM DUTY CYCLE (%)
MAX15014 toc04
99
500
-60 -40 -20 0 20 40 60 80 100 120 140 160
TEMPERATURE (°C)
MAXIMUM DUTY CYCLE
vs. INPUT VOLTAGE (MAX15016A)
100
510
460
130
-50
MAXIMUM DUTY CYCLE (%)
MAX15015A
520
131
0
OUTPUT CURRENT LIMIT (A)
530
EN_SW
2V/div
0V
TA = +135°C
VOUT
2V/div
VOUT
2V/div
0.5
0V
0V
0
0
10
20
30
INPUT VOLTAGE (V)
40
50
PHASE (DEGREES)
7
140
SWITCHING FREQUENCY (kHz)
8
SWITCHING FREQUENCY
vs. TEMPERATURE
MAX15014 toc02
MAX15016
9
SWITCHING FREQUENCY (kHz)
MAX15014 toc01
SYSTEM SHUTDOWN CURRENT (µA)
10
SWITCHING FREQUENCY
vs. TEMPERATURE
MAX15014 toc03
SYSTEM SHUTDOWN CURRENT
vs. TEMPERATURE
2ms/div
2ms/div
_______________________________________________________________________________________
7
Typical Operating Characteristics (continued)
(VIN_SW = VIN_LDO = VDRAIN =14V, VEN_SYS = VEN_SW = 2.4V, VREG = VDVREG, VSYNC = VSET_LDO = VSGND = VPGND = 0V, CREG =
1µF, CIN_SW = 0.1µF, CIN_LDO = 0.1µF, CLDO_OUT = 10µF, CDRAIN = 0.22µF, see Figures 6 and 7, TA = +25°C, unless otherwise noted.)
TURN-ON/-OFF WAVEFORM
INCREASING VIN
TURN-ON/-OFF WAVEFORM
INCREASING VIN
OUTPUT VOLTAGE vs. TEMPERATURE
MAX15014 toc11
MAX15014 toc10
ILOAD = 100mA
3.38
0V
VOUT
2V/div
VOUT
2V/div
3.36
OUTPUT VOLTAGE (V)
VIN
5V/div
VIN
5V/div
0V
3.34
3.32
ILOAD = 0A
3.30
3.28
3.26
3.24
0V
0V
MAX15014 toc12
3.40
ILOAD = 1A
ILOAD = 1A
3.22
3.20
10ms/div
EFFICIENCY vs. LOAD CURRENT
EFFICIENCY vs. LOAD CURRENT
(MAX15015A)
VIN = 4.5V
80
VIN = 12V
50
VIN = 24V
40
VIN = 40V
30
VIN = 7.5V
VIN = 4.5V
80
MAX15016A
ILDO_OUT = 0A
0
100
10
100
LOAD CURRENT (mA)
VIN = 12V
60
50
VIN = 24V
40
VIN = 24V
60
50
VIN = 12V
40
VIN = 40V
30
VIN = 40V
20
20
10
10
0
1000
1
100
10
1000
1
LOAD CURRENT (mA)
10
100
LOAD CURRENT (mA)
MAX15014 toc16
90
VIN = 7.5V
80
MAX15014 toc18
VIN = 4.5V, IOUT = 0.25A TO 1A
MAX15015A
VIN = 12V, IOUT = 0.25A TO 1A
MAX15015A
VOUT
AC-COUPLED
100mV/div
VOUT
AC-COUPLED
100mV/div
70
VIN = 24V
60
50
VIN = 12V
40
30
ILOAD
500mA/div
VIN = 40V
ILOAD
500mA/div
20
0
10
0
0
1
8
1000
LOAD-TRANSIENT RESPONSE
LOAD-TRANSIENT RESPONSE
MAX15014 toc17
VOUT = 5V
135
70
EFFICIENCY vs. LOAD CURRENT
(MAX15017A)
100
110
VIN = 7.5V
80
0
1
10
35
60
85
TEMPERATURE (°C)
VOUT = 5V
90
70
30
20
10
VOUT = 3.3V
90
EFFICIENCY (%)
EFFICIENCY (%)
70
60
100
EFFICIENCY (%)
90
VIN = 7.5V
-15
EFFICIENCY vs. LOAD CURRENT
(MAX15014)
MAX15014 toc14
VOUT = 3.3V
-40
MAX15014 toc15
10ms/div
MAX15014 toc13
100
EFFICIENCY (%)
MAX15014–MAX15017
1A, 4.5V to 40V Input Buck Converters with
50mA Auxiliary LDO Regulators
10
100
LOAD CURRENT (mA)
1000
200µs/div
200µs/div
_______________________________________________________________________________________
1A, 4.5V to 40V Input Buck Converters with
50mA Auxiliary LDO Regulators
LX VOLTAGE AND INDUCTOR CURRENT
LX VOLTAGE AND INDUCTOR CURRENT
MAX15014 toc20
MAX15014 toc19
MAX150_ _
VLX
5V/div
VLX
5V/div
0V
0V
INDUCTOR CURRENT
100mA/div
INDUCTOR CURRENT
200mA/div
0V
ILOAD = 40mA
ILOAD = 160mA
2µs/div
2µs/div
LX VOLTAGE AND INDUCTOR CURRENT
MINIMUM LX PULSE WIDTH
vs. LOAD CURRENT
MAX15014 toc21
MAX15014 toc22
400
350
LX PULSE WIDTH (ns)
VLX
5V/div
0V
INDUCTOR CURRENT
500mA/div
300
250
200
150
100
50
ILOAD = 1A
VOUT = 3.3V
0
300
2µs/div
400
500
600
700
800
900
1000
LOAD CURRENT (mA)
40
NO LOAD
30
20
5.05
ILOAD = 1mA
5.00
ILOAD = 10mA
4.95
ILOAD = 50mA
4.90
10
MAX15015A
MAX15015B
0
4.85
-50
-25
0
25
50
75
TEMPERATURE (°C)
100
125
ILOAD = 1mA
3.30
LDO OUTPUT VOLTAGE (V)
50
3.31
MAX15014 toc24
ILOAD = 100µA
LDO OUTPUT VOLTAGE (V)
LDO QUIESCENT CURRENT (µA)
60
OUTPUT VOLTAGE
vs. TEMPERATURE
5.10
MAX15014 toc23
70
OUTPUT VOLTAGE
vs. TEMPERATURE
MAX15014 toc25
LDO QUIESCENT CURRENT
vs. TEMPERATURE
3.29
3.28
ILOAD = 10mA
3.27
3.26
ILOAD = 50mA
3.25
3.24
MAX15015B
3.23
-40
-15
10
35
60
85
TEMPERATURE (°C)
110
135
-40
-15
10
35
60
85
TEMPERATURE (°C)
110
135
_______________________________________________________________________________________
9
MAX15014–MAX15017
Typical Operating Characteristics (continued)
(VIN_SW = VIN_LDO = VDRAIN =14V, VEN_SYS = VEN_SW = 2.4V, VREG = VDVREG, VSYNC = VSET_LDO = VSGND = VPGND = 0V, CREG =
1µF, CIN_SW = 0.1µF, CIN_LDO = 0.1µF, CLDO_OUT = 10µF, CDRAIN = 0.22µF, see Figures 6 and 7, TA = +25°C, unless otherwise noted.)
Typical Operating Characteristics (continued)
(VIN_SW = VIN_LDO = VDRAIN =14V, VEN_SYS = VEN_SW = 2.4V, VREG = VDVREG, VSYNC = VSET_LDO = VSGND = VPGND = 0V, CREG =
1µF, CIN_SW = 0.1µF, CIN_LDO = 0.1µF, CLDO_OUT = 10µF, CDRAIN = 0.22µF, see Figures 6 and 7, TA = +25°C, unless otherwise noted.)
700
0
TA = +85°C
TA = +25°C
500
400
TA = -40°C
ILOAD = 50mA
EN_SYS
2V/div
ILDO_OUT = 10mA
-20
PSRR (dB)
600
ILDO_OUT = 50mA
-10
MAX15014 toc28
MAX15014 toc27
VIN = 5V, ILOAD = 0 TO 50mA
MAX15015A
TA = +135°C
800
10
MAX15014 toc26
900
TURN-ON/-OFF WAVEFORM
TOGGLING EN_SYS
POWER-SUPPLY REJECTION RATIO
DROPOUT VOLTAGE vs. LOAD CURRENT
DROPOUT VOLTAGE (mV)
MAX15014–MAX15017
1A, 4.5V to 40V Input Buck Converters with
50mA Auxiliary LDO Regulators
0V
-30
-40
300
-50
200
-60
100
-70
VOUT
2V/div
0V
ILDO_OUT = 1mA
-80
0
0
10
20
30
LOAD CURRENT (mA)
40
0.1k
50
1k
10k
100k
FREQUENCY (Hz)
1M
2ms/div
10M
TURN-ON/-OFF WAVEFORM
TOGGLING EN_SYS
TURN-ON/-OFF WAVEFORM
TOGGLING EN_SYS
MAX15014 toc30
MAX15014 toc29
RLOAD = 1kΩ
MAX15015B
RLOAD = 66Ω
EN_SYS
2V/div
EN_SYS
2V/div
0V
0V
VLDO_OUT
1V/div
VOUT
2V/div
0V
0V
10ms/div
10ms/div
TURN-ON/-OFF WAVEFORM
TOGGLING EN_SYS
TURN-ON/-OFF WAVEFORM
INCREASING VIN
MAX15014 toc32
MAX15014 toc31
ILOAD = 50mA
MAX15015B
RLOAD = 660Ω
EN_SYS
2V/div
VIN
5V/div
0V
0V
VLDO_OUT
1V/div
0V
0V
10ms/div
10
VLDO_OUT
2V/div
10ms/div
______________________________________________________________________________________
1A, 4.5V to 40V Input Buck Converters with
50mA Auxiliary LDO Regulators
TURN-ON/-OFF WAVEFORM
INCREASING VIN
LDO TURN-ON/-OFF WAVEFORM
WITH INCREASING VIN
MAX15014 toc34
MAX15014 toc33
ILOAD = 5mA
MAX15015B
RLOAD = 66Ω
VIN
2V/div
VIN
5V/div
0V
0V
VLDO_OUT
1V/div
VLDO_OU
2V/div
0V
0V
10ms/div
10ms/div
TURN-ON/-OFF WAVEFORM
INCREASING VIN
LOAD-TRANSIENT RESPONSE
MAX15014 toc36
MAX15014 toc35
MAX15015B
RLOAD = 660Ω
VLDO_OUT
AC-COUPLED
100mV/div
VIN
5V/div
0V
VLDO_OUT
1V/div
0V
ILOAD
20mA/div
0
10ms/div
100µs/div
INPUT-VOLTAGE STEP RESPONSE
RESIDUAL SWITCHING NOISE
ON THE LDO OUTPUT
MAX15014 toc38
MAX15014 toc37
DC-DCLOAD = 1A
MAX15015B
ILOAD = 1mA
VIN
20V/div
VLDO_OUT
10mV/div
0V
VLDO_OUT
AC-COUPLED
100mV/div
1ms/div
400ns/div
______________________________________________________________________________________
11
MAX15014–MAX15017
Typical Operating Characteristics (continued)
(VIN_SW = VIN_LDO = VDRAIN =14V, VEN_SYS = VEN_SW = 2.4V, VREG = VDVREG, VSYNC = VSET_LDO = VSGND = VPGND = 0V, CREG =
1µF, CIN_SW = 0.1µF, CIN_LDO = 0.1µF, CLDO_OUT = 10µF, CDRAIN = 0.22µF, see Figures 6 and 7, TA = +25°C, unless otherwise noted.)
MAX15014–MAX15017
1A, 4.5V to 40V Input Buck Converters with
50mA Auxiliary LDO Regulators
Pin Description
PIN
NAME
FUNCTION
MAX15014/
MAX15017
MAX15015/
MAX15016
1, 2, 3, 9, 12,
14, 16, 19, 24,
26, 27, 30, 35
1, 2, 3, 9, 12,
14, 16, 19, 24,
26, 27, 30, 35
N.C.
No Connection. Not internally connected. Leave unconnected or connect to SGND.
23, 28
—
I.C.
Internally Connected. Leave unconnected.
4
4
RESET
Active-Low Reset Output. When the rising VLDO_OUT voltage crosses the reset
threshold, RESET goes high after an adjustable delay. Pull up RESET to LDO_OUT
with at least 4kΩ. RESET is an active-low open-drain output.
5
5
SGND
Signal Ground Connection. Connect SGND and PGND together at one point near
the input bypass capacitor negative terminal.
6
6
CT
7
7
EN_SW
Switching Regulator Enable Input (Active High). If EN_SW is high and EN_SYS is
high, the switching power supply is enabled. EN_SW is internally pulled down to
SGND through a 0.5µA current sink.
8
8
EN_SYS
Active-High System Enable Input. Connect EN_SYS high to turn on the system. The
LDO is active if EN_SYS is high; once EN_SYS is high, the switching regulator can
be turned on if EN_SW is high. EN_SYS is internally pulled down to SGND through a
0.5µA current sink.
10
10
SET_LDO
LDO Feedback Input/Output Voltage Setting. Connect SET_LDO to SGND to select
the preset output voltage (5V or 3.3V). Connect SET_LDO to an external resistordivider network for adjustable output operation.
11
11
LDO_OUT
Linear Regulator Output. Bypass with at least 10µF low-ESR capacitor from
LDO_OUT to SGND. In the 5V LDO versions (A), the LDO operates in dropout below
6V down to the UVLO trip point.
13
13
IN_LDO
15
15
BST
17, 18
17, 18
LX
20, 21
20, 21
DRAIN
Drain Connection of the Internal High-Side Switch. Connect both DRAIN inputs
together.
PGND
Power Ground Connection. Connect the input bypass capacitor negative terminal,
the anode of the freewheeling diode, and the output filter capacitor negative terminal
to PGND. Connect PGND to SGND together at a single point near the input bypass
capacitor negative terminal.
22
12
Reset Timeout Delay Capacitor Connection. CT is pulled low during reset. When out
of reset, CT is pulled up to an internal 3.6V rail with a 2µA current source. When the
rising CT voltage reaches the trip threshold (typically 1.24V), RESET is deasserted.
When EN_SYS is low or in thermal shutdown, CT is low.
22
LDO Input Voltage. The input voltage range for the LDO extends from 5V to 40V.
Bypass with a 0.1µF ceramic capacitor to SGND.
High-Side Gate Driver Supply. Connect BST to the cathode of the bootstrap diode
and to the positive terminal of the bootstrap capacitor.
Source Connection of Internal High-Side Switch. Connect both LX pins to the
inductor and the cathode of the freewheeling diode.
______________________________________________________________________________________
1A, 4.5V to 40V Input Buck Converters with
50mA Auxiliary LDO Regulators
PIN
MAX15014/
MAX15017
MAX15015/
MAX15016
NAME
FUNCTION
—
23
C-
25
25
DVREG
—
28
C+
29
29
SYNC
Oscillator Synchronization Input. SYNC can be driven by an external clock to
synchronize the switching frequency. Connect SYNC to SGND when not used.
31
31
COMP
Error Amplifier Output. Connect COMP to the compensation feedback network.
32
32
FB
Feedback Regulation Point. Connect to the center tap of a resistive divider from
converter output to SGND to set the output voltage. The FB voltage regulates to the
voltage present at SS (1.235V).
33
33
SS
Soft-Start and Reference Output. Connect a capacitor from SS to SGND to set the
soft-start time. See the Applications Information section to calculate the value of the
CSS capacitor.
34
34
REG
Internal Regulator Output. 5V output for the MAX15015/MAX15016 and 8V output for the
MAX15014/MAX15017. Bypass to SGND with at least a 1µF ceramic capacitor.
36
36
IN_SW
Supply Input Connection. Connect to IN_LDO and an external voltage source from
4.5V to 40V. EN_SW and EN_SYS must be high and IN_SW must be above its UVLO
threshold for operation of the switching regulator.
—
—
EP
Charge-Pump Flying Capacitor Negative Connection (MAX15015/MAX15016 only)
Gate Drive Supply for the High-Side MOSFET Driver. Connect to REG and to the
anode of the bootstrap diode for MAX15014/MAX15017. Connect to REG for
MAX15015/MAX15016.
Charge-Pump Flying Capacitor Positive Connection (MAX15015/MAX15016 only).
Connect to the positive terminal of the external pump capacitor and to the anode of
the bootstrap diode.
Exposed Pad. The exposed pad must be electrically connected to SGND. For an
effective heatsinking, solder the exposed pad to a large copper plane.
______________________________________________________________________________________
13
MAX15014–MAX15017
Pin Description
MAX15014–MAX15017
1A, 4.5V to 40V Input Buck Converters with
50mA Auxiliary LDO Regulators
Detailed Description
current falls to 6µA. Additional features include a programmable soft-start, cycle-by-cycle current limit,
hiccup-mode output short-circuit protection, and thermal
shutdown.
The LDO linear regulator operates from 5V to 40V and
delivers a guaranteed 50mA load current. The devices
feature a preset output voltage of 5.0V (MAX1501_A) or
3.3V (MAX1501_B). Alternatively, the output voltage
can be adjusted from 1.5V to 11V using an external
resistive divider. The LDO section also features a
RESET output with adjustable timeout period.
The MAX15014–MAX15017 combine a voltage-mode
buck converter with an internal 0.5Ω power MOSFET
switch and a low-quiescent-current LDO regulator. The
buck converter of the MAX15015/MAX15016 has a
wide input voltage range of 4.5V to 40V. The
MAX15014/MAX15017’s input voltage range is 7.5V to
40V. Fixed switching frequencies of 135kHz and
500kHz are available. The internal low RDS_ON switch
allows for up to 1A of output current, and the output
voltage can be adjusted from 1.26V to 32V. External
compensation and voltage feed-forward simplify loop
compensation design and allow for a wide variety of L
and C filter components. All devices offer an automatic
switchover to pulse-skipping (PFM) mode, providing
low quiescent current and high efficiency at light loads.
Under no load, PFM mode operation reduces the current consumption to 5.6mA for the MAX15014/
MAX15017 and 8.6mA for the MAX15015/MAX15016. In
shutdown (DC-DC and LDO regulator off), the supply
IN_SW
Enable Inputs and UVLO
The MAX15014–MAX15017 feature two logic inputs,
EN_SW (active-high) and EN_SYS (active-high) that can
be used to enable the switching power supply and the
LDO_OUT outputs. When VEN_SW is higher than the
threshold and EN_SYS is high, the switching power supply is enabled. When EN_SYS is high, the LDO is active.
When EN_SYS is low, the entire chip is off (see Table 1).
EN_SYS
IN_LDO
C-
C+
DVREG
DVREG
IN_LDO
VINT
REG
UVLO_LDO
VREFOK
VINTOK
VINT
VINT
VREG_EN
UVLO_SW
TSD
SHDN
-
ENABLE LDO
THERMAL
SHDN
TSD
-
SHDN
VREF
VINT
SET_LOD
MUX
VINT
UVLO_LDO
TSD
SHDN
VINT
VREF
VREFOK
+
PREREG
+
VREF
REF
VINT
VINTOK
VREG_OK
ISS
LDO_OUT
PASS ELEMENT
4.1V
+
REG_LDO
LEVEL
SHIFT
PCLK
UVLO_SW
VREFOK
VINTOK
-
EN_SW
MAX15015/MAX15016
7.0V OR 4.1V
VINT
VINT
2µA
OUT_LDO
185mV
0.925 x VREF
VREF
+
RESET
+
DELAY COMPARATOR
CT
EN
VREG_ OK
DRAIN
+
SS
+
E/A
-
FB
+
SSA
-
-
HIGH-SIDE
CURRENT
SENSE
PFM
OVERLOAD
MANAGEMENT
COMP
REF_ILIM
+
VREF
-
REF_PFM
BST
CLK
OVERL
LX
IN S/W
SYNC
EN
OSC
RAMP
-
+
CPWM
+
PFM
0.3V
SGND
DVREG
LOGIC
CLK
SCLK
PCLK
Figure 1. MAX15015/MAX15016 Simplified Block Diagram
14
______________________________________________________________________________________
PGND
1A, 4.5V to 40V Input Buck Converters with
50mA Auxiliary LDO Regulators
EN_SYS
IN_LDO
-
PASS ELEMENT
4.1V
VINT
VINT
VINT
VREG_EN
UVLO_SW
TSD
SHDN
-
ENABLE LDO
THERMAL
SHDN
TSD
-
SHDN
VREF
MUX
VINT
UVLO_LDO
TSD
SHDN
VINT
VREF
VREFOK
+
PREREG
VINTOK
VREG_OK
EN_SW
LDO_OUT
UVLO_LDO
VREFOK
VINTOK
+
VREF
REF
UVLO_SW
VREFOK
VINTOK
+
REG_LDO
ISS
MAX15014/MAX15017
7.0V OR 4.1V
VINT
REG
IN_LDO
VINT
VINT
2µA
VINT
SET_LOD
OUT_LDO
185mV
0.925 x VREF
VREG_ OK
VREF
+
+
RESET
DELAY COMPARATOR
EN
CT
+
+
E/A
-
SS
FB
+
SSA
-
ILIM
VREF
DRAIN
-
REF_ILIM
HIGH-SIDE
CURRENT
SENSE
+
PFM
OVERLOAD
MANAGEMENT
COMP
-
REF_PFM
CLK
BST
OVERL
IN S/W
SYNC
EN
OSC
RAMP
LX
+
-
CPWM
PFM
SCLK
0.3V
PCLK
CLK
SGND
DVREG
LOGIC
+
PGND
Figure 2. MAX15014/MAX15017 Simplified Block Diagram
Table 1. Enable Inputs Configuration
EN_SW
LDO REGULATOR
DC-DC SWITCHING
CONVERTER
Low
Low
Off
Off
Low
High
Off
Off
EN_SYS
High
Low
On
Off
High
High
On
On
The MAX15014–MAX15017 provide undervoltage lockout (UVLO). The UVLO monitors the input voltage
(VIN_LDO) and is fixed at 4.1V (MAX15015/MAX15016)
or 7V (MAX15014/MAX15017).
Internal Linear Regulator (REG)
REG is the output terminal of a 5V (MAX15015/
MAX15016), or 8V (MAX15014/MAX15017) LDO which
is powered from IN_SW and provides power to the IC.
Connect REG externally to DVREG to provide power for
the high-side MOSFET gate driver. Bypass REG to
SGND with a ceramic capacitor (CREG) of at least 1µF.
Place the capacitor physically close to the MAX15014–
MAX15017 to provide good bypassing. During normal
operation, REG is intended for powering up only the
internal circuitry and should not be used to supply
power to external loads.
______________________________________________________________________________________
15
MAX15014–MAX15017
IN_SW
MAX15014–MAX15017
1A, 4.5V to 40V Input Buck Converters with
50mA Auxiliary LDO Regulators
Soft-Start and Reference (SS)
SS is the 1.235V reference bypass connection for the
MAX15014–MAX15017 and also controls the soft-start
period. At startup, after input voltage is applied at IN_SW,
IN_LDO and the UVLO thresholds are reached, the
device enters soft-start. During soft-start, 14µA is sourced
into the capacitor (CSS) connected from SS to SGND
causing the reference voltage to ramp up slowly. When
VSS reaches 1.244V, the output becomes fully active. Set
the soft-start time (tSS) using following equation:
V × CSS
t SS = SS
ISS
where VSS = soft-start reference voltage = 1.235V (typ),
ISS = soft-start current = 14 x 10-6A (typ), tSS is in seconds and CSS is in Farads.
Internal Charge Pump
(MAX15015/MAX15016)
The MAX15015/MAX15016 feature an internal charge
pump to enhance the turn-on of the internal MOSFET,
allowing for operation with input voltages down to 4.5V.
Connect a flying capacitor (CF) between C+ and C-, a
boost diode from C+ to BST, as well as a bootstrap
capacitor (CBST) between BST and LX to provide the
gate drive voltage for the high-side n-channel DMOS
switch. During the on-time, the flying capacitor is
charged to VDVREG. During the off-time, the positive terminal of the flying capacitor (C+) is pumped to two times
VDVREG and charge is dumped onto CBST to provide
twice the regulator voltage across the high-side DMOS
driver. Use a ceramic capacitor of at least 0.1µF for
CBST and CF located as close as possible to the device.
Gate Drive Supply (DVREG)
DVREG is the supply input for the internal high-side
MOSFET driver. The power for DVREG is derived from
the output of the internal regulator (REG). Connect
DVREG to REG externally. To filter the switching noise,
the use of an RC filter (1Ω and 0.47µF) from REG to
DVREG is recommended. In the MAX15015/MAX15016,
the high-side drive supply is generated using the internal charge pump along with the bootstrap diode and
capacitor. In the MAX15014/MAX15017, the high-side
MOSFET driver supply is generated using only the bootstrap diode and capacitor.
Error Amplifier
The output of the internal error amplifier (COMP) is available for frequency compensation (see the Compensation
Design section). The inverting input is FB, the noninverting
input SS, and the output COMP. The error amplifier has an
16
80dB open-loop gain and a 1.8MHz GBW product. See
the Typical Operating Characteristics for the Gain and
Phase vs. Frequency graph.
Oscillator/Synchronization Input (SYNC)
With SYNC connected to SGND, the MAX15014–
MAX15017 use their internal oscillator and switch at a
fixed frequency of 135kHz and 500kHz. The MAX15014/
MAX15016 are the 135kHz options and MAX15015/
MAX15017 are the 500kHz options. For external synchronization, drive SYNC with an external clock from
400kHz to 600kHz (MAX15015/MAX15017) or 100kHz
to 200kHz (MAX15014/MAX15016). When driven with
an external clock, the device synchronizes to the rising
edge of SYNC.
PWM Comparator/Voltage Feed-Forward
An internal ramp generator clocked by the internal
oscillator is compared against the output of the error
amplifier to generate the PWM signal. The maximum
amplitude of the ramp (VRAMP) automatically adjusts to
compensate for input voltage and oscillator frequency
changes. This causes the V IN_SW / V RAMP to be a
constant 10V/V across the input voltage range of 4.5V to
40V (MAX15015/MAX15016) or 7.5V to 40V (MAX15014/
MAX15017) and the SYNC frequency range of 400kHz
to 600kHz (MAX15015/MAX15017) or 100kHz to 200kHz
(MAX15014/MAX15016).
Output Short-Circuit Protection
(Hiccup Mode)
The MAX15014–MAX15017 protect against an output
short circuit by utilizing hiccup-mode protection. In hiccup mode, a series of sequential cycle-by-cycle
current-limit events cause the part to shut down and
restart with a soft-start sequence. This allows the
device to operate with a continuous output short circuit.
During normal operation, the current is monitored at the
drain of the internal power MOSFET. When the current
limit is exceeded, the internal power MOSFET turns off
until the next on-cycle and a counter increments. If the
counter counts seven consecutive current-limit events,
the device discharges the soft-start capacitor and
shuts down for 512 clock periods before restarting with
a soft-start sequence. Each time the power MOSFET
turns on and the device does not exceed the current
limit, the counter is reset.
LDO Regulator
The LDO regulator operates over an input voltage from
5V to 40V, and can be enabled independently of the
DC-DC converter section. Its quiescent current is as
low as 47µA with a load current of 100µA. All devices
______________________________________________________________________________________
1A, 4.5V to 40V Input Buck Converters with
50mA Auxiliary LDO Regulators
RESET Output
The RESET output is typically connected to the reset
input of a microprocessor (µP). A µP’s reset input starts
or restarts the µP in a known state. The MAX15014–
MAX15017 supervisory circuits provide the reset logic
to prevent code-execution errors during power-up,
power-down, and brownout conditions. RESET
changes from high to low whenever the monitored voltage drops below the RESET threshold voltage. Once
the monitored voltage exceeds its respective RESET
threshold voltage(s), RESET remains low for the RESET
timeout period, then goes high. The RESET timeout
period is adjustable with an external capacitor (CCT)
connected to CT.
Thermal-Shutdown Protection
The MAX15014–MAX15017 feature thermal shutdown
protection which limits the total power dissipation in the
device and protects it in the event of an extended thermal fault condition. When the die temperature exceeds
+160°C, an internal thermal sensor shuts down the part,
turning off the DC-DC converter and the LDO regulator,
and allowing the IC to cool. After the die temperature
falls by 20°C, the part restarts with a soft-start sequence.
Applications Information
Setting the Output Voltage
Connect a resistive divider (R3 and R4, see Figures 6
and 7) from OUT to FB to SGND to set the output voltage. Choose R3 and R4 so that DC errors due to the FB
input bias current do not affect the output-voltage
setting precision. For the most common output-voltage
settings (3.3V or 5V), R3 values in the 10kΩ range are
adequate. Select R3 first and calculate R4 using the
following equation:
R4 =
where VFB = 1.235V.
R3
⎡ VOUT ⎤
− 1⎥
⎢
⎣ VFB
⎦
Inductor Selection
Three key inductor parameters must be specified for
operation with the MAX15014–MAX15017: inductance
value (L), peak inductor current (IPEAK), and inductor
saturation current (ISAT). The minimum required inductance is a function of operating frequency, input-to-output voltage differential, and the peak-to-peak inductor
current (∆IP-P). Higher ∆IP-P allows for a lower inductor
value while a lower ∆IP-P requires a higher inductor
value. A lower inductor value minimizes size and cost
and improves large-signal and transient response, but
reduces efficiency due to higher peak currents and
higher peak-to-peak output voltage ripple for the same
output capacitor. On the other hand, higher inductance
increases efficiency by reducing the ∆IP-P. Resistive
losses due to extra wire turns can exceed the benefit
gained from lower ∆I P-P levels especially when the
inductance is increased without also allowing for larger
inductor dimensions. A good compromise is to choose
∆IP-P equal to 40% of the full load current. Calculate the
inductor using the following equation:
(V − V
)
V
L = OUT IN OUT
VIN × fSW × ∆IP−P
VIN and VOUT are typical values so that efficiency is optimum for typical conditions. The switching frequency
(f SW ) is internally fixed at 135kHz (MAX15014/
MAX15016) or 500kHz (MAX15015/MAX15017) and
can vary when synchronized to an external clock (see
the Oscillator/Synchronization Input (SYNC) section).
The ∆IP-P, which reflects the peak-to-peak output ripple, is worst at the maximum input voltage. See the
Output-Capacitor Selection section to verify that the
worst-case output ripple is acceptable. The inductor
current (ISAT) is also important to avoid current runaway during continuous output short circuit. Select an
inductor with an I SAT specification higher than the
maximum peak current limit of 2.6A.
Input-Capacitor Selection
The discontinuous input current of the buck converter
causes large input ripple currents and therefore the
input capacitor must be carefully chosen to keep the
input voltage ripple within design requirements. The
input voltage ripple is comprised of ∆VQ (caused by
the capacitor discharge) and ∆VESR (caused by the
ESR of the input capacitor). The total voltage ripple is
the sum of ∆VQ and ∆VESR. Calculate the input capacitance and ESR required for a specified ripple using the
following equations:
______________________________________________________________________________________
17
MAX15014–MAX15017
feature a preset output voltage of 5V (MAX1501_A) or
3.3V (MAX1501_B). Alternatively, the output voltage
can be adjusted using an external resistive-divider network connected between LDO_OUT, SET_LDO, and
SGND. See Figure 5.
MAX15014–MAX15017
1A, 4.5V to 40V Input Buck Converters with
50mA Auxiliary LDO Regulators
ESR =
∆VESR
∆IP−P
2
IOUT _ MAX × D
IOUT _ MAX +
CIN =
∆VQ × fSW
where CIN is the sum of CDRAIN and additional decoupling capacitance at the buck converter input,
(V − V
) × VOUT
∆IP−P = IN OUT
and
VIN × fSW × L
V
D = OUT
VIN
IOUT_MAX is the maximum output current, D is the duty
cycle, and fSW is the switching frequency.
The MAX15014–MAX15017 include UVLO hysteresis
and soft-start to avoid chattering during turn-on.
However, use additional bulk capacitance if the input
source impedance is high. Use enough input capacitance at lower input voltages to avoid possible undershoot below the undervoltage lockout threshold during
transient loading.
Output-Capacitor Selection
The allowable output voltage ripple and the maximum
deviation of the output voltage during load steps determine the output capacitance (COUT) and its equivalent
series resistance (ESR). The output ripple is mainly
composed of ∆VQ (caused by the capacitor discharge)
and ∆VESR (caused by the voltage drop across the ESR
of the output capacitor). The equations for calculating
the peak-to-peak output voltage ripple are:
∆IP−P
8 × COUT × fSW
∆VESR = ESR × ∆IP−P
∆VQ =
Normally, a good approximation of the output voltage ripple is ∆VRIPPLE = ∆VESR + ∆VQ. If using ceramic capacitors, assume the contribution to the output voltage ripple
from ESR and the capacitor discharge to be equal to 20%
and 80%, respectively. ∆IP-P is the peak-to-peak inductor
current (see the Input-Capacitor Selection section) and
fSW is the converter’s switching frequency.
The allowable deviation of the output voltage during
fast load transients also determines the output capaci-
18
tance, its ESR, and its equivalent series inductance
(ESL). The output capacitor supplies the load current
during a load step until the controller responds with a
greater duty cycle. The response time (t RESPONSE)
depends on the closed-loop bandwidth of the converter
(see the Compensation Design section). The resistive
drop across the output capacitor’s ESR, the drop
across the capacitor’s ESL (∆VESL), and the capacitor
discharge causes a voltage droop during the loadstep.
Use a combination of low-ESR tantalum/aluminum electrolytic and ceramic capacitors for better transient load
and voltage ripple performance. Non-leaded capacitors and capacitors in parallel help reduce the ESL.
Keep the maximum output voltage deviation below the
tolerable limits of the electronics being powered. Use
the following equations to calculate the required ESR,
ESL, and capacitance value during a load step:
∆VESR
ISTEP
I
×t
COUT = STEP RESPONSE
∆VQ
∆VESL × t STEP
ESL =
ISTEP
1
tRESPONSE ≅
3ƒ C
ESR =
where ISTEP is the load step, tSTEP is the rise time of the
load step, tRESPONSE is the response time of the controller and fC is the closed-loop crossover frequency.
Compensation Design
The MAX15014–MAX15017 use a voltage-mode control
scheme that regulates the output voltage by comparing
the error amplifier output (COMP) with an internal ramp
to produce the required duty cycle. The output lowpass
LC filter creates a double pole at the resonant frequency,
which has a gain drop of -40dB/decade. The error
amplifier must compensate for this gain drop and
phase shift to achieve a stable closed-loop system.
The basic regulator loop consists of a power modulator,
an output feedback divider, and a voltage error amplifier.
The power modulator has a DC gain set by V IN /
VRAMP, with a double pole and a single zero set by the
output inductance (L), the output capacitance (COUT),
and its ESR. The power modulator incorporates a voltage
feed-forward feature, which automatically adjusts for variations in the input voltage resulting in a DC gain of 10.
______________________________________________________________________________________
1A, 4.5V to 40V Input Buck Converters with
50mA Auxiliary LDO Regulators
GMOD _ DC =
fLC =
VIN
VRAMP
1
C8
= 10
R5
C6
2 × π × L × COUT
fZESR =
1
fZI =
1
2π × R5 × C7
and
fZ2 =
1
2π × (R3 + R6) × C6
and the higher frequency poles are at:
fP2 =
and
fP3 =
1
2π × R6 × C6
1
C7 × C8
2π × R5 ×
C7 + C8
The compensation design primarily depends on the
type of output capacitor. Ceramic capacitors exhibit
very low ESR, and are well suited for high-switchingfrequency applications, but are limited in capacitance
R6
R3
VOUT
2 × π × COUT × ESR
The switching frequency is internally set at 500kHz for
MAX15015/MAX15017 and can vary from 400kHz to
600kHz when driven with an external SYNC signal. The
switching frequency is internally set at 135kHz for
MAX15014/MAX15016 and can vary from 100kHz to
200kHz when driven with an external sync signal. The
crossover frequency (fC), which is the frequency when
the closed-loop gain is equal to unity, should be set to
around 1/10 of the switching frequency or below.
The crossover frequency occurs above the LC doublepole frequency, and the error amplifier must provide a
gain and phase bump to compensate for the rapid gain
and phase loss from the LC double pole, which exhibits
little damping.
This is accomplished by utilizing a Type 3 compensator
that introduces two zeroes and three poles into the control loop. The error amplifier has a low-frequency pole
(fP1) near the origin so that tight voltage regulation at DC
can be achieved.
The two zeroes are at:
C7
EA
R4
COMP
REF
GAIN
(dB)
CLOSED-LOOP
GAIN
EA
GAIN
fZ1 fZ2
fC
fP2 fP3
FREQUENCY
Figure 3. Error Amplifier Compensation Circuit (Closed-Loop
and Error-Amplifier Gain Plot) for Ceramic Capacitors
value and tend to be more expensive. Aluminum electrolytic capacitors have much larger ESR but can reach
much larger capacitance values.
Compensation when fC < fZESR
This is usually the case when a ceramic capacitor is
selected. In this case, fZESR occurs after fC. Figure 3
shows the error amplifier feedback as well as its gain
response.
fZ1 is set to 0.5 to 0.8 x fLC and fZ2 is set to fLC to compensate for the gain and phase loss due to the double
pole. To achieve a 0dB crossover with -20dB/decade
slope, poles fP2 and fP3 are set above the crossover frequency fC.
The values for R3 and R4 are already determined in the
Setting the Output Voltage section. The value of R3 is
also used in the following calculations.
Since fZ2 < fC < fP2, then R3 >> R6, and R3 + R6 can
be approximated as R3.
Now we can calculate C6 for zero fZ2 :
C6 =
1
2π × fLC × R3
______________________________________________________________________________________
19
MAX15014–MAX15017
The following equations define the power modulator:
MAX15014–MAX15017
1A, 4.5V to 40V Input Buck Converters with
50mA Auxiliary LDO Regulators
fC occurs between fZ2 and fP2. In this region, the compensator gain (GEA) at fC is due primarily to C6 and R5.
Therefore, GEA(fC) = 2π x fC x C6 x R5 and the modulator gain at fC is:
C8
GMOD (fC ) =
R6
GMOD _ DC
(2π × fC )2 × L × COUT
R3
VOUT
Since GEA(fC) x GMOD(fC) = 1, R5 is calculated by:
EA
R4
The frequency of fZ1 is set to 0.5 x fLC and now we can
calculate C7:
1
2π × C6 × (0.5 × fSW )
Note that if the crossover frequency has been chosen
as 1/10 of the switching frequency, then fP2 = 5xfC.
The purpose of fP3 is to further attenuate the residual
switching ripple at the COMP pin.
If the ESR zero (f ZESR) occurs in a region between
fC and fSW / 2, then fP3 can be used to cancel it. This
way, the Bode plot of the loop gain plot will not flatten
out soon after the 0dB crossover, and will maintain
its -20dB/decade slope up to 1/2 of the switching
frequency.
If the ESR zero well exceeds fSW/2 (or even fSW), fP3
should in any case be set high enough not to erode the
phase margin at the crossover frequency. For example,
it can be set between 5 x fC and 10 x fC.
The value for C8 is calculated from:
C8 =
C7
(2π × C7 × R5 × fP3 − 1)
Compensation when fC > fZESR
For larger ESR capacitors such as tantalum and aluminum electrolytic, fZESR can occur before fC. If fZESR
< fC, then fC occurs between fP2 and fP3. fZ1 and fZ2
remain the same as before however, f P2 is now
set equal to fZESR. The output capacitor’s ESR zero
20
GAIN
(dB)
CLOSED-LOOP
GAIN
EA
GAIN
1
0.5 × 2π × R5 × fLC
fP2 is set at 1/2 the switching frequency (fSW). R6 is
then calculated by:
R6 =
COMP
REF
f × L × COUT × 2π
R5 = C
C6 × GMOD _ DC
C7 =
C7
R5
C6
fZ1 fZ2
fP2
fC
fP3
FREQUENCY
Figure 4. Error Amplifier Compensation Circuit (Closed-Loop
and Error-Amplifier Gain Plot) for Higher ESR Output
Capacitors
frequency is higher than fLC but lower than the closedloop crossover frequency. The equations that define
the error amplifier’s poles and zeros (fZ1, fZ2, fP2, and
fP3) are the same as before. However, fP2 is now lower
than the closed-loop crossover frequency. Figure 4
shows the error amplifier feedback as well as its gain
response for circuits that use higher-ESR output capacitors (tantalum or aluminum electrolytic).
Again, starting from R3, calculate C6 for zero fZ2:
C6 =
1
2π × fLC × R3
and then place fP2 to cancel the ESR zero. R6 is calculated as:
R6 =
COUT × ESR
C6
If the value obtained here for R6 is not considerably
smaller than R3, then recalculate C6 using (R3 + R6) in
place of R3. Then use the new value of C6 to obtain a
better approximation for R6. The process can be further
iterated, and convergence is ensured as long as fLC <
fZESR.
______________________________________________________________________________________
1A, 4.5V to 40V Input Buck Converters with
50mA Auxiliary LDO Regulators
VIN_LDO
IN_LDO
LDO_OUT
R3 × R6
fC2
R5 =
×
R3 + R6 GMOD _ DC × fLC2
C7 can still be calculated as:
R1
MAX15014–
MAX15017
SET_LDO
C7 =
1
0.5 × 2π × R5 × fLC
R2
SGND
fP3 is set at 5xfC. Therefore, C8 is calculated as:
C8 =
C7
2π × C7 × R5 × fP3 − 1
Setting the LDO Linear
Regulator Output Voltage
The MAX15014–MAX15017 LDO regulator features Dual
Mode™ operation: it can operate in either a preset voltage
mode or an adjustable mode. In preset voltage mode,
internal trimmed feedback resistors set the internal linear
regulator to 3.3V or 5V (see the Selector Guide). Select
preset voltage mode by connecting SET_LDO to ground.
In adjustable mode, select an output voltage between
1.5V and 11V using two external resistors connected as a
voltage-divider to SET_LDO (see Figure 5). Set the output
voltage using the following equation:
⎛ R1 ⎞
VOUT = VSET _ LDO ⎜1 + ⎟
⎝ R2 ⎠
where VSET_LDO = 1.241V and the recommended value
for R2 is around 50kΩ.
Setting the RESET Timeout Delay
The RESET timeout period is adjustable to accommodate a variety of µP applications. Adjust the RESET
timeout period by connecting a capacitor (C CT )
between CT and SGND.
t RP =
CCT × VCT − TH
ICT − THQ
where VCT-TH = delay comparator threshold (rising) =
1.241V (typ), ICT-THQ = CT charge current = 2 x 10-6A
(typ), tRP is in seconds and CCT is in Farads.
Figure 5. Setting the Output Voltage Using a Resistive Divider
Connect CT to LDO_OUT to select the internally fixed
timeout period. CCT must be low-leakage-type capacitor. Ceramic capacitors are recommended; do not use
capacitors lower than 200pF to avoid the influence of
parasitic capacitances.
Capacitor Selection and
Regulator Stability
For stable operation over the full temperature range and
with load currents up to 50mA, use a 10µF (min) output
capacitor (CLDO_OUT) with a maximum ESR of 0.4Ω. To
reduce noise and improve load-transient response, stability, and power-supply rejection, use larger output
capacitor values. Some ceramic dielectrics such as Z5U
and Y5V exhibit very large capacitance and ESR variation with temperature and are not recommended. With
X7R or X5R dielectrics, 15µF should be sufficient for
operation over their rated temperature range. For higherESR tantalum capacitors (up to 1Ω), use 22µF or more to
maintain stability. To improve power-supply rejection
and transient response use a minimum 0.1µF capacitor
between IN_LDO and SGND.
Power Dissipation
The MAX15014–MAX15017 are available in a thermally
enhanced package and can dissipate up to 2.86W at
T A = +70°C. When the die temperature reaches
+160°C, the part shuts down and is allowed to cool.
After the die cools by 20°C, the device restarts with a
soft-start. The power dissipated in the device is the
sum of the power dissipated in the LDO, power dissipated from supply current (PQ), transition losses due to
switching the internal power MOSFET (PSW), and the
Dual Mode is a trademark of Maxim Integrated Products, Inc.
______________________________________________________________________________________
21
MAX15014–MAX15017
The error amplifier gain between fP2 and fP3 is approximately equal to R5 / (R6 || R3).
The ESR zero frequency fZESR might not be very much
higher than the double-pole frequency fLC, therefore
the value of R5 can be calculated as:
MAX15014–MAX15017
1A, 4.5V to 40V Input Buck Converters with
50mA Auxiliary LDO Regulators
CIN_SW
CIN_LDO
R6
CDRAIN
VIN
4.5V TO 40V
R3
D1
C8
C6
IN_LDO
C7
R5
IN_SW
DRAIN
BST
COMP
CBST
FB
R4
VIN
5V TO 40V
EN_SW
L
VOUT1 AT 1A
LX
EN_SYS
COUT
D2
C+
MAX15015
MAX15016
CF
C-
RESET
SS
10kΩ
CT
VOUT2 AT 50mA
SYNC
PGND
LDO_OUT
SGND
REG
CSS
CCT
1Ω
CREG
DVREG
0.47µF
CLDO_OUT
SET_LDO
PGND
SGND
Figure 6. MAX15015/MAX15016 Typical Application Circuit (4.5V to 40V Input Operation)
power dissipated due to the RMS current through the
internal power MOSFET (PMOSFET). The total power
dissipated in the package must be limited such that the
junction temperature does not exceed its absolute maximum rating of +150°C at maximum ambient temperature. Calculate the power lost in the MAX15014–
MAX15017 using the following equations:
The power loss through the switch:
PMOSFET = (IRMS _ MOSFET )2 × RON
IRMS _ MOSFET =
D ⎡2
× I PK + (IPK × IDC ) + I2 DC ⎤⎥
⎦
3 ⎢⎣
∆I
IPK = IOUT + P−P
2
∆IP−P
IDC = IOUT −
2
VOUT
D=
VIN
22
RON is the on-resistance of the internal power MOSFET
(see the Electrical Characteristics).
The power loss due to switching the internal MOSFET:
V ×I
× (t R + t F ) × fSW
PSW = IN OUT
4
tR and tF are the rise and fall times of the internal power
MOSFET measured at LX.
The power loss due to the switching supply current (ISW):
PQ = VIN _ SW × ISW
The power loss due to the LDO regulator:
PLDO = (VIN _ LDO − VLDO _ OUT ) × ILDO _ OUT
The total power dissipated in the device will be:
PTOTAL = PMOSFET + PSW + PQ + PLDO
______________________________________________________________________________________
1A, 4.5V to 40V Input Buck Converters with
50mA Auxiliary LDO Regulators
CDRAIN
VIN
7.5V TO 40V
R3
MAX15014–MAX15017
CIN_SW
CIN_LDO
R6
D1
C8
C6
R5
IN_LDO
C7
IN_SW
DRAIN
BST
COMP
CBST
FB
R4
VIN
7.5V TO 40V
EN_SW
L
VOUT1 AT 1A
LX
EN_SYS
COUT
D2
MAX15014
MAX15017
RESET
SS
10kΩ
CT
VOUT2 AT 50mA
SYNC
PGND
LDO_OUT
SGND
REG
CSS
CCT
1Ω
CREG
DVREG
0.47µF
CLDO_OUT
SET_LDO
PGND
SGND
Figure 7. MAX15014/MAX15017 Typical Application Circuit (7.5V to 40V Input-Voltage Operation)
______________________________________________________________________________________
23
1A, 4.5V to 40V Input Buck Converters with
50mA Auxiliary LDO Regulators
28 C+ (I.C.)
29 SYNC
30 N.C.
31 COMP
32 FB
33 SS
34 REG
27
N.C.
26
N.C.
3
25
DVREG
4
24
N.C.
5
23
C- (I.C.)
22
PGND
21
DRAIN
20
DRAIN
19
N.C.
+
MAX15014–MAX15017
6
7
8
EP*
10
11
12
13
14
15
16
17
18
N.C.
IN_LDO
N.C.
BST
N.C.
LX
LX
9
( ) MAX15014/MAX15017
*EP = EXPOSED PAD.
Chip Information
PROCESS: BiCMOS/DMOS
2
1
SET_LDO
N.C.
N.C.
N.C.
RESET
SGND
CT
EN_SW
EN_SYS
N.C.
35 N.C.
36 IN_SW
TOP VIEW
LDO_OUT
MAX15014–MAX15017
Pin Configuration
TQFN
Selector Guide
LDO OUTPUT
SWITCHING
FREQUENCY (kHz)
DC-DC MINIMUM
INPUT VOLTAGE (V)
CHARGE
PUMP
MAX15014A
135
7.5
MAX15014B
135
7.5
MAX15015A
500
4.5
MAX15015B
500
4.5
MAX15016A
135
4.5
MAX15016B
135
MAX15017A
500
MAX15017B
500
PART
24
5V
3.3V
ADJUSTABLE
OUTPUT
—
X
—
X
—
—
X
X
X
X
—
X
X
—
X
X
X
X
—
X
4.5
X
—
X
X
7.5
—
X
—
X
7.5
—
—
X
X
______________________________________________________________________________________
1A, 4.5V to 40V Input Buck Converters with
50mA Auxiliary LDO Regulators
QFN THIN.EPS
______________________________________________________________________________________
25
MAX15014–MAX15017
Package Information
(The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information
go to www.maxim-ic.com/packages.)
MAX15014–MAX15017
1A, 4.5V to 40V Input Buck Converters with
50mA Auxiliary LDO Regulators
Package Information (continued)
(The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information
go to www.maxim-ic.com/packages.)
Maxim cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a Maxim product. No circuit patent licenses are
implied. Maxim reserves the right to change the circuitry and specifications without notice at any time.
26 ____________________Maxim Integrated Products, 120 San Gabriel Drive, Sunnyvale, CA 94086 408-737-7600
© 2007 Maxim Integrated Products
is a registered trademark of Maxim Integrated Products, Inc.
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