datasheet for PA78EU by Apex Microtechnology

datasheet for PA78EU by Apex Microtechnology
PA78
PA78
PA78
Power Operational Amplifier
FEATURES
DESCRIPTION
The PA78 is a high voltage, high speed, low idle current op-amp capable of delivering up to 200mA peak
output current. Due to the dynamic biasing of the input
stage, it can achieve slew rates over 350V/µs, while
only consuming less than 1mA of idle current. External
phase compensation allows great lexibility for the user
to optimize bandwidth and stability.
The output stage is protected with user selected current limit resistor. For the selection of this current limiting resistor, pay close attention to the SOA curves for
each package type. Proper heatsinking is required for
maximum reliability.
A Unique (Patent Pending) Technique for Very
Low Quiescent Current
Over 350 V/µs Slew Rate
Wide Supply Voltage
Single Supply: 20V To 350V
Split Supplies: ± 10V To ± 175V
Output Current – 150mA Cont.; 200mA Pk
Up to 23 Watt Dissipation Capability
Over 200 kHz Power Bandwidth
APPLICATIONS
Piezoelectric Positioning and Actuation
Electrostatic Delection
Deformable Mirror Actuators
Chemical and Biological Stimulators
BLOCK DIAGRAM
ACTIVE LOAD
VOUT+
BUFFER
V+
V–
CLASS AB INPUT STAGE
ACTIVE LOAD
VOUT–
CURRENT
LIMIT
VOUT
20–Pin PSOP
PACKAGE STYLE DK
www.apexanalog.com
PA78U
Copyright © Apex Microtechnology, Inc. 2012
(All Rights Reserved)
OCT 2012
1
PA78U REVE
PA78
CHARACTERISTICS AND SPECIFICATIONS
ABSOLUTE MAXIMUM RATINGS
Max
Units
SUPPLY VOLTAGE, +VS to −VS
Parameter
Symbol
Min
350
V
OUTPUT CURRENT, peak (200ms), within SOA
200
mA
14
W
16
V
POWER DISSIPATION, internal, DC
INPUT VOLTAGE, differential
−15
INPUT VOLTAGE, common mode
−VS
TEMPERATURE, junction
(Note 2)
+VS
V
150
°C
TEMPERATURE RANGE, storage
−55
125
°C
OPERATING TEMPERATURE, case
−40
125
°C
SPECIFICATIONS
Parameter
Test Conditions
Min
Typ
Max
Units
-40
8
40
mV
INPUT
OFFSET VOLTAGE
OFFSET VOLTAGE vs. temperature
0 to 125°C (Case Temperature)
-63
OFFSET VOLTAGE vs. supply
µV/°C
32
µV/V
8.5
200
pA
OFFSET CURRENT, initial
12
400
pA
INPUT RESISTANCE, DC
108
Ω
+VS - 2
V
BIAS CURRENT, initial
COMMON MODE VOLTAGE RANGE, pos.
COMMON MODE VOLTAGE RANGE, neg.
COMMON MODE REJECTION, DC
NOISE
90
700KHz
NOISE, VO NOISE
-VS + 5.5
V
118
dB
418
µV RMS
500
nV/√Hz
120
dB
GAIN
OPEN LOOP @ 1Hz
89
GAIN BANDWIDTH PRODUCT @ 1MHz
PHASE MARGIN
1
Full temperature range
50
MHz
º
OUTPUT
VOLTAGE SWING
IO = 10mA
|VS| - 2
VOLTAGE SWING
IO = 100mA
|VS| - 8.6
VOLTAGE SWING
IO = 150mA
CURRENT, continuous, DC
SLEW RATE
V
|VS| - 12
|VS| - 10
V
150
Package Tab connected to GND
100
V
mA
350
V/µS
SETTLING TIME, to 0.1%
2V Step
1
µS
POWER BANDWIDTH, 300VP-P
+VS = 160V, −VS = -160V
200
kHz
OUTPUT RESISTANCE, No load
RCL = 6.2
44
POWER SUPPLY
VOLTAGE
CURRENT, quiescent
2
(Note 5) ±150V Supply
±10
±150
±175
V
0.2
0.7
2.5
mA
PA78U
PA78
Parameter
Test Conditions
Min
Typ
Max
Units
8.3
9.1
ºC/W
THERMAL
RESISTANCE, DC, junction to case
Full temperature range
RESISTANCE, DC, junction to air (Note 6) Full temperature range
25
ºC/W
RESISTANCE, DC, junction to air (Note 7) Full temperature range
19.1
ºC/W
TEMPERATURE RANGE, case
-40
125
ºC
NOTES: 1. Unless otherwise noted: TC = 25°C, DC input speciications are ± value given, power supply voltage
is typical rating.
2. Long term operation at the maximum junction temperature will result in reduced product life. Derate
power dissipation to achieve high MTTF.
3. +VS and –VS denote the positive and negative supply voltages of the output stage.
4. Rating applies if output current alternates between both output transistors at a rate faster than 60Hz.
5. Supply current increases with signal frequency. See graph on page 4.
6. Rating applies when the heatslug of the DK package is soldered to a minimum of 1 square inch foil
area of a printed circuit board.
7. Rating applies with the JEDEC conditions outlined in the Heatsinksing section of this datasheet.
EXTERNAL CONNECTIONS
RC-
CC-IN
1
+IN
–
+
20
CC–
RC+ C +
R
OUTPUT
RLIM
IL
CC+
+VS
PA78DK
20 PIN PSOP
10
PA78U
CS
VOUT
CR–
CC+
-VS
RBIAS
11
3
PA78
TYPICAL APPLICATION CIRCUIT
+335V
CC
16
4
1
5
1.6K
2
RBIAS
20
CURRENT LIMIT, ILIM (mA)
CS
200
150
100
50
NO COMPENSATION
80
60
+VS
40
20
10K
+VS
40
–VS
50
RESISTOR VALUE (Ω)
100
OUTPUT VOLTAGE SWING
VOLTAGE DROP FROM SUPPLY (V)
POWER SUPPLY REJECTION (dB)
-VS
80
1K
FREQUENCY, (Hz)
-15V
100
POWER SUPPLY REJECTION
0
100
RC
120
0
0
1000
100
60
CC
140
20
12
10
DEFLECTION
PLATE
INK
DROPLETS
-VS SIDE DROP
8
6
+VS SIDE DROP
4
2
0
0
50
100
150
200
PEAK TO PEAK LOAD CURRENT (mA)
POWER DERATING
25
20
PA
78
15
EU
PA
78
DK
10
5
0
0
25
50
75
100 125
CASE TEMPERATURE, TC (°C)
COMMON MODE REJECTION
COMMON MODE REJECTION (dB)
OUTPUT VOLTAGE, (V)
GAIN = -100
100
10
FREQUENCY, (KHz)
19
160
GAIN = -50
300
0
1
3
CURRENT LIMIT
POWER RESPONSE
250
RCL
17
18
0-5V
DAC
TYPICAL PERFORMANCE GRAPHS
350
100K
RC
INTERNAL POWER DISSIPATION, P (W)
The PA78 is ideally suited for driving continuous
drop ink jet printers, in both piezo actuation and
delection applications. The high voltage of the ampliier creates an electrostatic ield on the delection plates to control the position of the ink droplets. The rate at which droplets can be printed is
directly related to the rate at which the ampliier
can drive the plate to a different electrostatic ield
strength.
140
120
100
80
60
40
20
0
1
10
100
1K
10K 100K
FREQUENCY (Hz)
PA78DK SOA
1
S
C
0m
S 5°
20
2
0m =
°C
85
=
30
C
,T
C
,T
D
C
0.1
D
C
CURRENT, AMPS (A)
PULSE CURVES
@ 10% DUTY CYCLE MAX
0.01
10
100
1000
SUPPLY TO OUTPUT DIFFERENTIAL, VS - VO (V)
4
PA78U
PA78
SMALL SIGNAL OPEN LOOP GAIN
100
RC = OPEN, CC = 0pF
RC = 3.3K, CC = 1pF
RC = 3.3K, CC = 2.2pF
60
RC = 3.3K, CC = 5pF
40
CS = 68pF
PIN = -40dBm
RBIAS = OPEN
RS = 48.7Ω
VS = ±50V
20
0
-20
1
RC = 3.3K, CC = 10pF
RC = 3.3K, CC = 22pF
10
100
FREQUENCY, KHz
SMALL SIGNAL OPEN LOOP PHASE, VO = 250mVP-P
180
RC = 3.3K, CC = 22pF
150
RC = 3.3K, CC = 10pF
120
PHASE, °
1000
60
0 CS = 68pF
-30 PIN = -40dBm
R
= OPEN
-60 RBIAS
= 48.7Ω
S
-90
1
RC = 3.3K, CC = 5pF
RC = 3.3K, CC = 2.2pF
RC = 3.3K, CC = 1pF
RC = OPEN, CC = 0pF
10
100
FREQUENCY, KHz
1000
GAIN vs. INPUT/OUTPUT SIGNAL LEVEL
45
30
CS = 68pF
0 PIN = -40dBm
-30 RBIAS = 100K
R = 48.7Ω
-60 V S = ±50V
S
-90
1
RC = 3.3K, CC = 5pF
RC = 3.3K, CC = 2.2pF
RC = 3.3K, CC = 1pF
RC = OPEN, CC = 0pF
10
100
FREQUENCY, KHz
15
A V = +51
RBIAS = 100K
RC = OPEN
RF = 75K
RG = 1.5K
RL = 50K
VS = ±50V
5
-5
-15
10
5 VP-P
SMALL SIGNAL GAIN vs. COMPENSATION, VO = 5VP-P
CC = 0pF
50 VP-P
100
1K
FREQUENCY, KHz
-35
10K
35
-5
-15
-25
A V = +26
RBIAS = 100K
RC = 3.3K
RF = 35.7K
RG = 1.5K
RL = 50K
VS = ±50V
-35
10
PA78U
CC = 5pF
CC = 10pF
CC = 22pF
100
1K
FREQUENCY, KHz
10K
LARGE SIGNAL GAIN vs. COMPENSATION, VO = 50VP-P
CC = 0pF
15
CC = 1pF
GAIN,dB
5
10
CC = 2.2pF
25
25
15
A V = +26
RBIAS = 100K
RF = 35.7K
RG = 1.5K
RL = 50K
VS = ±50V
-5
-25
CC = 0pF
35
CC = 1pF
5
-15
SMALL SIGNAL GAIN vs. COMPENSATION, VO = 500mVP-P
45
1000
15
500 mVP-P
GAIN,dB
GAIN, dB
60
25
25
GAIN,dB
RC = 3.3K, CC = 10pF
90
35
35
-25
RC = 3.3K, CC = 22pF
150
120
90
30
SMALL SIGNAL OPEN LOOP PHASE
180
PHASE, °
GAIN, Db
80
CC = 2.2pF
CC = 5pF
-25
CC = 22pF
100
1K
FREQUENCY, KHz
-5
-15
CC = 10pF
10K
CC = 1pF
5
-35
10
A V = +26
RBIAS = 100K
RF = 35.7K
RG = 1.5K
RL = 50K
VS = ±50V
CC = 2.2pF
CC = 5pF
CC = 10pF
CC = 22pF
100
1K
FREQUENCY, KHz
10K
5
SR+
SR, V/µs
600
A V = +101
CL = 8pF
RF = 25K
RG = 250Ω
RL = 50K
VS = ±150V
400
200
0
2
4
6
8
10
12
PEAK-TO-PEAK INPUT VOLTAGE
14
SR+/SR- (25% -75%)
1000
OUTPUT VOLTAGE, V
SRSR, V/µs
600
A V = +51
CL = 8pF
RF = 75K
RG = 1.5K
RL = 50K
VS = ±150V
400
200
0
2
4
6
8
10
12
PEAK-TO-PEAK INPUT VOLTAGE
14
SR+/SR- (25% - 75%)
1000
A V = +26
C = 8pF
800 RL = 35.6K
F
RG = 1.5K
R
= 50K
600
L
VS = ±150V
SR, V/µs
SR+
SR-
-2
0
2
4
TIME, µs
6
8
10
TRANSIENT RESPONSE
1.5
A V = +26
CC = 2.2pF 1
CL = 8pF
RC = 3.3K 0.5
RF = 35.7K
RG = 1.5K 0
RL = 50K
2VP-P
20
input2
10
-1.2
12
0
-10
-0.5
-20
-1
-2
0
2
4
TIME, µs
6
8
-1.5
12
10
TRANSIENT RESPONSE
10VP-P
input10
50
8
A V = +26
CC = 2.2pF
CL = 8pF
RC = 3.3K
RF = 35.7K
RG = 1.5K
RL = 50K
0
6
4
2
0
-2
-50
-4
2
4
6
8
10
12
PEAK-TO-PEAK INPUT VOLTAGE
14
16
RISE AND FALL TIME (10% - 90%)
0.6
TF
0.4
A V = +51
CL = 8pF
RF = 75K
RG = 1.5K
RL = 50K
VS = ±150V
TR
2
4
6
8
10
12
PEAK-TO-PEAK INPUT VOLTAGE
-2
0
2
4
6
TIME, µs
8
10
-8
12
PULSE RESPONSE vs. CC AND RC
0.2
0
-150
-4
-6
14
16
150
Out - 0pF
120 input
90
60
Out - 1pF & 3.3K
30
0
-30
-60
Out - 5pF & 3.3K
-90
-120
-150
-2
-1
0
1
2
3
4
TIME, µs
A V = +51
CC = 68pF
CL = 330pF
RC = 48Ω
RF = 75K
RG = 1.5K
RL = OPEN
VS = ±150V
5
6
7
3.0
2.4
1.8
1.2
0.6
0
-0.6
-1.2
-1.8
-2.4
-3.0
INPUT VOLTAGE, V
0
0.8
Time, µs
-0.8
-100
1
6
-10
150
200
0
-0.4
100
400
0
-5
-30
-4
16
OUTPUT VOLTAGE, V
0
input1
0
30
SR+
800
5
-15
-4
16
1VP-P
OUTPUT VOLTAGE, V
0
10
1.2
A V = +26
CC = 2.2pF 0.8
CL = 8pF
RC = 3.3K 0.4
RF = 35.7K
RG = 1.5K 0
RL = 50K
INPUT VOLTAGE, V
OUTPUT VOLTAGE, V
SR-
800
TRANSIENT RESPONSE
15
INPUT VOLTAGE, V
SR+/SR- (25% - 75%)
1000
INPUT VOLTAGE, V
PA78
8
PA78U
PA78
PULSE RESPONSE vs. CAP LOAD
300pf, 3VP-P
200pf, 3VP-P
100pf, 3VP-P
0.1
0.05
A V = -50
RF = 75K
RG = 1.5K
RL = 50K
VS = ±150V
4
6
8 10 12 14 16 18 20 22 24 26 28 30
TIME, µs
-0.05
-1
A V = -50
RF = 75K
RG = 1.5K
RL = 50K
VS = ±150V
CL = 8pF
2
4
6
100
0
-100
8 10 12 14 16 18 20 22 24 26 28 30
TIME, µs
-4
6
INPUT
4
OUTPUT
2
0
-2
-2
0
2
4
TIME, µs
6
8
10
-6
12
7
8
9
IS vs. VIN
18
A V = +51
CL = 8pF
CS = 68pF
RF = 75K
RG = 1.5K
RL = 50K
RS = 48.7Ω
VS = ±150V
16
14
10
8
6
4
2
0
8 10 12 14 16 18 20 22 24 26 28 30
TIME, µs
0
30
25
IS, mA
20
15
10
5
0
10
PA78U
6
5
-4
-300
-6
IS, mA
OUTPUT, V
A V = -50
RF = 75K
RG = 1.5K
RL = 50K
VS = ±150V
6
4
-200
12
4
2
3
TIME,µs
A V = +51
CC = OPEN
CL = 8pF
RC = OPEN
RF = 75K
RG = 1.5K
RL = 50K
VS = ±150V
200
300pF, 1VP-P
200pF, 1VP-P
100pF, 1VP-P
2
1
OVERDRIVE RECOVERY
300
OUTPUT VOLTAGE, V
OUTPUT, V
300pF, 2VP-P
200pF, 2VP-P
100pF, 2VP-P
0
INPUT VOLTAGE, V
2
0
PULSE RESPONSE vs. CAP LOAD
140
120
100
80
60
40
20
0
-20
-40
-60
-80
-6 -4 -2 0
A V = +51
CL = 8pF
RF = 75K
RG = 1.5K
RL = 50K
VS = ±150V
0.15
PULSE RESPONSE vs. CAP LOAD
140
120
100
80
60
40
20
0
-20
-40
-60
-80
-6 -4 -2 0
PULSE RESPONSE
0.2
IS, A
OUTPUT, V
140
120
100
80
60
40
20
0
-20
-40
-60
-80
-6 -4 -2 0
1
2
3
4
5
6
VIN, VP-P (100KHz sine wave)
SUPPLY CURRENT vs. FREQUENCY
A V = +51
CL = 8pF
CS = 68pF
RF = 75K
RG = 1.5K
RL = 50K
RS = 48.7Ω
VS = ±150V
VIN = 6VP
VIN = 3VP
100
Frequency, (KHz sine wave)
1000
7
PA78
Please read Application note 1 “General operating
considerations” which covers stability, power supplies, heat sinking, mounting, current limit, SOA interpretation, and speciication interpretation. Visit www.
apexanalog.com for design tools that help automate
tasks such as calculations for stability, internal power
dissipation, and current limit. There you will also ind
a complete application notes library, technical seminar workbook, and evaluation kits.
RF = 75K
1000 RG = 1.5K
RL = 50K
800 VS = ±150V
CL = 8pF
SR+(A V = -25)
SR-(A V = -25)
SR+(A V = +26)
SR-(A V = +26)
600
400
200
0
THEORY OF OPERATION
0
1
2
3
4 5 6 7 8 9 10 11 12 13 14 15
PEAK TO PEAK INPUT VOLTAGE
SR+/SR- (25%-75%)
1600
R = 75K
1400 RF = 1.5K
G
1200 RL = 50K
VS = ±150V
1000 C = 8pF
L
V/µs
The PA78 is designed speciically as a high speed
pulse ampliier. In order to achieve high slew rates
with low idle current, the internal design is quite different from traditional voltage feedback ampliiers.
Basic op amp behaviors like high input impedance
and high open loop gain still apply. But there are
some notable differences, such as signal dependent
supply current, bandwidth and output impedance,
among others. The impact of these differences varies depending on application performance requirements and circumstances. These different behaviors
are ideal for some applications but can make designs
more challenging in other circumstances.
SR+/SR- (25%-75%)
1200
SR+/SR- V/µs
GENERAL
800
600
SR+(A V = -50)
SR-(A V = -50)
SR+(A V = +51)
SR-(A V = +51)
400
200
0
0
1
2
3 4 5 6 7 8 9 10 11 12 13 14 15
INPUT VOLTAGE, VOLTS PEAK-TO-PEAK
SUPPLY CURRENT AND BYPASS CAPACITANCE
A traditional voltage feedback ampliier relies on ixed current sources in each stage to drive the parasitic capacitances of the next stage. These currents combine to deine the idle or quiescent current of the ampliier. By design,
these ixed currents are often the limiting parameter for slew rate and bandwidth of the ampliier. Ampliiers which
are high voltage and have fast slew rates typically have high idle currents and dissipate notable power with no signal applied to the load. At the heart of the PA78 design is a signal dependent current source which strikes a new
balance between supply current and dynamic performance. With small input signals, the supply current of the PA78
is very low, idling at less than 1 mA. With large transient input signals, the supply currents increase dramatically to
allow the ampliier stages to respond quickly. The Pulse Response plot in the typical performance section of this
datasheet describes the dynamic nature of the supply current with various input transients.
Choosing proper bypass capacitance requires careful consideration of the dynamic supply currents. High frequency
ceramic capacitors of 0.1µF or more should be placed as close as possible to the ampliier supply pins. The inductance of the routing from the supply pins to these ceramic capacitors will limit the supply of peak current during
transients, thus reducing the slew rate of the PA78. The high frequency capacitance should be supplemented by
additional bypass capacitance not more than a few centimeters from the ampliier. This additional bypass can be
a slower capacitor technology, such as electrolytic, and is necessary to keep the supplies stable during sustained
output currents. Generally, a few microfarad is suficient.
SMALL SIGNAL PERFORMANCE
The small signal performance plots in the typical performance section of this datasheet describe the behavior when
the dynamic current sources described previously are near the idle state. The selection of compensation capacitor
directly affects the open loop gain and phase performance.
Depending on the coniguration of the ampliier, these plots show that the phase margin can diminish to very low
levels when left uncompensated. This is due to the amount of bias current in the input stage when the part is in
standby. An increase in the idle current in the output stage of the ampliier will improve phase margin for small
signals although will increase the overall supply current.
Current can be injected into the output stage by adding a resistor, RBIAS, between CC- and VS+. The size of RBIAS
8
PA78U
PA78
will depend upon the application but 500µA (50V V+ supply/100K) of added bias current shows signiicant improvement in the small signal phase plots. Adding this resistor has little to no impact on small signal gain or large signal
performance as under these conditions the current in the input stage is elevated over its idle value. It should also
be noted that connecting a resistor to the upper supply only injects a ixed current and if the upper supply is ixed
and well bypassed. If the application includes variable or adjustable supplies, a current source diode could also be
used. These two terminal components combine a JFET and resistor connected within the package to behave like
a current source.
As a second stability measure, the PA78 is externally compensated and performance can be optimized to the application. Unlike the RBIAS technique, external phase compensation maintains the low idle current but does affect
the large signal response of the ampliier. Refer to the small and large signal response plots as a guide in making
the tradeoffs between bandwidth and stability. Due to the unique design of the PA78, two symmetric compensation
networks are required. The compensation capacitor Cc must be rated for a working voltage of the full operating
supply voltage (+VS to –VS). NPO capacitors are recommended to maintain the desired level of compensation over
temperature.
The PA78 requires an external 33pF capacitor between CC- and –VS to prevent oscillations in the falling edge of the
output. This capacitor should be rated for the full supply voltage (+VS to –VS).
LARGE SIGNAL PERFORMANCE
As the amplitude of the input signal increases, the internal dynamic current sources increase the operation bandwidth of the ampliier. This unique performance is apparent in its slew rate, pulse response, and large signal performance plots. Recall the previous discussion about the relationships between signal amplitude, supply current, and
slew rate. As the amplitude of the input amplitude increases from 1VP-P to 15VP-P, the slew rate increases from 50V/
µs to well over 350V/µs.
Notice the knee in the Rise and Fall times plot, at approximately 6VP-P input voltage. Beyond this point the output
becomes clipped by the supply rails and the ampliier is no longer operating in a closed loop fashion. The rise and
fall times become faster as the dynamic current sources are providing maximum current for slewing. The result of
this ampliier architecture is that it slews fast, but allows good control of overshoot for large input signals. This can
be seen clearly in the large signal Transient Response plots.
HEATSINKING AND SAFE OPERATING AREA
The MOSFET output stage of the PA78 is not limited by second breakdown considerations as in bipolar output
stages. Only thermal considerations of the package and current handling capabilities limit the Safe Operating Area.
The SOA plots include power dissipation limitations which are dependent upon case temperature. Keep in mind
that the dynamic current sources which drive high slew rates can increase the operating temperature of the ampliier during periods of repeated slewing. The plot of supply current vs. input signal amplitude for a 100 kHz signal
provides an indication of the supply current with repeated slewing conditions. This application dependent condition
must be considered carefully.
The output stage is self-protected against transient lyback by the parasitic body diodes of the output stage. However, for protection against sustained high energy lyback, external, fast recovery diodes must be used.
CURRENT LIMIT
For proper operation, the current limit resistor, RLIM, must be connected as shown in the external connections
diagram. For maximum reliability and protection, the largest resistor value should be used. The minimum practical value for RLIM is about 12 . However, refer to the SOA curves for each package type to assist in selecting the
optimum value for RLIM in the intended application. Current limit may not protect against short circuit conditions with
supply voltages over 200V.
LAYOUT CONSIDERATIONS
The PA78 is built on a dielectrically isolated process and the package tab is therefore not electrically connected
to the ampliier. For high speed operation, the package tab should be connected to a stable reference to reduce
capacitive coupling between ampliier nodes and the loating tab. It is often convenient to directly connect the tab
to GND or one of the supply rails, but an AC connection through a 1µF capacitor to GND is also suficient if a DC
connection is undesirable
PA78U
9
PA78
Care should be taken to position the RC / CC compensation networks close to the ampliier compensation pins. Long
loops in these paths pick up noise and increase the likelihood of LC interactions and oscillations.
The PA78DK package has a large exposed integrated copper heatslug to which the monolithic ampliier is directly
attached. The solder connection of the heat slug to a 1 square inch foil area on the printed circuit board will result
in improved thermal performance of 25ºC/W. In order to improve the thermal performance, multiple metal layers in
the printed circuit board are recommended. This may be adequate heatsinking but the large number of variables
involved suggest temperature measurements be made on the top of the package. Do not allow the temperature to
exceed 85ºC.
The junction to ambient thermal resistance of the DK package can achieve a 19.1ºC/W rating by using the PCB
conditions outlined in JEDEC standard: (JESD51–5):
PCB Conditions:
PCB Layers = 4L, Copper, FR–4
PCB Dimensions = 101.6 x 114.3mm
PCB Thickness = 1.6mm
Conditions:
Power dissipation = 2 watt
Ambient Temperature = 55ºC
ELECTROSTATIC DISCHARGE
Like many high performance MOSFET ampliiers, the PA78 very sensitive to damage due to electrostatic discharge
(ESD). Failure to follow proper ESD handling procedures could have results ranging from reduced operating performance to catastrophic damage. Minimum proper handling includes the use of grounded wrist or shoe straps,
grounded work surfaces. Ionizers directed at the work in progress can neutralize the charge build up in the work
environment and are strongly recommended.
NEED TECHNICAL HELP? CONTACT APEX SUPPORT!
For all Apex Microtechnology product questions and inquiries, call toll free 800-546-2739 in North America.
For inquiries via email, please contact [email protected]
International customers can also request support by contacting their local Apex Microtechnology Sales Representative.
To ind the one nearest to you, go to www.apexanalog.com
IMPORTANT NOTICE
Apex Microtechnology, Inc. has made every effort to insure the accuracy of the content contained in this document. However, the information is subject to change
without notice and is provided "AS IS" without warranty of any kind (expressed or implied). Apex Microtechnology reserves the right to make changes without further
notice to any speciications or products mentioned herein to improve reliability. This document is the property of Apex Microtechnology and by furnishing this information, Apex Microtechnology grants no license, expressed or implied under any patents, mask work rights, copyrights, trademarks, trade secrets or other intellectual
property rights. Apex Microtechnology owns the copyrights associated with the information contained herein and gives consent for copies to be made of the information only for use within your organization with respect to Apex Microtechnology integrated circuits or other products of Apex Microtechnology. This consent does not
extend to other copying such as copying for general distribution, advertising or promotional purposes, or for creating any work for resale.
APEX MICROTECHNOLOGY PRODUCTS ARE NOT DESIGNED, AUTHORIZED OR WARRANTED TO BE SUITABLE FOR USE IN PRODUCTS USED FOR
LIFE SUPPORT, AUTOMOTIVE SAFETY, SECURITY DEVICES, OR OTHER CRITICAL APPLICATIONS. PRODUCTS IN SUCH APPLICATIONS ARE UNDERSTOOD TO BE FULLY AT THE CUSTOMER OR THE CUSTOMER’S RISK.
Apex Microtechnology, Apex and Apex Precision Power are trademarks of Apex Microtechnolgy, Inc. All other corporate names noted herein may be trademarks
of their respective holders.
10
www.apexanalog.com
Copyright © Apex Microtechnology, Inc. 2012
(All Rights Reserved)
OCTPA78U
2012
PA78U REVE
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