1EZ51E
Products: R&S ZVM, R&S ZVK
Measurement Method for Determining
the Equivalent Reflection Coefficient of
Directional Couplers and Power Splitters
A measurement method presented by John R. Juroshek (NIST) in conjunction with the Vector Network
Analyzers R&S ZVM or R&S ZVK from Rohde & Schwarz allows fast and accurate determination of the
equivalent reflection coefficient of power splitters or directional couplers. If the magnitude and phase of
reflection coefficients of source (e.g. power splitter) and sink (e.g. power meter) are known, a mathematical
correction of the measurement error caused by mismatch is possible. This measurement uncertainty
content can thus normally be reduced by one order of magnitude, which is beneficial during the calibration
of power meters, for example.
Subject to change – Harald Jäger 08.02 – 1EZ51_1E
Determination of equivalent reflection coefficient
Contents
1
2
3
4
Overview ................................................................................................. 2
Description of Measurement Method...................................................... 4
Further Measuring Methods in Brief ....................................................... 6
Practical Implementation of Measurement Method using Vector
Network Analyzer R&S ZVM or R&S ZVK .............................................. 8
5 Measurement Uncertainty..................................................................... 12
6 Experimental Results Check – Comparison with Other Measurement
Methods ................................................................................................ 14
7 Special Technical Features................................................................... 18
8 Summary............................................................................................... 18
9 References............................................................................................ 19
10 Further Application Notes ..................................................................... 20
11 Ordering Information ............................................................................. 21
1 Overview
Resistive power splitters or directional couplers are frequently used for the
calibration of power meters. An example is provided in the following figure.
A
3
D
E
1
ΓB
Γeq,2
B
2
C
ΓC
Γeq,2
Fig. 1 Calibration of power meter
With
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A
Incident Power Detector
B
Reference | Transfer Standard
C
Device under Test | Calibration Item
D
Source | Signal Generator
E
Directional Coupler or Power-Splitter
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The measurement uncertainty occurring during the calibration of the
calibration item mainly consists of two components:
1
the calibration uncertainty of the reference standard,
2
the uncertainty caused by mismatch of
a)
power splitter or directional coupler <> reference standard
b)
power splitter or directional coupler <> calibration item.
If, for example, a power sensor with the reflection coefficient ΓC is
calibrated according to a setup described in Fig. 1, the incident power will
deviate by the following factor as compared to the measurement using the
reference standard with the reflection coefficient ΓB :
1 1 − Γeq ΓB
=
Q 1− Γ Γ
eq C
2
2
[7]
If values of 0.13 are assumed for the magnitudes of all three reflection
coefficients, which is quite realistic in the frequency range up to 40 GHz, Q
can be in the range from 0.93 to 1.07.
In general, such deviations (max. 7%) cannot be tolerated for the
calibration of power meters.
It should be noted that this uncertainty content is only caused by mismatch
and that it is purely systematic.
The calibration uncertainty of the reference standard can only be reduced
by choosing a calibration laboratory accredited for a lower measurement
uncertainty. The calibration uncertainty during the recalibration of the
reference power meter is thus principally limited by national and
international institutions (PTB, NIST, etc.).
However, the user can directly influence measurement uncertainty caused
by mismatch by doing either of the following:
•
Using a power splitter with a low equivalent source match (what is
generally recommended).
•
Correcting the measured values mathematically. The mathematical
correction of measured values is also called Γ correction. The true
value of the incident power can quite accurately be determined (i.e. the
incident power can be determined with a much smaller measurement
uncertainty) by means of this method.
If the vector Γ correction is to be performed in the broadband and at a large
number of frequency points, some methods for determining the equivalent
reflection coefficient of a power splitter are not suitable for use in practice.
This is due to the fact that a lot of time would be required for the calibration
of a power splitter. And it is also due to the fact that various methods are
limited to certain discrete frequency points.
Methods based on vector network analyzers are suitable for use since the
alignment of the DUT regarding magnitude and phase must be measured
with a vector network analyzer, i.e. this measuring instrument and the
corresponding accessories are always required anyway.
The method proposed by John R. Juroshek in conjunction with a Vector
Network Analyzer R&S ZVM or R&S ZVK from Rohde & Schwarz can be
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used to determine the equivalent reflection coefficient of a power splitter in
complex form and at up to 2001 frequency points within only a few minutes.
The time required to determine the equivalent reflection coefficient of a
power splitter port corresponds to a full two-port calibration of a network
analyzer.
2 Description of Measurement Method
Vector network analysis is based on the idea that errors of this kind of
measuring instruments and/or of the complete test setup can be
determined and therefore corrected. However, only time-invariant,
systematic and linear influences can be eliminated. The errors of the vector
network analyzer are determined by measuring different well known
calibration standards to the test port (or the test ports). A set of correction
values is calculated based on these measurements. This set is used to
correct the "raw measured values" measured at a later time.
The most widely known method for one-port calibration is the OSM method
(Open Short Match).
These three standards are connected one after the other to the test port
(reference plane) and the relations occurring for wave-quantities a1 to b1
are determined.
The behaviour of the individual standards is assumed to be known. The
corresponding descriptive models are stored in the vector network
analyzer.
Based on the three relations obtained, the three unknown quantities, i.e.
the three characteristic system data items source match, directivity and
reflection tracking, can be calculated using the following formula:
Γ=
ΓM − e00
[1]
e11 (ΓM − e00 ) + e01
where
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Γ=
measured value after the correction, which is defined by the
models of the calibration standards
ΓM =
raw, uncorrected measured value; relation of wave-quantities
e00 =
directivity in forward direction
e11 =
source match in forward direction
e01 =
reflection tracking in forward direction.
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Determination of equivalent reflection coefficient
The method described by John R. Juroshek makes use of the fact that a
vector network analyzer determines its own errors and forms - together
with the DUT - an "enhanced network analyzer".
The DUT is connected between the two test ports of the vector network
analyzer. The DUT port of interest remains "open". It forms the reference
plane and is the "new" port of the enhanced network analyzer.
The OSM calibration (including sliding loads) will now be performed step by
step and the resulting relations of the wave-quantities will be determined.
After completion of the measurements, the system error correction can
externally be simulated and the required parameter (the equivalent source
match) can be determined.
The most obvious approach would ostensibly be to use the vector network
analyzer to perform this calculation since these algorithms for evaluation
must be implemented in the vector network analyzer anyway. This would
reduce the time required for measuring the equivalent reflection coefficient
(especially when a sliding load is used as usually required for
high-frequency measurements) and would also reduce potential error
sources to a considerable extent.
Unfortunately, characteristic system data cannot be output with most of the
vector network analyzers, which makes the implementation of the method
according to John R. Juroshek difficult.
But with a vector network analyzer of the ZVx family from Rohde &
Schwarz, these parameters can now very easily be output: by entering a
service function, the desired term can be displayed and stored in any usual
form on a storage medium.
Other functions of the vector network analyzer are of course also available
in this mode, which allows the insertion of limit lines (and "limit checks"), for
example.
The measurement results can be displayed on screen in the most common
formats (SWR, reflection coefficient, return loss, ...), output to a
commercial printer or saved to a storage medium.
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3 Further Measuring Methods in Brief
Different methods were presented in the technical literature [1, 2, 3, 4, 5,
7]. Three of these methods will be discussed in the following.
1
Determination of the equivalent reflection coefficient based on the
S-parameters of the power splitter according to the following
equation
Γeq = S 22 − S 32 ⋅
S 21
[1-7].
S 31
2
Determination of the equivalent reflection coefficient according to a
method developed by Rohde & Schwarz [7]. This method is based
on a swept power measurement by using an air line, where
evaluation is performed by means of digital signal processing
methods.
3
Direct measurement of equivalent reflection coefficient at port 2 or
3 by applying a virtual ground at the junction point of the two
resistors by passive or active means on port 1 (AOC and POC
technique [3]).
Although method 1) is discussed sufficiently in the technical literature,
some important facts should be pointed out here since they reduce the
suitability of the method or limit measurement uncertainty. Normally, a
power splitter has three connectors of the same type and gender, i.e. the
network analyzer has to be configured and calibrated to determine the Sparameters of non-insertable DUTs.
In the microwave range, the adapter removal calibration of the vector
network analyzer is thus indispensable.
Unfortunately, this method is very time-consuming and requires twice the
effort of a full two-port calibration. Also the measurement uncertainty is
slightly higher than that obtained with a calibration for insertable DUTs.
The S-parameters must be measured via a measurement cable. The
measurement cables largely contribute to measurement uncertainty since
the position of the cables largely differs from the position used during the
calibration of the vector network analyzer.
Moreover, the DUT’s test port not included in the measurement has to be
terminated with its characteristic reference impedance. In the broadband
range (e.g. to 40 GHz) this is usually not possible within the desired quality.
The accuracy can be improved to a large extent by using a sliding load for
the higher frequency range but this is accompanied by a very
time-consuming measurement and calculation.
The method 2) [7] makes use of the fact that the symmetry of power
splitting depends on the load match.
A longer air line terminated with an mismatched power sensor is connected
to port 2 (port under test) of the power splitter. The end of the air line
connected to port 2 of the power splitter is thus characterized by a
relatively high reflection coefficient whose phase angle quickly changes
with the frequency. Due to interactions with the equivalent reflection
coefficient to be determined for the power splitter, the ratio of the powers
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output at ports 2 and 3 changes and thus also the ratio of measured values
at the power meters. The amplitude of the ripple is proportional to the
magnitudes of the reflection coefficient being determined and the reflection
coefficient at the input of the air line. If the complex reflection coefficient is
also known at the input of the air line, the parameter in question, i.e. the
equivalent reflection coefficient of the test port, can be calculated by digital
signal processing.
This method offers determination of the equivalent reflection coefficient
with only slight uncertainties. Since the method is very convenient and
simple (the port to be tested must be connected only once per
measurement), it is of great importance for use in practice (e.g.
production).
As a specially mismatched sensor is required for this method, its general
use is restricted.
The method was developed for the measurement of power reference
standard and is used by Rohde & Schwarz in this field of application. An
important advantage of this method, especially for this purpose, is the fact
that the power reference (consisting of a power splitter with a fixed power
sensor) does not have to be disassembled to determine the equivalent
reflection coefficient.
The method presented in [7] was implemented up to 40 GHz at Rohde &
Schwarz and was used here as a comparison or reference method.
Remarks regarding 3): The POC method (Passive Open Circuit) allows
measurements only at discrete frequencies. The attainable measurement
accuracy depends on the attenuation between node and port 1. Therefore,
accurate measurements are only possible for the lower GHz range.
The AOC method (Active Open Circuit) prevents the influence of
attenuation by applying a correction signal at port 1. Therefore, the method
is very accurate. However, this method is difficult to automate since the
phase shifter and the attenuator have to be set individually for each
frequency.
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4 Practical Implementation of Measurement Method using Vector
Network Analyzer R&S ZVM or R&S ZVK
If an R&S ZVM or R&S ZVK is used for measuring the equivalent reflection
coefficient, only a microwave cable, a 50 Ω termination and a 10 dB or 20
dB attenuator is required in addition to the corresponding calibration kit.
The method for test port 1 of the vector network analyzer is described as
follows (the case is similar for port 2):
Example:
The equivalent reflection coefficient of port 2 of a power splitter (connectors
3 x 2.92 mm female) is to be determined up to 40 GHz by means of an
R&S ZVK (frequency range 100 MHz to 40 GHz, 100 MHz intervals):
The input of the power splitter is connected to port 1 of the vector network
analyzer. Port 3 of the power splitter is connected to the "R1 CH IN" input
via a cable. The insertion of an adapter does not affect the measurement
accuracy. To prevent the reference channel from being overdriven, it is
recommended to interconnect an attenuator of approx. 10 dB to 20 dB (see
Fig. 2).
The "R1 CH OUT" output is terminated with a 50 Ω load.
Port 2 of the power splitter is now the "new" port 1 of the vector network
analyzer. A "full one-port" calibration (OSM) would be sufficient to
determine
the
equivalent
source
match.
Fig. 2 Test setup with R&S ZVM or R&S ZVK
Since only "full two-port" methods (e.g. TOSM) currently offer direct output
of system errors, such a method has to be used. But only the calibration
steps relevant for port 1 have to be performed. The remaining calibration
steps can be performed without having to connect the corresponding
standards.
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Settings on the R&S ZVK:
PRESET
START 100 MHz
STOP 40 GHz
SWEEP > NUMBER OF POINTS > 400
AVG > IF BW > 100 Hz
FORMAT > MAGNITUDE > SWR
CAL > START NEW CAL > FULL TWO PORT
PORT 1 CONNECTOR > 2.92 mm FEMALE
Note: PORT 1 CONNECTOR refers to the connector system and gender used by the test port
of the vector network analyzer. If the equivalent reflection coefficient of a port at a power
splitter is to be determined, the system or gender of the port to be measured is relevant since
this port represents the test port of the corresponding vector network analyzer port.
PORT 2 CONNECTOR > 2.92 mm MALE or FEMALE
Here, the gender of the connector is irrelevant for measuring the equivalent reflection
coefficient since the measurements at port 2 of the vector network analyzer do not affect the
measurement result of interest.
CAL > START NEW
> TOSM CAL MEAS
CAL
>
FULL
TWO
PORT
>
TOSM
Fig. 3 Calibration steps for the TOSM method
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THROUGH
It is not necessary to connect a standard or to establish a connection.
OPEN PORT 1
Connect OPEN 2.92 mm male to port 2 of power splitter.
OPEN PORT 2
It is not necessary to connect a standard.
SHORT PORT 1
Connect SHORT 2.92 mm male to port 2 of power splitter.
SHORT PORT 2
It is not necessary to connect a standard.
MATCH PORT 1
Connect MATCH 2.92 mm male to port 2 of power splitter.
MATCH PORT 2
It is not necessary to connect a standard.
The following measurements with a sliding load are optional but they
considerably contribute to higher accuracy.
SLIDE PORT 1
Connect sliding load 2.92 mm male to port 2 of power splitter.
The sliding load is measured at 5 positions.
SLIDE PORT 2
This step is not required if the broadband termination (MATCH PORT 2) is defined in the kit
definition up to the stop frequency (i.e.: 40 GHz). If this is not the case, this measurement
must be performed but it is not required to connect a standard.
APPLY CAL
The measurements are completed by pressing this softkey. The correction data for the vector
network analyzer will be determined.
The desired parameter, the equivalent reflection coefficient of port 2 of the
power splitter, can be read by means of a service function.
The service password must be entered first:
SETUP > SERVICE > ENTER PASSWORD
Entry of the following password: 894129
The password is confirmed with "X1 / Enter".
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The vector network analyzer is now in the service mode. After entry of the
service function 2.0.13.12.1, which is confirmed by the ENTER (X1) key,
the equivalent reflection coefficient will be displayed.
Fig. 4 Equivalent reflection coefficient of DUT displayed by the R&S ZVK. Representation in
'SWR' format with limit lines and limit check displayed.
The measurement result can now be displayed in the desired format (e.g.
SWR, reflection coefficient, return loss) on the vector network analyzer.
The result can be printed and stored (e.g. in the ASCII or Touchstone
format) for documentation purposes and/or further processing. The usual
functions of the vector network analyzer are of course available for this
purpose.
The service function can be deactivated by entering the service function
2.0.13.0.
Short summary of important service functions:
Password to access the service menu: 894129
Service function to display the source match at port 1 of the vector network
analyzer: 2.0.13.12.1
Service function to display the source match at port 2 of the vector network
analyzer: 2.0.13.22.1
Service function to switch off the above service functions: 2.0.13.0 or
2.0.13.0.0
Service function to deactivate all service functions with subsequent
PRESET: 0.0.0
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5 Measurement Uncertainty
When measuring the equivalent reflection coefficient, the accuracy is
mainly determined by the specific calibration kit used. The residual system
port impedance match (better known as “Effective Source Match” of the
calibration - kit) more or less corresponds to the measurement uncertainty.
The tools used, e.g. test cables, attenuators and adapters, do not affect the
measurement uncertainty. They only have to be suitable for the frequency
range of interest to avoid any phase discontinuities caused by higher
propagation modes.
Moreover, the measurement accuracy is limited by effects resulting from
a) the DUT
b) the network analyzer
Remarks regarding a): Vector Γ correction is only useful if the power
splitter has stable electronic data. A precondition for this are precision
connectors, for example.
Depending on the connector system, different factors regarding the
reproducibility of the connection have to be considered in the calculation.
Remarks regarding b): The network analyzer can contribute the following
to measurement uncertainty:
-
linearity of the receiver
-
stability of the receiver
-
noise
A drift of the network analyzer is negligible since the measured values are
recorded during calibration. The time required for one measurement is
approx. 5 minutes.
Example:
Measurement uncertainty occurring when determining the equivalent
reflection coefficient of a 2.92 mm power splitter. Since the equivalent
reflection coefficient is a complex parameter, the measurement uncertainty
is calculated as the magnitude of an error vector (radius of the “uncertainty
circle”). As can be shown very easily, the vector uncertainty is expressed
only to a minor extent in the magnitude of the measurand, i.e. a magnitude
uncertainty of approx. 0.7 times the vector uncertainty is expected (if the
equivalent reflection coefficient is greater than the vector uncertainty).
Measuring equipment:
Vector Network Analyzer
R&S ZVK
2.92 mm Calibration Kit with Sliding Loads
R&S ZV-Z35
Test Cables 2.92 mm
R&S ZV-Z15
Attenuators 10 dB, 2.92 mm
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The residual system port impedance match of the 2.92 mm Calibration Kit
R&S ZV-Z35 can be described by approximation with the following
equation
Γq ,eff , ZV − Z 35 ≈ 0.005 + 0.00025 ⋅
f
(see Fig. 5)
GHz
R&S ZV-Z35 specification:
DC to 20 GHz min. 40 dB residual system port impedance match (0.01
linear).
20 to 40 GHz
linear).
min. 35 dB residual system port impedance match (0.018
Fig. 5 µ residual system port impedance match of 2.92 mm Calibration Kit R&S ZV-Z35
The residual system port impedance match in Fig. 5 was determined by
means of a method that made use of an air line.
Due to the skin effect, the impedance of the air line deviates from the
nominal value towards lower frequencies. This deviation is purely
systematic and can be corrected. This correction has not been made (see
Fig. 12) which is why the residual system port impedance match below
approx. 3 GHz has increased.
Parameter
Standard uncertainty
Residual system port impedance 0.0025+0.000125*f/GHz
match with used calibration kit
Reproducibility of measurements
0.0005+0.00005*f/GHz
(noise, repeatability of connections)
Linearity deviation of vector network 0.0005
analyzer
Combined uncertainty (1σ)
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0.0027+0.00013*f/GHz
Rohde & Schwarz
Determination of equivalent reflection coefficient
With a coverage factor of k=2, corresponding to a confidence level of
approx. 95%, a combined uncertainty of approx. 0.0054 + 0.00026*f/GHz is
obtained.
If only the magnitude of the equivalent reflection coefficient is of interest,
2 which corresponds to a
this value can be reduced by a factor of
combined measurement uncertainty of approx. 0.0038 + 0.00018*f/GHz.
6 Experimental Results Check – Comparison with Other
Measurement Methods
The accuracy of the method described can be shown by comparisons with
other methods at 2 power splitters.
a
Power splitter N, DC to 18 GHz, Weinschel model 1870A
The power splitter was kindly provided by PTB. Measured values obtained
by using the AOC method [3] and method [7] ('Ripple method') were
already available for this power splitter. The measurements using the AOC
method were performed in the DKD laboratory 401 of DASA in the city of
Ulm (Germany).
When comparing the three measurement methods, it should also be noted
that several years had elapsed between the different measurement results
and that the power splitter has meanwhile been used.
Measuring equipment used:
Vector Network Analyzer
R&S ZVK
Calibration Kit "N" with Sliding Loads
Agilent 85054B
Test Cable "N"
R&S ZV-Z11
Attenuator 10 dB, various adapters
Fig. 6 Equivalent source match of power splitter Weinschel model 1870A using the method
from John R. Juroshek [1]
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Fig. 7 One standard deviation (σ) based on 4 measurements. Measurement according to [1]
Fig. 8 Error vector magnitude of results according to Juroshek [1] compared with AOC method
[3] and Ripple method [7] (35 points)
Fig. 9 Error vector magnitude of results according to Juroshek [1] compared with Ripple
method [7] (360 test points)
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Remarks regarding Figs. 8 and 9: The measured values obtained using the
AOC method occurred only in a very coarse grid (500 MHz) which is why
the comparison with the Ripple method in the 50 MHz grid is again given in
Fig. 9.
Fig. 8 clearly shows that the deviation to both other methods is nearly the
same, i.e. that the deviation is systematic. The deviation is mainly
determined by the calibration kit used, i.e. by the deviation of the calibration
standards from their mathematical models (e.g. coefficients of the open
standards).
This represents the limit of the method according to Juroshek. If this error
component, the 'residual system port impedance match', were known, the
measurement result of the equivalent reflection coefficient could be
corrected accordingly with this value and the measurement uncertainty
could thus be reduced.
b
Power splitter 2.92mm, DC to 40 GHz, Weinschel model 1534
Measured values (up to 26.5 GHz) of the magnitude of the equivalent
reflection coefficient were provided for this power splitter by the
manufacturer. For this reason, a vectorial comparison is not useful. The
power splitter was measured using the Ripple method [7] and reveals that
the two methods correspond very well with each other up to 40 GHz.
Measuring equipment used:
Vector Network Analyzer
R&S ZVK
2.92 mm Calibration Kit with Sliding Loads
R&S ZV-Z35
Test Cable 2.92 mm
R&S ZV-Z15
Attenuator 10 dB, various adapters
Fig. 10 Equivalent source match of power splitter Weinschel model 1534 using the method
from John R. Juroshek [1]
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Fig. 11 One standard deviation (σ) based on 3 measurements. Measurement according to [1]
Fig. 12 Error vector magnitude of results according to Juroshek [1] compared with Ripple
method [7] (400 test points)
Remarks regarding Figs. 10 and 11:
These two figures clearly show the discontinuity at 4 GHz. A passive power
splitter cannot cause such a hop. The reason for the hop is the use of
different components as terminations during the measurement: fixed
termination up to 4 GHz and sliding load for frequency range from 4 GHz to
40 GHz.
Remarks regarding Fig. 12:
The Ripple method is based on the evaluation of a ripple caused by
mismatch using an air line.
Since the impedance of the air line strongly varies towards lower
frequencies due to the skin effect, the Ripple method would have to be
corrected accordingly in order to work properly for very low frequencies
(with small uncertainties).
Since this correction has not been performed, the “very large” difference of
the two methods between 100 MHz and approx. 3 GHz occurs.
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7 Special Technical Features
The measurement method proposed by John R. Juroshek for determining
the equivalent reflection coefficient of a power splitter can basically be
implemented with any vector network analyzer. However, the transmission
and conversion of measurement data as well as the calculation (especially
when a sliding load is used) is relatively time-consuming and error prone.
Hardware requirements:
If the method is to be implemented using the Vector Network Analyzer R&S
ZVR/E or R&S ZVC/E from Rohde & Schwarz, option R&S ZVR-B6 is
required. This option allows direct access to reference channel a1.
Depending on the type of model used, the equivalent reflection coefficient
can be measured in the frequency range from 9 kHz (R&S ZVR Var. 61and
R&S ZVR-B6) up to 40 GHz (R&S ZVK).
8 Summary
The method described allows fast, accurate and elegant determination of
the equivalent reflection coefficient of a power splitter.
The user can thus very easily apply vector Γ correction, e.g. during the
calibration of power meters, and can consequently profit from a
considerable increase in measurement accuracy.
Once the Γ correction has been implemented, these advantages in the
calibration of power meters can be verified without increasing the DUT
measurement time and without incurring additional costs for expensive
hardware.
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9 References
[1]
John R. Juroshek,
'A direct calibration method for measuring equivalent source
mismatch',
Microwave Journal, October 1997. pp. 106 - 118
[2]
Bengt A. Ulriksson,
'Measurement of Equivalent Source Mismatch',
Lucal Weinschel Inc. P.O. Box 6001, Gaithersburg, MD 208840961
[3]
Robert D. Moyer,
'Techniques for measuring the Effective Source Reflection
Coefficient of Two-Resistor Power-Splitters',
IEEE Transactions on Instrumentation and Measurement, Vol. IM36, No. 1, March 1987 pp. 23 - 28
[4]
Russel A. Johnson,
'Understanding Microwave Power Splitters',
Microwave Journal 12, December 1975. pp. 40 - 51
[5]
'Fundamentals of RF and Microwave Power Measurements'
Application Note 64-1C. Agilent Technologies, April 2001
[6]
Thomas Reichel,
'Voltage and Power Measurements',
Rohde & Schwarz, September 1999. PD 0757.0835.13
[7]
Thomas Reichel,
'Meßverfahren für den äquivalenten Reflexionsfaktor von PowerSplittern',
Presentation for 139th PTB seminar, May 1998, PTB report E-58.
ISBN 3-89701-173-5
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10 Further Application Notes
1EZ51_1E
[1]
O. Ostwald: 3-Port Measurements with Vector Network Analyzer
ZVR, Appl. Note 1EZ26_1E.
[2]
H.-G. Krekels: Automatic Calibration of Vector Network Analyzer
ZVR, Appl. Note 1EZ30_1E.
[3]
O. Ostwald: 4-Port Measurements with Vector Network Analyzer
ZVR, Appl. Note 1EZ25_1E.
[4]
T. Bednorz: Measurement Uncertainties for Vector Network
Analysis, Appl. Note 1EZ29_1E.
[5]
P. Kraus: Measurements on Frequency-Converting DUTs using
Vector Network Analyzer ZVR, Appl. Note 1EZ32_1E.
[6]
J. Ganzert: Accessing Measurement Data and Controlling the
Vector Network Analyzer via DDE, Appl. Note 1EZ33_1E.
[7]
J. Ganzert: File Transfer between Analyzers FSE or ZVR and PC
using MS-DOS Interlink, Appl. Note 1EZ34_1E.
[8]
O. Ostwald: Group and Phase Delay Measurements with Vector
Network Analyzer ZVR, Appl. Note 1EZ35_1E.
[9]
O. Ostwald: Multiport Measurements using Vector Network
Analyzer, Appl. Note 1EZ37_1E.
[10]
O. Ostwald: Frequently Asked Questions about Vector Network
Analyzer ZVR, Appl. Note 1EZ38_3E.
[11]
A. Gleißner: Internal Data Transfer between Windows 3.1 / Excel
and Vector Network Analyzer ZVR, Appl. Note 1EZ39_1E.
[12]
A. Gleißner: Power Calibration of Vector Network Analyzer ZVR,
Appl. Note 1EZ41_2E
[13]
O. Ostwald: Pulsed Measurements on GSM Amplifier SMD ICs
with Vector Analyzer ZVR, Appl. Note 1EZ42_1E.
[14]
O. Ostwald: Time Domain Measurements using Vector Network
Analyzer ZVR, Appl. Note 1EZ44_0E.
[15]
J. Simon: Virtual Embedding Networks for ZVR and ZVC Network
Analyzers, Appl. Note 1EZ45_0E.
[16]
J. Ganzert: Controlling External Generators and Power Meters with
Vector Network Analyzer ZVR, Appl. Note 1EZ46_0E.
[17]
A. Gleißner: Using the Frequency Conversion Mode of Vector
Network Analyzer ZVR, Appl. Note 1EZ47_0E.
[18]
O. Ostwald: Measurement Accuracy of Vector Network Analyzer
ZVK, Appl. Note 1EZ48_0E.
[19]
J. Simon: Reading and Modifying the Correction Data for System
Errors and Power of a ZVR Vector Network Analyzer, Appl. Note
1EZ47_0E.
[20]
T. Bednorz: Conversion Gain Measurements on Mixers with
different Input and Output Impedances, Appl. Note 1EZ50_0E.
20
Rohde & Schwarz
Determination of equivalent reflection coefficient
11 Ordering Information
Vector Network Analyzer
R&S ZVM
R&S ZVK
10 MHz to 20 GHz
10 MHz to 40 GHz
1127.8500.60
1127.8651.00
Test Cables
R&S ZV-Z11
R&S ZV-Z14
R&S ZV-Z15
0 Hz to 18 GHz
0 Hz to 26.5 GHz
0 Hz to 40 GHz
1085.6505.03
1134.4093.02
1134.4193.02
Calibration Kit
R&S ZV-Z21
R&S ZV-Z33
R&S ZV-Z35
0 Hz to 18 GHz
0 Hz to 26.5 GHz
0 Hz to 40 GHz
1085.7099.02
1128.3518.02
1128.3547.02
.
.
.
.
ROHDE & SCHWARZ GmbH & Co. KG Mühldorfstraße 15 D-81671 München Postfach 80 14 69 D-81614 München
.
.
Tel. (+4989) 4129 -0 Fax (+4989) 4129 - 13777 Internet: http://www.rohde-schwarz.com
.
This application note and the supplied programs may only be used subject to observance of the conditions of use set forth
in the download area of the Rohde & Schwarz website.
1EZ51_1E
21
Rohde & Schwarz
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