Download datasheet for LTC3104 by Linear Technology
LTC3104
2.6µA Quiescent Current,
15V, 300mA Synchronous
Step-Down DC/DC
Converter and 10mA LDO
FEATURES
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DESCRIPTION
Ultralow Quiescent Current: 2.6µA
Synchronous Rectification Efficiency Up to 95%
Wide VIN Range: 2.5V to 15V
Wide VOUT Range: 0.6V to 13.8V
300mA Output Current
User-Selectable Automatic Burst Mode® or Forced
Continuous Operation
Accurate and Programmable RUN Pin Threshold
1.2MHz Fixed Frequency PWM
Internal Compensation
Power Good Status Output for VOUT
10mA Adjustable LDO
Available in Thermally Enhanced 3mm × 4mm ×
0.75mm, 14-Pin DFN and 16-Pin MSOP Packages
APPLICATIONS
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Remote Sensor Networks
Distributed Power Systems
Multicell Battery or SuperCap Regulator
Energy Harvesters
Portable Instruments
Low Power Wireless Systems
The LTC®3104 is a high efficiency, monolithic synchronous
step-down converter using a current mode architecture
capable of supplying 300mA of output current. The LTC3104
includes an integrated, adjustable 10mA LDO to power
noise sensitive functions.
The LTC3104 offers two operational modes: automatic
Burst Mode operation and forced continuous mode allowing the user to optimize output voltage ripple, noise and
light load efficiency. With Burst Mode operation enabled,
the typical DC input supply current at no load drops to
2.6µA, maximizing the efficiency for light loads. Selection of forced continuous mode provides very low noise
constant frequency, 1.2MHz operation.
Additionally, the LTC3104 includes an accurate RUN comparator, thermal overload protection, a power good output
and an integrated soft-start feature to guarantee that the
power system start-up is well controlled.
L, LT, LTC, LTM, Burst Mode, Linear Technology and the Linear logo are registered trademarks
of Linear Technology Corporation. All other trademarks are the property of their respective
owners.
TYPICAL APPLICATION
Efficiency vs Output Current
100
ON
OFF
VIN
BST
RUN
SW
FB
ON
OFF
665k
RUNLDO PGOOD
MODE
VINLDO
VLDO
10µF
VCC
1µF
FBLDO
GND
825k
412k
1.8V
10mA
4.7µF
3104 TA01a
47µF
2.2V
300mA
90
85
10
80
75
70
1
65
60
55
50
0.0001
VIN = 3V
VIN = 5V
VIN = 10V
VIN = 15V
0.01
0.1
0.001
OUTPUT CURRENT (A)
1
POWER LOSS (mW)
12pF
1.78M
LTC3104
100
95
22nF 10µH
EFFICIENCY (%)
3V TO 15V
0.1
3104 TA01b
3104f
1
LTC3104
ABSOLUTE MAXIMUM RATINGS
(Note 1)
VIN ............................................................. –0.3V to 18V
SW ................................................ –0.3V to (VIN + 0.3V)
FB, FBLDO.................................................... –0.3V to 6V
BST ........................................ (SW – 0.3V) to (SW + 6V)
VINLDO ........................................................ –0.3V to 17V
VLDO ........................................................... –0.3V to 17V
RUN, MODE, RUNLDO ............................... –0.3V to VIN
VCC, PGOOD ................................................. –0.3V to 6V
Operating Junction Temperature Range
(Notes 2, 3) ............................................ –40°C to 125°C
Storage Temperature Range .................. –65°C to 150°C
Lead Temperature (Soldering, 10 sec)
MSE Only .......................................................... 300°C
PIN CONFIGURATION
TOP VIEW
MODE
TOP VIEW
14 VINLDO
1
VIN
2
13 VLDO
SW
3
12 FBLDO
BST
4
15
GND
NC
MODE
VIN
SW
BST
GND
RUNLDO
PGOOD
11 FB
GND
5
10 RUN
RUNLDO
6
9 VCC
PGOOD
7
8 NC
DE PACKAGE
14-LEAD (4mm × 3mm) PLASTIC DFN
TJMAX = 125°C, θJA = 53°C/W, θJC = 10°C/W
EXPOSED PAD (PIN 15) IS GND, MUST BE SOLDERED TO PCB
1
2
3
4
5
6
7
8
17
GND
16
15
14
13
12
11
10
9
NC
VINLDO
VLDO
FBLDO
FB
RUN
VCC
NC
MSE PACKAGE
16-LEAD PLASTIC MSOP
TJMAX = 125°C, θJA = 40°C/W, θJC = 10°C/W
EXPOSED PAD (PIN 17) IS GND, MUST BE SOLDERED TO PCB
ORDER INFORMATION
LEAD FREE FINISH
TAPE AND REEL
PART MARKING*
PACKAGE DESCRIPTION
TEMPERATURE RANGE
LTC3104EDE#PBF
LTC3104EDE#TRPBF
3104
14-Lead (4mm × 3mm) Plastic DFN
–40°C to 125°C
LTC3104IDE#PBF
LTC3104IDE#TRPBF
3104
14-Lead (4mm × 3mm) Plastic DFN
–40°C to 125°C
LTC3104EMSE#PBF
LTC3104EMSE#TRPBF
3104
16-Lead Plastic MSOP
–40°C to 125°C
LTC3104IMSE#PBF
LTC3104IMSE#TRPBF
3104
16-Lead Plastic MSOP
–40°C to 125°C
Consult LTC Marketing for parts specified with wider operating temperature ranges. *The temperature grade is identified by a label on the shipping container.
Consult LTC Marketing for information on non-standard lead based finish parts.
For more information on lead free part marking, go to: http://www.linear.com/leadfree/
For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/
3104f
2
LTC3104
ELECTRICAL CHARACTERISTICS
The l denotes the specifications which apply over the full operating
junction temperature range, otherwise specifications are at TA = 25°C (Note 2). VIN = VINLDO = 10V unless otherwise noted.
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
Step-Down Converter
Input Voltage Range
Input Undervoltage Lockout Threshold
l
VIN Rising
VIN Rising, TJ = 0°C to 85°C (Note 4)
Input Undervoltage Lockout Hysteresis
(Note 4)
Feedback Voltage
(Note 5)
Feedback Voltage Line Regulation
VIN = 2.5V to 15V (Note 5)
Feedback Input Current
(Note 5)
Oscillator Frequency
Quiescent Current, VIN—Sleep
TJ = 0°C to 85°C, RUN = MODE = VIN, FB > 0.612
RUNLDO = VIN (Note 4)
RUNLDO = 0V (Note 4)
Quiescent Current, VIN—Shutdown
0.588
l
TJ = 0°C to 85°C (Note 4)
RUN = VIN, RUNLDO = VIN, MODE = 0V,
FB > 0.612, Nonswitching
2.1
2.1
15
V
2.6
2.5
V
V
0.4
l
l
Quiescent Current, VIN—Active
2.5
l
0.93
1.0
V
0.6
0.612
V
0.02
0.05
%/V
1
20
nA
1.2
1.2
1.55
1.45
600
MHz
MHz
µA
2.6
1.8
3.3
2.6
µA
µA
RUN = MODE = VIN, FB > 0.612
RUNLDO = VIN
RUNLDO = 0V
l
l
2.8
1.8
5.5
4.5
µA
µA
RUN = 0V, RUNLDO = 0V, TJ = 0°C to 85°C (Note 4)
RUN = 0V, RUNLDO = 0V
l
1
1
1.7
3.3
µA
µA
N-Channel MOSFET Synchronous Rectifier Leakage
Current
VIN = VSW =15V, VRUN = 0V
0.01
0.3
µA
N-Channel MOSFET Switch Leakage Current
VIN =15V, VSW = 0V, VRUN = 0V
0.01
0.3
µA
N-Channel MOSFET Synchronous Rectifier RDS(ON)
ISW = 200mA
0.85
Ω
N-Channel MOSFET Switch RDS(ON)
ISW = –200mA
0.65
Ω
Peak Current Limit
PGOOD Threshold
l
FB Falling, Percentage Below FB
0.40
0.50
0.75
A
–14
–10
–5
%
PGOOD Hysteresis
Percentage of FB
2
%
PGOOD Voltage Low
IPGOOD = 100µA
0.2
V
PGOOD Leakage Current
VPGOOD = 5V
Maximum Duty Cycle
0.01
µA
%
(Note 4)
65
ns
Synchronous Rectifier Minimum On Time (tON(MIN)) (Note 4)
70
ns
Switch Minimum Off Time (tOFF(MIN))
RUN Pin Threshold
RUN Pin Rising
l
89
0.3
92
l
0.76
RUN Pin Hysteresis
RUN Input Current
RUN = 1.2V
MODE Threshold
MODE Input Current
0.8
0.85
0.06
l
l
0.5
MODE = 1.2V
Soft-Start Time
0.7
V
V
0.01
0.4
µA
0.8
1.2
V
0.1
4
µA
1.4
2.5
ms
15
V
LDO Regulator
LDO Input Voltage Range (VIN(LDO))
LDO Output Voltage Range (VLDO)
l
2.5
l
0.6
LDO Feedback Voltage
l
0.576
LDO Feedback Input Current
l
ILDO = 1mA
14.5
V
0.6
0.624
V
1
20
nA
3104f
3
LTC3104
ELECTRICAL CHARACTERISTICS
The l denotes the specifications which apply over the full operating
junction temperature range, otherwise specifications are at TA = 25°C (Note 2). VIN = VINLDO = 10V unless otherwise noted.
PARAMETER
CONDITIONS
Dropout Voltage (VDO)
ILDO = 10mA
MIN
MAX
UNITS
150
Output Current
Output Current—Short Circuit
TYP
VLDO = 0V
l
10
l
15
mV
mA
20
mA
Quiescent Current, VINLDO
VIN = VINLDO = RUNLDO = 10V
0.3
µA
Line Regulation
VINLDO = 2.5V to 15V, ILDO = 1mA
0.1
%
Load Regulation
ILDO = 1mA to 10mA
0.75
RUNLDO Threshold
RUNLDO Input Current
RUNLDO = 1.2V
Note 1: Stresses beyond those listed under Absolute Maximum Ratings
may cause permanent damage to the device. Exposure to any Absolute
Maximum Rating condition for extended periods may affect device
reliability and lifetime.
Note 2: The LTC3104 is tested under pulsed load conditions such that
TJ ≈ TA. The LTC3104E is guaranteed to meet specifications from
0°C to 85°C junction temperature. Specifications over the –40°C to
125°C operating junction temperature range are assured by design,
characterization and correlation with statistical process controls. The
LTC3104I is guaranteed over the full –40°C to 125°C operating junction
temperature range. The junction temperature (TJ) is calculated from the
ambient temperature (TA) and power dissipation (PD) according to the
formula:
TJ = TA + (PD)( θJA°C/W)
where θJA is the package thermal impedance. Note the maximum ambient
temperature consistent with these specifications is determined by specific
operating conditions in conjunction with board layout, the rated package
thermal resistance and other environmental factors.
100
90
90
85
85
80
75
70
65
55
50
0.0001
VIN = 4V
VIN = 7V
VIN = 10V
VIN = 15V
0.001
0.01
0.1
OUTPUT CURRENT (A)
80
75
70
65
ILOAD = 300mA
ILOAD = 100mA
ILOAD = 10mA
ILOAD = 1mA
ILOAD = 100µA
60
55
1
3104 G01
50
4.0
VOUT = 2.2V
L = 10µH
95
EFFICIENCY (%)
EFFICIENCY (%)
VOUT = 3.3V
95 L = 15µH
2
4
12
10
8
INPUT VOLTAGE (V)
6
V
0.01
0.3
µA
Application No-Load Input Current
vs Supply Voltage (Automatic
Burst Mode Operation)
INPUT CURRENT (µA)
Efficiency vs Output Current
1.2
TA = 25°C unless otherwise noted
Efficiency vs Input Voltage
(Automatic Burst Mode Operation)
100
%
0.8
Note 3: This IC includes overtemperature protection that is intended to
protect the device during momentary overload conditions. The maximum
rated junction temperature will be exceeded when this protection is active.
Continuous operation above the specified absolute maximum operating
junction temperature may impair device reliability or permanently damage
the device.
Note 4: Specification is guaranteed by design.
Note 5: The LTC3104 has a proprietary test mode that allows testing in a
feedback loop which servos VFB to the balance point for the error amplifier.
TYPICAL PERFORMANCE CHARACTERISTICS
60
0.5
l
14
16
3104 G02
FRONT PAGE APPLICATION
LDO ENABLED
3.5
3.0
2.5
2.0
0
2
4
6
8 10 12 14
INPUT VOLTAGE (V)
16
18
3104 G03
3104f
4
LTC3104
TYPICAL PERFORMANCE CHARACTERISTICS
100
100
VOUT = 3.3V
L = 10µH
80
80
70
70
60
50
40
30
VIN = 3.7V
VIN = 5V
VIN = 7V
VIN = 10V
VIN = 15V
20
10
0
0.0001
0.001
0.01
0.1
OUTPUT CURRENT (A)
3.0
ILOAD = 300mA
ILOAD = 100mA
ILOAD = 10mA
ILOAD = 1mA
60
50
40
30
20
0
1
10
8
0.25
0
–0.25
3
5
9
7
11
INPUT VOLTAGE (V)
13
15
40
6
4
2
0
–2
–4
–6
0
100
50
0
25 50 75 100 125 150
TEMPERATURE (°C)
3104 G10
SYNCHRONOUS
RECTIFIER
20
10
MAIN
SWITCH
0
–10
–25
75
50
25
TEMPERATURE (°C)
0
5.0
4.5
2.5
0
–2.5
–5.0
VIN = 10V
VOUT = 2.5V
4.0
3.5
3.0
2.5
–7.5
–10.0
–50
125
Application No-Load Input Current
vs Temperature (Automatic Burst
Mode Operation)
VIN = 10V
7.5 VOUT = 2.5V
5.0
100
3104 G09
INPUT CURRENT (µA)
PEAK CURRENT LIMIT CHANGE (%)
LEAKAGE CURRENT (nA)
150
16
30
Peak Current Limit vs Temperature
VIN = 10V
14
NORMALIZED TO 25°C
VIN = 10V
–30
–50
25 50 75 100 125 150
TEMPERATURE (°C)
10.0
MAIN
SWITCH
10
8
12
6
INPUT VOLTAGE (V)
3104 G08
SW Leakage vs Temperature
250
4
–20
3104 G07
SYNCHRONOUS
RECTIFIER
2
RDS(ON) vs Temperature
50
NORMALIZED TO 25°C
–10
–50 –25
–0.50
– 60 – 40 – 20 0 20 40 60 80 100 120 140
TEMPERATURE (°C)
350
FRONT PAGE APPLICATION
LDO ENABLED
3104 G06
–8
0
–50 –25
1.0
0
CHANGE IN RESISTANCE (%)
FREQUENCY CHANGE (%)
CHANGE IN VFB (%)
0.50
200
1.5
Oscillator Frequency
vs Temperature
NORMALIZED TO 25°C
300
2.0
3104 G05
Feedback Voltage
vs Temperature
400
2.5
0.5
10
3104 G04
0.75
3.5
VOUT = 3.3V, L = 10µH
90
EFFICIENCY (%)
EFFICIENCY (%)
90
Application No-Load Input Current
vs Supply Voltage (Forced
Continuous Operation)
Efficiency vs Input Voltage
(Forced Continuous Operation)
INPUT CURRENT (mA)
Efficiency vs Output Current
(Forced Continuous Operation)
TA = 25°C unless otherwise noted
–20
10
70
40
TEMPERATURE (°C)
100
130
3104 G11
2.0
–50 –25 –10 10 30 50 70
TEMPERATURE (°C)
90
110
3104 G12
3104f
5
LTC3104
TYPICAL PERFORMANCE CHARACTERISTICS
Automatic Burst Mode Operation
VOUT
50mV/DIV
AC-COUPLED
Forced Continuous Operation
RUN
5V/DIV
VOUT
1V/DIV
VOUT
20mV/DIV
AC-COUPLED
IL
100mA/DIV
PGOOD
5V/DIV
IL
100mA/DIV
ILOAD = 25mA
VIN = 10V
CIN = 10µF
L = 10µH
VOUT = 2.5V
COUT = 22µF
3104 G13
10µs/DIV
Start-Up into Pre-Biased Output
(Forced Continuous Operation)
PGOOD
5V/DIV
VBST REFRESH
CURRENT PULSES
ILOAD = 2mA
VIN = 10V
L = 10µH
VOUT = 2.5V
500µs/DIV
1µs/DIV
3104 G14
ILOAD = 25mA
VIN = 10V
L = 10µH
VOUT = 2.5V
500µs/DIV
3104 G17
ILOAD = 25mA
VIN = 10V
L = 10µH
VOUT = 2.5V
3104 G18
500µs/DIV
Minimum Input Voltage at
Maximum Duty Cycle vs Load
Current
Load Step
(Forced Continuous Operation)
5.5
5.0
200µs/DIV
ILOAD = LOAD STEP, 50mA TO 200mA
VIN = 10V
L = 10µH
VOUT = 2.5V
COUT = 22µF
3104 G20
INPUT VOLTAGE (V)
3104 G19
SOFT-START/
FOLDBACK PERIOD
IL
100mA/DIV
ILOAD
100mA/DIV
200µs/DIV
ILOAD = LOAD STEP, 5mA TO 300mA
VIN = 10V
CIN = 10µF
L = 10µH
VOUT = 2.5V
COUT = 47µF
3104 G15
500µs/DIV
VOUT
1V/DIV
IL
100mA/DIV
ILOAD
200mA/DIV
BURST CURRENT
PULSES
Start-Up from Shutdown
(Forced Continuous Operation)
VOUT
50mV/DIV
AC-COUPLED
IL
200mA/DIV
SOFT-START
PERIOD
RUN
5V/DIV
PGOOD
5V/DIV
Load Step
(Automatic Burst Mode Operation)
VOUT
200mV/DIV
AC-COUPLED
VBST REFRESH
CURRENT PULSES
ILOAD = 2mA
VIN = 10V
CIN = 10µF
L = 10µH
VOUT = 2.5V
COUT = 47µF
Start-Up from Shutdown
(Automatic Burst Mode Operation)
IL
100mA/DIV
3104 G16
Start-Up into Pre-Biased Output
(Automatic Burst Mode Operation)
IL
100mA/DIV
ILOAD = 25mA
VIN = 10V
CIN = 10µF
L = 10µH
VOUT = 2.5V
COUT = 22µF
RUN
5V/DIV
PGOOD
5V/DIV
VOUT
1V/DIV
RUN
5V/DIV
VOUT
1V/DIV
IL
100mA/DIV
TA = 25°C unless otherwise noted
VOUT = 4.2V
VOUT = 3.3V
VOUT = 2.5V
4.5
VOUT = 2.2V
VOUT = 1.8V
VOUT = 1.5V
4.0
3.5
3.0
2.5
0
50
100
150
200
LOAD CURRENT (mA)
250
300
3104 G21
3104f
6
LTC3104
TYPICAL PERFORMANCE CHARACTERISTICS
Minimum Input Voltage at
Maximum Duty Cycle vs Load
Current
Load Regulation
(Automatic Burst Mode Operation)
1.0
15
CHANGE IN VOUT (%)
INPUT VOLTAGE (V)
12
11
VOUT = 9V
9
0
7
–1.0
0
50
COUT = 68µF
COUT = 47µF
COUT = 22µF
–1.5
VOUT = 5V
6
150
200
100
LOAD CURRENT (mA)
–2.0
300
250
0
10
20
30
ILOAD (mA)
–0.5
–1.0
–1.5
–2.0
COUT = 100µF
COUT = 68µF
COUT = 47µF
–2.5
–3.0
0
20
40
60
ILOAD (mA)
80
100
160
95
140
IOUT = 1mA
90
IOUT = 300mA
85
80
75
70
65
100
2
3
6
5
7
4
INPUT VOLTAGE (V)
8
3104 G25
0.10
CHANGE IN VFB (%)
1.00
0.75
0.50
0.25
0
–0.25
–0.50
–0.75
–1.00
– 60 – 40 – 20 0 20 40 60 80 100 120 140
TEMPERATURE (°C)
3104 G28
60
0.06
80
60
40
20
0
2
4
8
6
10 12
INPUT VOLTAGE (V)
14
16
3104 G27
0.06
0.04
0.02
0
–0.02
–0.04
80
LDO Output Voltage
vs Load Current
NORMALIZED TO VIN = 3.3V
NOMINAL VLDO = 1.8V
ILDO = 5mA
VIN = VINLDO
0.08
70
100
0
9
CHANGE IN OUTPUT VOLTAGE (%)
CHANGE IN LDO OUTPUT VOLTAGE (%)
1.25
30 40 50
ILOAD (mA)
VOUT = 1.2V
VOUT = 1.8V
VOUT = 2.5V
VOUT = 3.3V
VOUT = 5V
120
LDO Output Voltage
vs VIN(LDO) Supply Voltage
NORMALIZED TO 25°C
20
3104 G26
LDO Feedback Voltage
vs Temperature
1.50
10
Automatic Burst Mode Threshold
vs Supply Voltage
BURST THRESHOLD (ILOAD, mA)
0
0
3104 G24
Maximum Duty Cycle
vs Input Voltage
MAXIMUM DUTY CYCLE (%)
CHANGE IN VOUT (%)
0.5
–2.0
3104 G23
Load Regulation
(Automatic Burst Mode Operation)
NORMALIZED AT ILOAD = 100mA
VIN = 10V
VOUT = 1.8V
CFF = 12pF
COUT = 68µF
COUT = 47µF
COUT = 33µF
–1.5
50
40
3104 G22
1.0
0
–0.5
–1.0
8
NORMALIZED AT ILOAD = 100mA
VIN = 10V
VOUT = 3.3V
CFF = 12pF
0.5
–0.5
10
5
1.0
CHANGE IN VOUT (%)
0.5
13
Load Regulation
(Automatic Burst Mode Operation)
NORMALIZED AT ILOAD = 100mA
VIN = 10V
VOUT = 5V
CFF = 12pF
VOUT = 12V
14
TA = 25°C unless otherwise noted
NORMALIZED TO ILDO = 5mA
NOMINAL VLDO = 1.8V
VIN = VINLDO = 10V
0.05
0.04
0.03
0.02
0.01
0
–0.01
2
4
10
8
12
6
INPUT VOLTAGE (V)
14
16
3104 G29
–0.02
0
2
4
8
6
LDO LOAD CURRENT (mA)
10
3104 G30
3104f
7
LTC3104
TYPICAL PERFORMANCE CHARACTERISTICS
TA = 25°C unless otherwise noted
LDO Output Voltage
Load Step
LDO Ripple Rejection
(Automatic Burst Mode Operation)
VOUT
50mV/DIV
AC-COUPLED
VLDO
20mV/DIV
AC-COUPLED
VLDO
20mV/DIV
AC-COUPLED
IL
200mA/DIV
ILOAD
10mA/DIV
20ms/DIV
ILOAD = LOAD STEP, NO LOAD TO 10mA
VLDO = 1.8V
VIN(LDO) = VIN = 10V
CIN = 10µF
COUT = 10µF
PIN FUNCTIONS
3104 G31
50µs/DIV
ILOAD = 10mA
ILDO = 1mA
VLDO = 1.8V, VIN = 10V
VIN(LDO) = VOUT = 2.5V
CIN = 10µF, COUT = 22µF
CLDO = 4.7µF, L = 10µH
3104 G32
(DFN/MSOP)
MODE (Pin 1/Pin 2): Logic-Controlled Input to Select
Mode of Operation. Forcing this pin high commands high
efficiency automatic Burst Mode operation where the buck
will automatically transition from PWM operation at heavy
load to Burst Mode operation at light loads. Forcing this
pin low commands low noise, fixed frequency, forced
continuous operation.
VIN (Pin 2/Pin 3): Main Supply Pin. Decouple with a 10µF
or larger ceramic capacitor. The capacitor should be as
close to the part as possible.
SW (Pin 3/Pin 4): Switch Pin Connects to the Inductor.
This pin connects to the drains of the internal main and
synchronous power MOSFET switches.
BST (Pin 4/Pin 5): Bootstrapped Floating Supply for High
Side Gate Drive. Connect to SW through a 22nF (minimum)
capacitor. The capacitor must be connected between BST
and SW and be located as close as possible to the part
as possible.
GND (Pin 5/Pin 6): Power Ground.
RUNLDO (Pin 6/Pin 7): Logic-Controlled LDO Enable Pin.
This pin may be tied to VIN to enable the LDO.
PGOOD (Pin 7/Pin 8): Open-drain output that is pulled
to ground when the feedback voltage falls 10% (typical)
below the regulation point, during a thermal shutdown
event or if the converter is disabled. The PGOOD output
is valid 1ms after the buck converter is enabled.
NC (Pin 8/Pins 1, 9, 16): No Connect Pin(s) Must Be Tied
to GND.
VCC (Pin 9/Pin 10): Internally Regulated Supply Rail.
Internal power rail regulated off of VIN to power control
circuitry. Decouple with a 1µF or larger ceramic capacitor
placed as close to the part as possible.
RUN (Pin 10/Pin 11): Run Pin Comparator Input. A voltage
greater than 0.84V will enable the IC. Tie this pin to VIN to
enable the IC or connect to an external resistor divider from
VIN to provide an accurate undervoltage lockout threshold.
60mV of hysteresis is provided internally.
FB (Pin 11/Pin 12): Feedback Input to Error Amplifier.
The resistor divider connected to this pin sets the buck
converter output voltage.
FBLDO (Pin 12/Pin 13): Feedback Input to the LDO Error
Amplifier. The resistor divider on this pin sets the LDO
output voltage.
VLDO (Pin 13/Pin 14): LDO Regulator Output. Decouple
with a 4.7µF or larger ceramic capacitor placed as close
to the part as possible.
VINLDO (Pin 14/Pin 15): LDO Supply Pin (15V Maximum).
Decouple with a 10µF or larger ceramic capacitor.
GND (Exposed Pad Pin 15/Exposed Pad Pin 17): Backpad Ground Common. This pad must be soldered to the
PC board and connected to the ground plane for optimal
thermal performance.
3104f
8
LTC3104
BLOCK DIAGRAM
C2
VIN
VCC
VCC
PRE-REG
VCC
C3
IBIAS
UVLO
VCC
OSC
+
UVLO
R6
RUN
+
SHUTDOWN
R5
SD LOGIC
0.8V
BURST ENABLE
CBST
IPEAK
COMP
TOP_ON
VREF_GOOD
VREF
BST
–
IPEAK(REF)
IPEAK
0.6V 0.8V
BOOST
CONTROL
LOGIC
BOT_ON
SW
ANTICROSS
CONDUCT
–
L1
VOUT
C1
+
TSD
MODE
SHUTDOWN
UVLO
RUNLDO
–
THERMAL
SHUTDOWN
IZERO
COMP
TSD
RUNLDO
LOGIC
LDOENABLE
+
+
PWM
PWM
COMP
SLOPE COMP
–
gm
+
SLEEP
COMP
–
+
+
–
0.6V
SS
R2
FB
R1
SLEEP
REF
PGOOD
–
+
0.6V – 10%
VINLDO
VCC
LDO
LDOENABLE
0.6V
VLDO
FBLDO
GND
VLDO
R4
C5
R3
3104 BD
OPERATION
The LTC3104 step-down DC/DC converter is capable of
supplying 300mA to the load. The output voltage is adjustable over a broad range and can be set as low as 0.6V.
Both the power and the synchronous rectifier switches
are internal N-channel MOSFETs. The converter uses a
constant-frequency, current mode architecture and may
be configured using automatic Burst Mode operation for
highly efficient light load operation or for low noise forced
continuous conduction operation where the converter is
optimized to operate over a broad range of step-down
ratios without pulse skipping. With the automatic Burst
Mode feature and the LDO enabled, the typical DC supply
current drops to only 2.6µA with no load. The LTC3104
also includes an independent, 10mA LDO regulator with
a VIN range of 2.5V to 15V.
Main Control Loop
During normal operation, the internal top power MOSFET
is turned on at the beginning of each cycle and turned
off when the PWM current comparator trips. The peak
3104f
9
LTC3104
OPERATION
inductor current where the comparator trips is controlled
by the voltage on the output of the error amplifier. The FB
pin allows the internally compensated error amplifier to
receive an output feedback voltage from an external resistive divider from VOUT . When the load current increases,
the output begins to fall causing a slight decrease in the
feedback voltage relative to the 0.6V reference, this in turn,
causes the control voltage to increase until the average
inductor current matches the new load current. While the
top MOSFET is off, the bottom MOSFET is turned on until
either the inductor current starts to reverse as indicated by
the current reversal comparator, IZERO, or the beginning
of the next clock cycle. IZERO is set to 40mA (typical) in
automatic Burst Mode operation and –110mA (typical) in
forced continuous mode.
Forced Continuous Mode
Grounding MODE enables forced continuous operation
and disables Burst Mode operation. At light loads, forced
continuous mode minimizes output voltage ripple and
noise but is less efficient than Burst Mode operation.
Forced continuous operation may be desirable for use in
applications that are sensitive to the Burst Mode output
voltage ripple or its harmonics. The LTC3104 offers a broad
range of possible step down ratios without pulse skipping
but for very small step-down ratios, the minimum on-time
of the main switch will be reached and the converter will
begin turning off for multiple cycles in order to maintain
regulation.
Burst Mode Operation
Holding the MODE pin above 1.2V will enable automatic
Burst Mode operation and disable forced continuous operation. As the load current increases, the converter will
automatically transition between Burst Mode and PWM
operation. Conversely the converter will automatically
transition from PWM operation to Burst Mode operation
as the load decreases. Between bursts the converter is not
active (i.e., both switches are off) and most of the internal
circuitry is disabled to reduce the quiescent current to
2.6µA. Burst Mode entry and exit is determined by the peak
inductor current and therefore the load current at which
Burst Mode operation will be entered or exited depends
on the input voltage, the output voltage and the inductor
value. Typical curves for Burst Mode entry threshold are
provided in the Typical Performance Characteristics section of this data sheet.
Soft-Start
The converter has an internal closed-loop soft-start circuit
with a nominal duration of 1.4ms. The converter remains
in regulation during soft-start and will therefore respond
to output load transients that occur during this time. In
addition, the output voltage rise time has minimal dependency on the size of the output capacitor or load current.
Thermal Shutdown
If the die temperature exceeds 150°C (typical) the converter and LDO will be disabled. All power devices will be
turned off and the switch node will be forced into a high
impedance state. The soft-start circuit is reset during
thermal shutdown to provide a smooth recovery once the
overtemperature condition is eliminated. If enabled, the
converter and the LDO will restart when the die temperature
drops to approximately 130°C.
Power Good Status Output
The PGOOD pin is an open-drain output which indicates
the output voltage status of the step-down converter. If the
output voltage falls 10% below the regulation voltage, the
PGOOD open-drain output will pull low. A built-in deglitching delay prevents false trips due to voltage transients on
load steps. The output voltage must rise 2% above the
falling threshold before the pull-down will turn off. The
PGOOD output will also pull low during overtemperature
shutdown and undervoltage lockout to indicate these fault
conditions. The PGOOD output is valid 1ms after the buck
converter is enabled. When the converter is disabled the
open-drain device is forced on into a low impedance state.
The PGOOD pull-up voltage must be below the 6V absolute
maximum voltage rating of the pin.
Current Limit
The peak inductor current limit comparator shuts off the
buck switch once the internal limit threshold is reached.
Peak switch current is no less than 400mA.
3104f
10
LTC3104
OPERATION
Slope Compensation
A comparator ensures there is sufficient voltage across
the boost capacitor to guarantee start-up after long sleep
periods or if starting up into a pre-biased output.
Current mode control requires the use of slope compensation to prevent sub-harmonic oscillations in the
inductor current waveform at high duty cycle operation. In
some current mode ICs, current limiting is performed by
clamping the error amplifier voltage to a fixed maximum
which leads to a reduced output current capability at low
step-down ratios. Slope compensation is accomplished
on the LTC3104 internally through the addition of a compensating ramp to the current sense signal. The current
limiting function is completed prior to the addition of the
compensation ramp and therefore achieves a peak inductor
current limit that is independent of duty cycle.
The LTC3104 has an internal UVLO which disables the
converter if the supply voltage decreases below 2.1V (typical). The soft-start for the converter will be reset during
undervoltage lockout to provide a smooth restart once the
input voltage increases above the undervoltage lockout
threshold. The RUN pin can alternatively be configured as
a precise undervoltage lockout (UVLO) on the VIN supply
with a resistive divider connected to the RUN pin.
Short-Circuit Protection
VLDO OUTPUT
When the output is shorted to ground, the error amplifier
will saturate high and the high side switch will turn on at
the start of each cycle and remain on until the current limit
trips. During this minimum on-time, the inductor current
will increase rapidly and will decrease very slowly during
the remainder of the period due to the very small reverse
voltage produced by a hard output short. To eliminate the
possibility of inductor current runaway in this situation, the
switching frequency is reduced to approximately 300kHz
when the voltage on FB falls below 0.3V.
The VLDO output utilizes an internal PMOS pass device
that is guaranteed to support a 10mA load with a typical dropout voltage of 150mV. The LDO is powered by
the VINLDO input which can be tied to an independent
power source or to the VOUT of the step-down converter.
VINLDO can be tied to VIN only if VIN is guaranteed to be
within the absolute maximum ratings of the VINLDO pin.
The quiescent current will increase by about 0.3µA when
VINLDO is tied to VIN. The VLDO output is only active when
VIN is greater than the UVLO threshold and the RUNLDO
pin is high but can be disabled independently by bringing
RUNLDO below 0.5V.
BST Pin Function
The input switch driver operates from the voltage generated on the BST pin. An external capacitor between the SW
and BST pins and an internal synchronous PMOS boost
switch are used to generate a voltage that is higher than
the input voltage. When the synchronous rectifier is on
(SW is low) the internal boost switch connects one side
of the capacitor to VCC replenishing its charge. When the
synchronous rectifier is turned off the input switch is turned
on forcing SW high and the BST pin is at a potential equal
to VCC + SW, relative to ground.
Undervoltage Lockout
The LDO is specifically designed to be stable with a small
4.7µF capacitor, but to also maintain stable operation with
arbitrarily large capacitance values without requiring a
series resistor. The LDO output is current-limit protected
to 20mA (typ). During an undervoltage or overtemperature
fault, the LDO is disabled until the fault condition clears.
3104f
11
LTC3104
APPLICATIONS INFORMATION
The basic LTC3104 application circuit is shown as the
Typical Application on the front page of this data sheet.
The external component selection is determined by the
desired output voltage, output current, desired noise immunity and ripple voltage requirements for each particular
application. However, basic guidelines and considerations
for the design process are provided in this section.
Inductor Selection
The choice of inductor value influences both the efficiency
and the magnitude of the output voltage ripple. Larger inductance values will reduce inductor current ripple and will
therefore lead to lower output voltage ripple. For a fixed DC
resistance, a larger value inductor will yield higher efficiency
by lowering the peak current to be closer to the average.
However, a larger value inductor within the same family
will generally have a greater series resistance, thereby
offsetting this efficiency advantage. Given a desired peak
to peak current ripple, ∆IL (A), the required inductance
can be calculated via the following expression:
L≥
VOUT
1.2 • ∆IL
 V 
•  1– OUT  (µH)
VIN 

A reasonable choice for ripple current is ∆IL = 120mA
which represents 40% of the maximum 300mA load
current. The DC current rating of the inductor should be
at least equal to the maximum load current plus half the
ripple current in order to prevent core saturation and loss
of efficiency during operation. To optimize efficiency the
inductor should have a low series resistance. In particularly
space restricted applications it may be advantageous to
use a much smaller value inductor at the expense of larger
ripple current. In such cases, the converter will operate
in discontinuous conduction for a wider range of output
loads and efficiency will be reduced. In addition, there is a
minimum inductor value required to maintain stability of the
current loop (given the fixed internal slope compensation).
Specifically, if the buck converter is going to be utilized at
duty cycles greater than 40%, the inductance value must
be at least LMIN as given by the following equation:
LMIN ≥ 2.5 • VOUT (µH)
Table 1 depicts the minimum required inductance for
several common output voltages using standard inductor values.
Table 1. Minimum Inductance
OUTPUT VOLTAGE (V)
MINIMUM INDUCTANCE (µH)
0.8
2.2
1.2
3.3
2.0
5.6
2.7
6.8
3.3
8.3
5.0
15
A large variety of low ESR, power inductors are available
that are well suited to the LTC3104 converter applications.
The trade-off generally involves PCB area, application
height, required output current and efficiency. Table 2
provides a representative sampling of small surface mount
inductors that are well suited for use with the LTC3104
buck converter. The inductor specifications listed are for
comparison purposes but other values within these inductor families are generally well suited to this application
as well. Within each family (i.e., at a fixed inductor size),
the DC resistance generally increases and the maximum
current generally decreases with increased inductance.
Output Capacitor Selection
A low ESR output capacitor should be utilized at the buck
output in order to minimize voltage ripple. Multilayer ceramic capacitors are an excellent choice as they have low
ESR and are available in small footprints. In addition to
controlling the output ripple magnitude, the value of the
output capacitor also sets the loop crossover frequency
and therefore can impact loop stability. There is both a
minimum and maximum capacitance value required to
3104f
12
LTC3104
APPLICATIONS INFORMATION
Table 2. Representative Inductor Selection
PART NUMBER
VALUE
(µH)
DCR
(Ω)
MAX DC
CURRENT
(A)
SIZE (MM)
W×L×H
6.8
0.19
1.00
3.0 × 3.0 × 1.5
Coilcraft
EPL3015
LPS3314
10
0.33
0.70
3.3 × 3.3 × 1.3
LPS4018
15
0.26
1.12
4.0 × 4.0 × 1.8
SD3114
6.8
0.30
0.98
3.1 × 3.1 × 1.4
SD3118
10
0.3
0.75
3.2 × 3.2 × 1.8
LQH3NPN
6.8
0.20
1.25
3.0 × 3.0 × 1.4
LQH44PN
10
0.16
1.10
4.0 × 4.0 × 1.7
Cooper-Bussman
Murata
Sumida
CDRH3D16
6.8
0.17
0.73
3.8 × 3.8 × 1.8
CDRH3D16
10
0.21
0.55
3.8 × 3.8 × 1.8
CBC3225
6.8
0.16
0.93
3.2 × 2.5 × 2.5
NR3015
10
0.23
0.70
3.0 × 3.0 × 1.5
NR4018
15
0.30
0.65
4.0 × 4.0 × 1.8
744029006
6.8
0.25
0.95
2.8 × 2.8 × 1.4
744031006
6.8
0.16
0.85
3.8 × 3.8 × 1.7
Taiyo-Yuden
Würth
744031100
10
0.19
0.74
3.8 × 3.8 × 1.7
744031100
15
0.26
0.62
3.8 × 3.8 × 1.7
Panasonic
ELLVGG6R8N
6.8
0.23
1.00
3.0 × 3.0 × 1.5
ELL4LG100MA
10
0.20
0.80
3.8 × 3.8 × 1.8
VLF3012
6.8
0.18
0.78
3.0 × 2.8 × 1.2
VLC4018
10
0.16
0.85
4.0 × 4.0 × 1.8
TDK
ensure stability of the loop. If the output capacitance is
too small, the loop crossover frequency will increase to
the point where switching delay and the high frequency
parasitic poles of the error amplifier will degrade the
phase margin. In addition, the wider bandwidth produced
by a small output capacitor will make the loop more susceptible to switching noise. At the other extreme, if the
output capacitor is too large, the crossover frequency can
decrease too far below the compensation zero and also
lead to degraded phase margin. Table 3 provides a guideline for the range of allowable values of low ESR output
capacitors assuming a feedforward capacitor is used.
See the Output Voltage Programming section for more
details on selecting a feedforward capacitor. Larger value
output capacitors can be accommodated provided they
have sufficient ESR to stabilize the loop, or by increasing
the value of the feedforward capacitor in parallel with the
upper resistor divider resistor.
In Burst Mode operation, the output capacitor stores energy
to satisfy the load current when the LTC3104 is in a low
current sleep state between the burst pulses. It can take
several cycles to respond to a large load step during a sleep
period. If large transient load currents are required then
a larger capacitor can be used at the output to minimize
output voltage droop until the part transitions from Burst
Mode operation to continuous mode operation.
Note that even X5R and X7R type ceramic capacitors have
a DC bias effect which reduces their capacitance when a
DC voltage is applied. It is not uncommon for capacitors
offered in the smallest case sizes to lose more than 50%
of their capacitance when operated near their rated voltage. As a result it is sometimes necessary to use a larger
capacitance value or use a higher voltage rating in order to
realize the intended capacitance value. Consult the manufacturer’s data for the capacitor you select to be assured
of having the necessary capacitance in your application.
Table 3. Recommended Output Capacitor Limits
OUTPUT VOLTAGE (V)
CMIN (µF)
CMAX (µF)
0.8
22.0
220
1.2
15.0
220
2.0
12.0
100
2.7
6.8
68
3.3
4.7
47
5.0
4.7
47
3104f
13
LTC3104
APPLICATIONS INFORMATION
Input Capacitor Selection
Minimum Off-Time/On-Time Considerations
The VIN and VINLDO pins provide current to the power
stages of the buck converter and the LDO, respectively.
It is recommended that a low ESR ceramic capacitor with
a value of at least 10µF be used to bypass each of these
pins. These capacitors should be placed as close to the
respective pin as possible and should have a short return
path to the GND pin.
The maximum duty cycle is limited in the LTC3104 by the
boost capacitor refresh time, the rise/fall times of the switch
as well as propagation delays in the PWM comparator, the
level shifts and the gate drive. This minimum off-time is
typically 65ns which imposes a maximum duty cycle of:
Output Voltage Programming
The output voltage is set by a resistive divider according
to the following formula:
 R2 
VOUT = 0.6V •  1+ 
 R1
1
2 • π •R2 • CFF1
For R2 resistor values of ~1M a 12pF ceramic capacitor
will suffice, however that value may be increased or decreased to optimize the converter’s response for a given
set of application parameters.
VOUT
R2
CFF1
FB
LTC3104
where f is the 1.2MHz switching frequency and tOFF(MIN)
is the minimum off-time. If the maximum duty cycle is
surpassed, due to a dropping input voltage for example,
the output will drop out of regulation. The minimum input
voltage to avoid this dropout condition is:
VIN(MIN) =
The external divider is connected to the output as shown
in Figure 1. Note that FB divider current is not included in
the LTC3104 quiescent current specification. For improved
transient response, a feedforward capacitor, CFF , may be
placed in parallel with resistor R2. The capacitor modifies
the loop dynamics by adding a pole-zero pair to the loop
dynamics which generates a phase boost that can improve
the phase margin and increase the speed of the transient
response, resulting in smaller voltage deviation on load
transients. The zero frequency depends not only on the
value of the feed forward capacitor, but also on the upper
resistor divider resistor. Specifically, the zero frequency,
fZERO, is given by the following equation:
fZERO =
DCMAX = 1 – (f • tOFF(MIN))
R1
GND
3104 F01
Figure 1. Setting the Output Voltage
(
VOUT
1– f • tOFF(MIN)
)
Conversely, the minimum on-time is the smallest duration
of time in which the buck switch can be in its “on” state.
This time is limited by similar factors and is typically 70ns.
In forced continuous operation, the minimum on-time limit
imposes a minimum duty cycle of:
DCMIN = f • tON(MIN)
where tON(MIN) is the minimum on-time. In extreme stepdown ratios where the minimum duty cycle is surpassed,
the output voltage will still be in regulation but the rectifier
switch will remain on for more than one cycle and subharmonic switching will occur to provide a higher effective
duty cycle. The result is higher output voltage ripple. This is
an acceptable result in many applications so this constraint
may not be of critical importance in some cases.
Precise Undervoltage Lockout
The LTC3104 is in shutdown when the RUN pin is low and
active when the pin is higher than the RUN pin threshold.
The rising threshold of the RUN pin comparator is an
accurate 0.8V, with 60mV of hysteresis. This threshold is
enabled when VIN is above the 2.5V minimum value. If VIN
is lower than 2.5V, an internal undervoltage monitor puts
the part in shutdown independent of the RUN pin state.
The RUN pin can be configured as a precise undervoltage
lockout (UVLO) on the VIN supply with a resistive divider
tied to the RUN pin as shown in Figure 2 to meet specific
3104f
14
LTC3104
APPLICATIONS INFORMATION
VIN voltage requirements. If used, note that the external
divider current is not included in the LTC3104 quiescent
current specification.
For most applications a 0.022µF will suffice. The capacitor should be placed as close to the respective pins as
possible.
The rising UVLO threshold can be calculated using the
following equation:
LDO Output Capacitor Selection
 R6 
VUVLO = 0.8V •  1+ 
 R5 
VIN
R6
The LDO is designed to be stable with a minimum 4.7µF
output capacitor. No series resistor is required when using
low ESR capacitors. For most applications, a 10µF ceramic
capacitor is recommended. Larger values will improve
transient response and raise the power supply rejection
ratio (PSRR) of the LDO.
RUN
R5
LDO Output Voltage Programming
LTC3104
The output voltage is set by a resistive divider according
to the following formula:
GND
3104 F02
Figure 2. Setting the Undervoltage Lockout Threshold
Internal VCC Regulator
The LTC3104 uses an internal NMOS source follower
regulator off of VIN to generate a low voltage internal rail,
VCC. The regulator is designed to deliver current only to
the internal drivers and other internal control circuits and
not to an external load. The VCC pin should be bypassed
with a 1µF or larger ceramic capacitor.
 R4 
VLDO = 0.6V •  1+ 
 R3 
The external divider is connected to the LDO output, VLDO,
as shown in Figure 3. Similar to the buck feedback network,
a feedforward capacitor may be placed in parallel with
resistor R4 for improved transient response. For resistor
values of ~1M a 12pF ceramic capacitor will suffice.
VLDO
R4
Boost Capacitor Selection
CFF2
FBLDO
The LTC3104 uses a bootstrapped supply to power the
buck switch gate drivers. When the synchronous rectifier
turns on, an internal PMOS switch turns on synchronously
to charge the boost capacitor, CBST , to the voltage on VCC.
LTC3104
R3
GND
3104 F03
Figure 3. Setting the LDO Output Voltage
VINLDO
VIN
VOUT
VIA GROUND PLANE
MODE
1
14 VINLDO
VIN
2
SW
3
13 VLDO
12 FBLDO
BST
4
11 FB
GND
5
10 RUN
RUNLDO
6
PGOOD
7
9 VCC
8 NC
VLDO
KELVIN TO VOUT
UNINTERRUPTED GROUND PLANE
SHOULD EXIST UNDER ALL COMPONENTS
SHOWN AND UNDER THE TRACES
CONNECTING THOSE COMPONENTS
3104 F04
Figure 4. PCB Layout Recommendations
3104f
15
LTC3104
TYPICAL APPLICATIONS
Dual Lithium-Ion to 2.5V/300mA Regulator with 1.8V /10mA LDO
Efficiency vs Output Current
100
BST
VIN
ON
OFF
SW
RUN
L1
CBST
6.8µH
22nF
R2
931k
LTC3104
FB
CIN
10µF
ON
OFF
VINLDO
VLDO
VCC
C1
1µF
FBLDO
COUT
47µF
90
1.8V
10mA
R4
825k
VIN = 5V
85
VIN = 9V
80
75
70
65
CLDO
4.7µF
R3
412k
GND
CFF
12pF
R1
294k
RUNLDO PGOOD
MODE
95
2.5V
300mA
EFFICIENCY (%)
5V TO 9V
60
0.0001
3104 TA02a
0.001
0.01
0.1
LOAD CURRENT (A)
L1: TDK VLCF4018T
1
3104 TA02b
12V to 3.3V/300mA Regulator with Accurate 5V UVLO,
Forced Continuous Operation and Independently Powered LDO
VIN
12V
VIN
BST
SW
R6
1.47M
R5
280k
L1
10µH
FB
ON
OFF
RUNLDO PGOOD
MODE
VCC
C1
1µF
R1
442k
PGOOD 1M
VINLDO
2.5V TO 12V
VINLDO
VLDO
FBLDO
R4
1.78M
R3
665k
GND
3.3V
COUT 300mA
10µF
CFF
10pF
R2
2M
LTC3104
RUN
CIN
10µF
CBST
22nF
2.2V
10mA
CLDO
4.7µF
C2
10µF
3104 TA03a
L1: WÜRTH 744031100
Start-Up with Ramped Input
Power into 100mA Load on VOUT
VIN
20V/DIV
VOUT
2V/DIV
VLDO
3V/DIV
IL
100mA/DIV
SOFT-START
FOLDBACK PERIOD
1ms/DIV
3104 TA03b
3104f
16
LTC3104
TYPICAL APPLICATIONS
Solar-Powered 2.2V Supply and 1.8V LDO with Li Battery Backup and Run Threshold Set to Battery Minimum Voltage
SDM20E40C
VIN
4.8V, 0.6W
SOLAR PANEL
MPT4.8-150
(6.5VOC)
+
3.6V TADIRAN
AA LITHIUM
BATTERY
R6
3.09M
+
CBULK
100µF
+
CIN
10µF
R5
715k
BST
SW
3.2V RUN
THRESHOLD
L1
15µH
FB
RUNLDO
PGOOD
MODE
CFF1
12pF
R2
1.78M
LTC3104
RUN
R7
1.78M
COUT
47µF
2.2V
R1
665k
VINLDO
VLDO
VCC
C1
1µF
CBST
22nF
FBLDO
GND
R4
825k
R3
412k
1.8V
CLDO
4.7µF
3104 TA04a
L1: COILCRAFT LPS4018
3104f
17
LTC3104
PACKAGE DESCRIPTION
Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings.
DE Package
14-Lead Plastic DFN (4mm × 3mm)
(Reference LTC DWG # 05-08-1708 Rev B)
0.70 ±0.05
3.30 ±0.05
3.60 ±0.05
2.20 ±0.05
1.70 ± 0.05
PACKAGE
OUTLINE
0.25 ± 0.05
0.50 BSC
3.00 REF
RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS
APPLY SOLDER MASK TO AREAS THAT ARE NOT SOLDERED
R = 0.115
TYP
4.00 ±0.10
(2 SIDES)
R = 0.05
TYP
3.00 ±0.10
(2 SIDES)
8
0.40 ± 0.10
14
3.30 ±0.10
1.70 ± 0.10
PIN 1 NOTCH
R = 0.20 OR
0.35 × 45°
CHAMFER
PIN 1
TOP MARK
(SEE NOTE 6)
(DE14) DFN 0806 REV B
7
0.200 REF
1
0.25 ± 0.05
0.50 BSC
0.75 ±0.05
3.00 REF
0.00 – 0.05
BOTTOM VIEW—EXPOSED PAD
NOTE:
1. DRAWING PROPOSED TO BE MADE VARIATION OF VERSION (WGED-3) IN JEDEC
PACKAGE OUTLINE MO-229
2. DRAWING NOT TO SCALE
3. ALL DIMENSIONS ARE IN MILLIMETERS
4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE
MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE
5. EXPOSED PAD SHALL BE SOLDER PLATED
6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION ON THE
TOP AND BOTTOM OF PACKAGE
3104f
18
LTC3104
PACKAGE DESCRIPTION
Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings.
MSE Package
16-Lead Plastic MSOP, Exposed Die Pad
(Reference LTC DWG # 05-08-1667 Rev E)
BOTTOM VIEW OF
EXPOSED PAD OPTION
2.845 ± 0.102
(.112 ± .004)
5.23
(.206)
MIN
2.845 ± 0.102
(.112 ± .004)
0.889 ± 0.127
(.035 ± .005)
8
1
1.651 ± 0.102
(.065 ± .004)
1.651 ± 0.102 3.20 – 3.45
(.065 ± .004) (.126 – .136)
0.305 ± 0.038
(.0120 ± .0015)
TYP
16
0.50
(.0197)
BSC
4.039 ± 0.102
(.159 ± .004)
(NOTE 3)
RECOMMENDED SOLDER PAD LAYOUT
0.254
(.010)
0.35
REF
0.12 REF
DETAIL “B”
CORNER TAIL IS PART OF
DETAIL “B” THE LEADFRAME FEATURE.
FOR REFERENCE ONLY
9
NO MEASUREMENT PURPOSE
0.280 ± 0.076
(.011 ± .003)
REF
16151413121110 9
DETAIL “A”
3.00 ± 0.102
(.118 ± .004)
(NOTE 4)
4.90 ± 0.152
(.193 ± .006)
0° – 6° TYP
GAUGE PLANE
0.53 ± 0.152
(.021 ± .006)
DETAIL “A”
1.10
(.043)
MAX
0.18
(.007)
SEATING
PLANE
0.17 – 0.27
(.007 – .011)
TYP
1234567 8
0.50
(.0197)
BSC
NOTE:
1. DIMENSIONS IN MILLIMETER/(INCH)
2. DRAWING NOT TO SCALE
3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS.
MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS.
INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX
6. EXPOSED PAD DIMENSION DOES INCLUDE MOLD FLASH. MOLD FLASH ON E-PAD SHALL
NOT EXCEED 0.254mm (.010") PER SIDE.
0.86
(.034)
REF
0.1016 ± 0.0508
(.004 ± .002)
MSOP (MSE16) 0911 REV E
3104f
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights.
19
LTC3104
TYPICAL APPLICATION
12V to 5V/300mA Regulator with High Efficiency, Ultralow IQ
(2.8µA with VOUT in Regulation, No Load) and 1.8V/10mA LDO
12V
VIN
BST
RUN
SW
CBST
22nF
L1
10µH
LTC3104
FB
MODE
VINLDO
VLDO
VCC
C1
1µF
FBLDO
R4
2.1M
R3
1.05M
GND
5V
COUT 300mA
47µF
R1
255k
RUNLDO PGOOD
CIN
10µF
CFF
10pF
R2
1.87M
1.8V
10mA
CLDO
4.7µF
3104 TA05
L1: SUMIDA CDRH4D16FB/NP-100M
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PART NUMBER
DESCRIPTION
COMMENTS
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15V, 300mA Synchronous Step-Down DC/DC Converter
with Ultralow Quiescent Current
VIN: 2.5V to 15V, VOUT(MIN) = 0.6V, IQ = 1.8µA, ISD = 1µA,
3mm × 3mm DFN-10, MSOP-10
LTC3642
45V (Transient to 60V) 50mA Synchronous Step-Down
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VIN: 4.5V to 45V, VOUT(MIN) = 0.8V, IQ = 12µA, ISD < 1µA,
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LTC3631
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DC/DC Converter
VIN: 4.5V to 45V, VOUT(MIN) = 0.8V, IQ = 12µA, ISD < 1µA,
3mm × 3mm DFN-8, MSOP-8
LTC3632
50V (Transient to 60V) 20mA Synchronous Step-Down
DC/DC Converter
VIN: 4.5V to 50V, VOUT(MIN) = 0.8V, IQ = 12µA, ISD < 1µA,
3mm × 3mm DFN-8, MSOP-8
LTC3388-1/LTC3388-3
20V, 50mA High Efficiency Nano Power Step-Down
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VIN: 2.7V to 20V, VOUT(MIN) Fixed 1.1V to 5.5V, IQ = 720nA,
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LTC3108/LTC3108-1
Ultralow Voltage Step-Up Converter and Power Managers
VIN: 0.02V to 1V, VOUT(MIN) Fixed 2.35V to 5V, IQ = 6µA,
ISD < 1µA, 3mm × 4mm DFN-12, SSOP-16
LTC3109
Auto-Polarity, Ultralow Voltage Step-Up Converter
and Power Manager
VIN: 0.03V to 1V, VOUT(MIN) Fixed 2.35V to 5V, IQ = 7µA,
ISD < 1µA, 4mm × 4mm QFN-20, SSOP-20
LTC4071
Li-Ion/Polymer Shunt Battery Charger System with Low
Battery Disconnect
Charger Plus Pack Protection in One IC Low Operating Current
(550nA), 50mA Internal Shunt Current, Pin Selectable Float
Voltages (4.0V, 4.1V, 4.2V), 8-Lead, 2mm × 3mm, DFN and MSOP
Packages
LTC4070
Li-Ion/Polymer Low Current Shunt Battery Charger System Selectable VFLOAT = 4.0V, 4.1V, 4.2V, Max Shunt Current = 50mA,
ICCQ = 450nA to 1.04mA, ICCQLB = 300nA, 2mm × 3mm DFN-8,
MSOP-8
LTC1877
10V, 600mA High Efficiency Synchronous Step-Down
DC/DC Converter
VIN: 2.65V to 10V, VOUT(MIN) = 0.8V, IQ = 10µA, ISD < 1µA, MSOP-8
LTC3105
5V, 400mA, MPPC Step-Down Converter with 250mV
Start-Up
VIN: 0.225V to 5V, VOUT(MAX) = 5.25V, IQ = 24µA, ISD = 10µA,
3mm × 3mm DFN-10, MSOP-12
3104f
20 Linear Technology Corporation
LT 1011 • PRINTED IN USA
1630 McCarthy Blvd., Milpitas, CA 95035-7417
(408) 432-1900 ● FAX: (408) 434-0507
●
www.linear.com
 LINEAR TECHNOLOGY CORPORATION 2011
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