TDA2030

TDA2030
UNISONIC TECHNOLOGIES CO., LTD
TDA2030
LINEAR INTEGRATED CIRCUIT
14W HI-FI AUDIO AMPLIFIER
„
DESCRIPTION
The UTC TDA2030 is a monolithic audio power amplifier
integrated circuit.
„
FEATURES
* Very low external component required.
* High current output and high operating voltage.
* Low harmonic and crossover distortion.
* Built-in Over temperature protection.
* Short circuit protection between all pins.
* Safety Operating Area for output transistors.
*Pb-free plating product number: TDA2030L
„
ORDERING INFORMATION
Ordering Number
Normal
Lead Free Plating
TDA2030-TA5-T
TDA2030L-TA5-T
TDA2030-TB5-T
TDA2030L-TB5-T
„
Package
Packing
TO-220-5
TO-220B
Tube
Tube
PIN CONFIGURATION
PIN NO.
1
2
3
4
5
PIN NAME
Non inverting input
Inverting input
-VS
Output
+VS
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QW-R107-004,D
TDA2030
„
LINEAR INTEGRATED CIRCUIT
ABSOLUTE MAXIMUM RATINGS (Ta=25°C)
PARAMETER
SYMBOL
RATINGS
UNIT
±18
Supply Voltage
Vs
V
Input Voltage
VIN
Vs
V
±15
Differential Input Voltage
VI(DIFF)
V
Peak Output Current(internally limited)
IOUT
3.5
A
Total Power Dissipation at Tc=90°C
PD
20
W
Junction Temperature
TJ
-40~+150
°C
Storage Temperature
TSTG
-40~+150
°C
Note: Absolute maximum ratings are those values beyond which the device could be permanently damaged.
Absolute maximum ratings are stress ratings only and functional device operation is not implied.
„
ELECTRICAL CHARACTERISTICS (Refer to the test circuit, Vs =±16V,Ta=25°C)
PARAMETER
Supply Voltage
Quiescent Drain Current
Input Bias Current
Input Offset Voltage
Input Offset Current
Power Bandwidth
Output Power
Open Loop Voltage Gain
Closed Loop Voltage Gain
Distortion
Input Noise Voltage
Input Noise Current
Input Resistance(pin 1)
Supply Voltage Rejection
Thermal Shut-Down Junction
Temperature
SYMBOL
TEST CONDITIONS
Vs
IQ
II(BIAS)
Vs=±18v
VI(OFF)
II(OFF)
BW
POUT=12W, RL=4Ω, Gv=30dB
d=0.5%, Gv=30dB
RL=4Ω
f=40Hz to 15KHz
RL=8Ω
POUT
d=10%, Gv=30dB
RL=4Ω
f=1KHz
RL=8Ω
Gvo
Gvc
f=1kHz
POUT=0.1 to 12W, RL=4Ω
f=40Hz to 15KHz, Gv=30dB
THD
POUT=0.1 to 8W, RL=8Ω
f=40Hz to 15KHz, Gv=30dB
eN
B= 22Hz to 22kHz
iN
B= 22Hz to 22kHz
RIN
RL=4Ω, Gv=30dB
Rg=22kΩ, fripple=100Hz,
SVR
Vripple=0.5Veff
TJ
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MIN
±6
TYP
MAX
±18
10~140,000
14
9
18
11
90
29.5
30
30 .5
UNIT
V
mA
µA
MV
NA
Hz
W
W
W
W
dB
dB
40
0.2
±2
±20
60
2
±20
±200
0.2
0.5
%
0.1
0.5
%
10
200
0.5
3
80
5
µV
pA
MΩ
40
50
dB
145
°C
12
8
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QW-R107-004,D
TDA2030
LINEAR INTEGRATED CIRCUIT
„
TEST CIRCUIT
„
APPLICATION CIRCUIT
+ Vs
Vi
C5
220 F
C1
1 F
C3
100nF
D1
1N4001
1
R3
22k
5
UTC
TDA 2030
2
4
3
R1
13k
R3
680
C2
22 F
R4
1
D1
1N4001
C6
100 F
RL
C4
C7
100nF 220nF
-Vs
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QW-R107-004,D
TDA2030
TYPICAL CHARACTERISTICS
Fig.2 Open loop frequency response
Fig.3 Output power vs. Supply voltage
180
Phase
100
90
60
0
24
Phase
140
Gv=26dB
d=0.5%
f=40 to 15kHz
20
PoUT (W)
Gv(dB)
RL=4
Gain
20
-20
-60
16
RL=8
12
8
4
1
10
2
10
3
10
4
10
5
10
6
10
7
10
24
28
32
Frequency (Hz)
40
44
Fig.5 Two tone CCIF intermodulation
distortion
2
10
2
10
1
10
1
10
Gv=26dB
0
10
d( % )
d( % )
36
Vs (V)
Fig.4 Total harmonic distortion
vs. output power
Vs=38V
RL=8
Vs=32V
PoUT=4W
RL=4
Gv=26dB
0
10
f=15kHz
-1
10
Order (2f1-f2)
-1
10
Vs=32V
RL=4
Order (2f2-f1)
f=1kHz
-2
10
-2
10
-1
10
0
10
1
10
-2
10
2
10
1
10
2
10
Po (W)
3
10
4
10
5
10
Frequency (Hz)
Fig.7 Maximum allowable power
dissipation vs. ambient temperture
Fig.6 Large signal frequency response
30
30
Vs=+-15V
RL=8
25
25
PD (W)
Vs=+-15V
RL=4
20
15
10
20
he
at
Rt sink
h=
h
4° av
C/ ing
he
ats
W
ink
Rt
ha
h=
vi
8°
C/ ng
W
15
10
5
ink
ats
he
te
ini
inf ving
ha
ink C/W
°
ats
he h=25
Rt
Vo(Vp-p)
„
LINEAR INTEGRATED CIRCUIT
5
1
10
2
10
3
10
4
10
Frequency (kHz)
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-50
0
50
100
150
200
Ta (°C)
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QW-R107-004,D
TDA2030
LINEAR INTEGRATED CIRCUIT
5
C2
22 F
R3
56k
R2
56k
UTC
TDA2030
2
4
3
R5
30k
R4
3.3k
C4
10 F
C8
2200 F
R8
1
RL=4
1
1N4001
R6
1.5
1N4001
R1
56k
C5
220 F
/40V
C6
0.22 F
Vi
C1
2.2 F
C3
0.22 F
+Vs
R7
1.5
C7
0.22 F
Fig. 1 Single supply high power amplifier
„
TYPICAL PERFORMANCE OF THE CIRCUIT OF FIG. 1
PARAMETER
Supply Voltage
Quiescent Drain Current
Output Power
Voltage Gain
Slew Rate
Total Harmonic Distortion
SYMBOL
Vs
IQ
POUT
Gv
SR
d
Input Sensitivity
VIN
Signal to Noise Ratio
S/N
TEST CONDITIONS
Vs=36V
d=0.5%,RL=4Ω
f=40Hz to 15kHz,Vs=39V
d=0.5%,RL=4Ω
f=40Hz to 15kHz,Vs=36V
d=10%,f=1kHz,
RL=4Ω,Vs=39V
d=10%,RL=4Ω
f=1kHz,Vs=36V
f=1kHz
POUT=20W,f=1kHz
POUT=20W,f=40Hz to 15kHz
Gv=20dB,POUT=20W,
f=1kHz,RL=4Ω
RL=4Ω,Rg=10kΩ
B=curve A,POUT=25W
RL=4Ω,Rg=10kΩ
B=curve A,POUT=4W
UNISONIC TECHNOLOGIES CO., LTD
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MIN
TYP
36
50
MAX
44
UNIT
V
mA
35
28
W
44
35
19.5
20
8
0.02
0.05
890
108
20.5
dB
V/µsec
%
%
mV
dB
100
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QW-R107-004,D
TDA2030
„
LINEAR INTEGRATED CIRCUIT
TYPICAL PERFORMANCE CHARACTERISTICS
Total Harmonic Distortion vs. Output Power
Output Power vs. Supply Voltage
45
Vs=36V
RL=4
Gv=20dB
10 0
35
25
10 -1
f=15kHz
15
f=1kHz
5
24
28
32
34
Vs (V)
36
40
10 -2
10-1
Output Power vs. Input Level
20
100
101
Power Dissipation vs. Output Power
20
Complete
Amplifier
Gv=26dB
15
PoUT (W)
15
Gv=20dB
10
10
5
5
0
UTC
TDA2030
0
100
250
400
550
VIN (mV)
700
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0
8
16
24
PoUT (W)
32
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QW-R107-004,D
TDA2030
LINEAR INTEGRATED CIRCUIT
TYPICAL AMPLIFIER WITH SPLIT POWER SUPPLY
+Vs
C5
100 F
C1
1 F
Vi
C3
100nF
D1
1N4001
1
5
R3
22k
4
2
3
R1
22k
R3
680
C2
22 F
C6
100 F
R4
1
C8
R5
RL
D2
1N4001
C4
C7
100nF 220nF
-Vs
BRIDGE AMPLIFIER WITH SPLIT POWER SUPPLY(POUT=34W,VS=16V, VS=-16V)
Vs+
C6
100 F
C7
100nF
C1
2.2 F
1
IN
R1
22k
5
UTC TDA2030
4
C8
0.22
F
R8
1
2
3
R3
22k
C4
22 F
RL
8
R4
680
R7
22k
1
R2
22k
5
UTC TDA2030
2
3
VsC2
100 F
C3
100nF
UNISONIC TECHNOLOGIES CO., LTD
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R5
22k
4
C9
0. 22 F
R9
1
C5
22 F
R6
680
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TDA2030
„
LINEAR INTEGRATED CIRCUIT
MULTIWAY SPEAKER SYSTEMS AND ACTIVE BOXES
Multiway loudspeaker systems provide the best possible acoustic performance since each loudspeaker is
specially designed and optimized to handle a limited range of frequencies. Commonly, these loudspeaker systems
divide the audio spectrum two or three bands.
To maintain a flat frequency response over the Hi-Fi audio range the bands cobered by each loudspeaker must
overlap slightly. Imbalance between the loudspeakers produces unacceptable results therefore it is important to
ensure that each unit generates the correct amount of acoustic energy for its segments of the audio spectrum. In this
respect it is also important to know the energy distribution of the music spectrum to determine the cutoff frequencies
of the crossover filters(see Fig. 2).As an example, a 100W three-way system with crossover frequencies of 400Hz
and 3KHz would require 50W for the woofer,35W for the midrange unit and 15W for the tweeter.
Both active and passive filters can be used for crossovers but active filters cost significantly less than a good
passive filter using aircored inductors and non-electrolytic capacitors. In addition active filters do not suffer from the
typical defects of passive filters:
--Power less;
--Increased impedance seen by the loudspeaker(lower damping)
--Difficulty of precise design due to variable loudspeaker impedance.
Obviously, active crossovers can only be used if a power amplifier is provide for each drive unit. This makes it
particularly interesting and economically sound to use monolithic power amplifiers.
In some applications complex filters are not relay necessary and simple RC low-pass and high-pass
networks(6dB/octave) can be recommended.
The result obtained are excellent because this is the best type of audio filter and the only one free from phase and
transient distortion.
The rather poor out of band attenuation of single RC filters means that the loudspeaker must operate linearly well
beyond the crossover frequency to avoid distortion.
A more effective solution is shown in Fig. 3.
The proposed circuit can realize combined power amplifiers and 12dB/octave or high-pass or low-pass filters.
In proactive, at the input pins amplifier two equal and in-phase voltages are available, as required for the active
filter operations.
The impedance at the Pin(-) is of the order of 100Ω,while that of the Pin (+) is very high, which is also what was
wanted.
The components values calculated for fc=900Hz using a Bessel 3rd Sallen and Key structure are:
C1=C2=C3=22nF,R1=8.2KΩ,R2=5.6KΩ,R3=33KΩ.
Using this type of crossover filter, a complete 3-way 60W active loudspeaker system is shown in Fig. 20.
It employs 2nd order Buttherworth filter with the crossover frequencies equal to 300Hz and 3kHz.
The midrange section consistors of two filters a high pass circuit followed by a low pass network. With Vs=36V the
output power delivered to the woofer is 25W at d=0.06%( 30W at d=0.5%).The power delivered to the midrange and
the tweeter can be optimized in the design phase taking in account the loudspeaker efficiency and impedance
(RL=4Ω to 8Ω).
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QW-R107-004,D
TDA2030
LINEAR INTEGRATED CIRCUIT
It is quite common that midrange and tweeter speakers have an efficiency 3dB higher than woofers.
Vs+
Low-pass
300Hz
IN
1 F
2200 F
0.22 F
22k
22k
1
5
2
33nF
BD908
4
UTC
TDA2030
18nF
680
1N4001
1.5
2200 F
0.22 F
3
100 F
22k
1
BD907
4
1.5
100
1N4001
0.22 F
3.3k
Woofer
Vs+
Band-pass
300Hz to 3KHz
0.22 F
1N4001
0.1 F
0.1 F
22k
22k
1
5
18nF
3.3k
2
6.8k
220 F
4
UTC
TDA2030
1
3
3.3nF
8
0.22 F
1N4001
100 F
2.2k
Midrange
Vs+
100
0.22 F
High-pass
3KHz
Vs+
3.3 nF
22k
1N4001
3.3 nF
12k
1
22k
2
5
UTC
TDA2030
100 F
4
1
3
8
1N4001
100 F
0.22 F
22k
47 F
2.2k
100
„
High-pass
3KHz
Tweeter
MUSICAL INSTRUMENTS AMPLIFIERS
Another important field of application for active system is music.
In this area the use of several medium power amplifiers is more convenient than a single high power amplifier, and
it is also more reliable. A typical example (see Fig. 4) consist of four amplifiers each driving a low-cost, 12 inch
loudspeaker. This application can supply 80 to 160W rms.
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QW-R107-004,D
TDA2030
„
LINEAR INTEGRATED CIRCUIT
TRANSIENT INTER-MODULATION DISTORTION(TIM)
Transient inter-modulation distortion is an unfortunate phenomena associated with negative-feedback amplifiers.
When a feedback amplifier receives an input signal which rises very steeply, i.e. contains high-frequency
components, the feedback can arrive too late so that the amplifiers overloads and a burst of inter-modulation
distortion will be produced as in Fig.5. Since transients occur frequently in music this obviously a problem for the
designed of audio amplifiers. Unfortunately, heavy negative feedback is frequency used to reduce the total harmonic
distortion of an amplifier, which tends to aggravate the transient inter-modulation (TIM situation.)
Fig.4 High power active box for musical instrument
Fig.5 Overshoot phenomenon in feedback amplifiers
FEEDBACK
PATH
20 to 40W
Amplifier
¦ÂV4
INPUT
PRE AMPLIFIER
V1
V2
V3
POWER
AMPLIFIER
OUTPUT
V4
20 to 40W
Amplifier
V1
20 to 40W
Amplifier
20 to 40W
Amplifier
V2
V3
V4
The best known method for the measurement of TIM consists of feeding sine waves superimposed onto square
wavers, into the amplifier under test. The output spectrum is then examined using a spectrum analyzer and
compared to the input. This method suffers from serious disadvantages: the accuracy is limited, the measurement is
a tatter delicate operation and an expensive spectrum analyzer is essential.
The "inverting-sawtooth" method of measurement is based on the response of an amplifier to a 20KHz saw-tooth
wave-form. The amplifier has no difficulty following the slow ramp but it cannot follow the fast edge. The output will
follow the upper line in Fig.6 cutting of the shade area and thus increasing the mean level. If this output signal is
filtered to remove the saw-tooth, direct voltage remains which indicates the amount of TIM distortion, although it is
difficult to measure because it is indistinguishable from the DC offset of the amplifier. This problem is neatly avoided
in the IS-TIM method by periodically inverting the saw-tooth wave-form at a low audio frequency as shown in
Fig.7. In the case of the saw-tooth in Fig. 8 the mean level was increased by the TIM distortion, for a saw-tooth in the
other direction the opposite is true.
SR(V/ s)
m2
m1
Input
Signal
Filtered
Output
Siganal
Fig.6 20kHz sawtooth waveform
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Fig.7 Inverting sawtooth waveform
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TDA2030
LINEAR INTEGRATED CIRCUIT
The result is an AC signal at the output whole peak-to-peak value is the TIM voltage, which can be measured
easily with an oscilloscope. If the peak-topeak value of the signal and the peak-to-peak of the inverting sawtooth are
measured, the TIM can be found very simply from:
TIM =
VOUT
* 100
.0
1%
TI
M
=1
%
=0
.1
%
TI
M
TI
M
=0
TIM(%)
SR(V/¦Ìs)
Vsawtooth
In Fig.8 The experimental results are shown for the 30W amplifier using the UTC TDA2030 as a driver and a
low-cost complementary pair. A simple RC filter on the input of the amplifier to limit the maximum signal slope(SS) is
an effective way to reduce TIM.
The Diagram of Fig.9 can be used to find the Slew-Rate(SR) required for a given output power or voltage and a
TIM design target.
For example if an anti-TIM filter with a cutoff at 30kHz is used and the max. peak to peak output voltage is 20V
then, referring to the diagram, a Slew-Rate of 6V/µs is necessary for 0.1% TIM.
As shown Slew-Rates of above 10V/µs do not contribute to a further reduction in TIM.
Slew-Rates of 100V/µs are not only useless but also a disadvantage in hi-fi audio amplifiers because they tend to
turn the amplifier into a radio receiver.
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QW-R107-004,D
TDA2030
„
LINEAR INTEGRATED CIRCUIT
POWER SUPPLY
Using monolithic audio amplifier with non regulated supply correctly. In any working case it must provide a supply
voltage less than the maximum value fixed by the IC breakdown voltage.
It is essential to take into account all the working conditions, in particular mains fluctuations and supply voltage
variations with and without load. The UTC TDA2030 (Vsmax=44V) is particularly suitable for substitution of the
standard IC power amplifiers (with Vsmax=36V) for more reliable applications.
An example, using a simple full-wave rectifier followed by a capacitor filter, is shown in the table and in the diagram
of Fig.10.
A regulated supply is not usually used for the power output stages because of its dimensioning must be done
taking into account the power to supply in signal peaks. They are not only a small percentage of the total music
signal, with consequently large overdimensioning of the circuit.
Even if with a regulated supply higher output power can be obtained(Vs is constant in all working conditions),the
additional cost and power dissipation do not usually justify its use. using non-regulated supplies, there are fewer
designee restriction. In fact, when signal peaks are present, the capacitor filter acts as a flywheel supplying the
required energy.
In average conditions, the continuous power supplied is lower. The music power/continuous power ratio is greater
in case than for the case of regulated supplied, with space saving and cost reduction.
Fig.10 DC characteristics of 50W non-regulated supply
VOUT(V)
34
Ripple
4
32
2
30
Vout
Ripple (Vp-p)
36
220V
Vo
3300 F
0
28
0
0.4
0.8
1.2
1.6
2.0
IOUT(A)
Mains(220V)
Secondary Voltage
+20%
+15%
+10%
—
-10%
-15%
-20%
28.8V
27.6V
26.4V
24V
21.6V
20.4V
19.2V
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IOUT =0
43.2V
41.4V
39.6V
36.2V
32.4V
30.6V
28.8V
DC Output Voltage(VOUT)
IOUT =0.1A
42V
40.3V
38.5V
35V
31.5V
29.8V
28V
IOUT =1A
37.5V
35.8V
34.2V
31V
27.8V
26V
24.3V
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TDA2030
„
LINEAR INTEGRATED CIRCUIT
SHORT CIRCUIT PROTECTION
The UTC TDA2030 has an original circuit which limits the current of the output transistors. This function can be
considered as being peak power limiting rather than simple current limiting. It reduces the possibility that the device
gets damaged during an accidental short circuit from AC output to Ground.
„
THERMAL SHUT-DOWN
The presence of a thermal limiting circuit offers the following advantages:
1).An overload on the output (even if it is permanent),or an above limit ambient temperature can be easily
supported since the Tj can not be higher than 150°C
2).The heatsink can have a smaller factor of safety compared with that of a congenital circuit, There is no
possibility of device damage due to high junction temperature increase up to 150°C, the thermal shut-down
simply reduces the power dissipation and the current consumption.
„
APPLICATION SUGGESTION
The recommended values of the components are those shown on application circuit of Fig.14. Different values can
be used. The following table can help the designer.
SMALLER THAN
LARGER THAN
RECOMMENDED
RECOMMENDED
PURPOSE
COMPONENT
RECOMMENDED VALUE
VALUE
VALUE
Closed loop gaon
Increase of Gain
Decrease of Gain
R1
22KΩ
setting.
Closed loop gaon
Decrease of Gain
Increase of Gain
R2
680Ω
setting.
Decrease of input
Non inverting input
Increase of input impedance
R3
22KΩ
impedance
biasing
Danger of oscillation at high
R4
1Ω
Frequency stability
frequencies with inductive
loads.
Poor high frequencies
Danger of oscillation
R5
≈3R2
Upper frequency cutoff
attenuation
Increase of low
C1
1µF
Input DC decoupling
frequencies cutoff
Increase of low
Inverting DC
C2
22µF
frequencies cutoff
decoupling
C3,C4
0.1µF
Supply voltage bypass
Danger of oscillation
C5,C6
100µF
Supply voltage bypass
Danger of oscillation
C7
0.22µF
Frequency stability
Larger bandwidth
C8
≈1/(2π*B*R1)
Upper frequency cutoff smaller bandwidth
Larger bandwidth
To protect the device
D1,D2
1N4001
against output voltage
spikes.
UTC assumes no responsibility for equipment failures that result from using products at values that
exceed, even momentarily, rated values (such as maximum ratings, operating condition ranges, or
other parameters) listed in products specifications of any and all UTC products described or contained
herein. UTC products are not designed for use in life support appliances, devices or systems where
malfunction of these products can be reasonably expected to result in personal injury. Reproduction in
whole or in part is prohibited without the prior written consent of the copyright owner. The information
presented in this document does not form part of any quotation or contract, is believed to be accurate
and reliable and may be changed without notice.
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QW-R107-004,D
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