ÿþw w w . D a t a S h e e t 4 U . c o m

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SLUS452B – APRIL 2001 – REVISED NOVEMBER 2002
D Dynamic Power Management, DPM
D
D
D
D
D
D
D
D
D
PW PACKAGE
(TOP VIEW)
Minimizes Battery Charge Time
Integrated Selector Supports Battery
Conditioning and Smart Battery Learn
Cycle
Selector Feedback Circuit Insures
Break-Before-Make Transition
±0.4% Charge Voltage Accuracy, Suitable
for Charging Li-Ion Cells
±4% Charge Current Accuracy
300-kHz Integrated PWM Controller for
High-Efficiency Buck Regulation
Depleted Battery Detection and Indication
to Protect Battery From Over Discharge
15-µA Sleep Mode Current for Low Battery
Drain
Designed for Charge Management of
NiCd/NiMH and Li-Ion/Li-Pol Battery Packs
24-Pin TSSOP Package
ACDET
ACPRES
ACSEL
BATDEP
SRSET
ACSET
VREF
ENABLE
BATSET
COMP
ACN
ACP
1
24
2
23
3
22
4
21
5
20
6
19
7
18
8
17
9
16
10
15
11
14
12
13
ACDRV
BATDRV
VCC
PWM
VHSP
ALARM
VS
GND
SRP
SRN
IBAT
BATP
application schematic
D1
R5
ADAPTER MBRD640CT 0.025
SUPPLY
DPAK
1W
Q1
IRFR5305
100Ω
11
ACN
ACDRV 24
1 µF
12 ACP
1
ACDET
VBAT
R6
D1
MBRD640CT 0.05
0.5 W
DPAK
220µF
30 V
bq24700PW
100Ω
R1
499 kΩ
33 µH
D05022p–333
Q2
IRFR5305
4.7 Ω
PWM 21
TO SYSTEM
D4
17 V
R7
523 k Ω
VCC 22
100 kΩ
Q3
IRFR5305
12.6 V +
C5, C6
22 µF
x2
35 V
D4
17 V
R14
523 k Ω
4.7µF
R10
Ω
20Ω
8
ENABLE
SRP 16
3
ACSEL
SRN 15
19 ALARM
BATP 13
C3 10µ F
R9
57.6 k Ω
R15
57.6 k Ω
10Ω
B330
100 kΩ
B330
5
SRSET
BATDRV 23
J1
6
ACSET
2
ACPRES
14 IBAT
20 k Ω
5VREF
C7
3.3µF
C8
7
VREF
VS 18
D3
18 V
VHSP 20
VCC
BATSET 9
499 k Ω
BATDEP 4
150 pF
GND 17
VBAT
C4
10 µF
35 V
180 pF
76.8 kΩ
10 COMP
C9
4.7µF
R13
100Ω
UDG–00138
CHARGE VOLTAGE SETPOINT
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of
Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
Copyright  2002, Texas Instruments Incorporated
!"#$%&" ' ()##* & %' "! +),(%&" -%&*.
#"-)(&' (" !"#$ &" '+*(!(%&" ' +*# &/* &*#$' "! *0%' '&#)$* &'
'&% -%#- 1%##% &2. #"-)(&" +#"(*'' 3 -"*' "& *(*''%#,2 (,)-*
&*'& 3 "! %,, +%#%$*&*#'.
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SLUS452B – APRIL 2001 – REVISED NOVEMBER 2002
description
The bq24700/bq24701 is a highly integrated battery charge controller and selector tailored for the notebook and
sub-notebook PC applications.
The bq24700/bq24701 uses dynamic power management (DPM) to minimize battery charge time by
maximizing use of available wall-adapter power. This is achieved by dynamically adjusting the battery charge
current based on the total system (adapter) current.
The bq24700/bq24701 uses a fixed frequency, pulse width modulator (PWM) to accurately control battery
charge current and voltage. Charge current limits can be programmed from a keyboard controller DAC or by
external resistor dividers from the precision 5-V, ±0.6%, externally bypassed voltage reference (VREF),
supplied by the bq24700/bq24701.
The battery voltage limit can be programmed by using the internal 1.25-V, ±0.5% precision reference, making
it suitable for the critical charging demands of lithium-ion cells. Also, the bq24700/bq24701 provides an option
to override the precision 1.25-V reference and drive the error amplifier either directly from an external reference
or from a resistor divider off the 5 V supplied by the integrated circuit.
The selector function allows the manual selection of the system power source, battery or wall-adapter power.
The bq24700 supports battery-conditioning and battery-lean cycles through the ACSEL function. The ACSEL
function allows manual selection of the battery or wall power as the main system power. It also provides
autonomous switching to the remaining source (battery or ac power) should the selected system power source
terminate (refer to Table 1 for the differences between the bq24700 and the bq24701). The bq24700/bq24701
also provides an alarm function to indicate a depleted battery condition.
The bq24700/bq24701 PWM controller is ideally suited for operation in a buck converter for applications when
the wall-adapter voltage is greater than the battery voltage.
AVAILABLE OPTIONS
Condition
–40 C TA 85 C
Selector Operation
bq24700PW
bq24701PW
Battery as Power Source
Battery removal
Automatically selects ac
Automatically selects ac
Battery reinserted
Selection based on selector inputs
Selection based on selector inputs
AC removal
Automatically selects battery
Automatically selects battery
AC reinserted
Selection based on selector inputs
Selection based on selector inputs
Battery as power source
Sends ALARM signal
Automatically selects ac
Sends ALARM signal
AC as power source
Sends ALARM signal
Sends ALARM signal
Depleted battery condition
Depleted battery condition
ac as Power Source
Depleted Battery Condition
ALARM Signal Active
Selector inputs do not match selector outputs
2
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SLUS452B – APRIL 2001 – REVISED NOVEMBER 2002
absolute maximum ratings over operating free-air temperature (unless otherwise noted)Ĕ}
Supply voltage range: VCC . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to 20 V
Battery voltage range: SRP, SRN . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to 19 V
Input voltage: ACN, ACP . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to 20 V
Virtual junction temperature range, TJ . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –40°C to 85°C
Storage temperature range Tstg . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –65°C to 150°C
Lead temperature (Soldering, 10 seconds) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 300°C
† Stresses beyond those listed under “absolute maximum ratings” may cause permanent damage to the device. These are stress ratings only, and
functional operation of the device at these or any other conditions beyond those indicated under “recommended operating conditions” is not
implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
‡ All voltages are with respect to ground. Currents are positive into and negative out of the specified terminals. Consult the Packaging section of
the databook for thermal limitations and considerations of the package.
recommended operating conditions (TA = TOPR) all voltages relative to Vss
MIN
MAX
Analog and PWM operation
7.0
20
Selector operation
4.5
20
Negative ac current sense, (ACN)
7.0
20
V
Positive ac current sense, (ACP)
7.0
20
V
Negative battery current sense, (SRN)
5.0
18
V
S ppl voltage,
Supply
oltage (VCC)
Positive battery current sense, (SRP)
UNIT
V
5.0
18
V
AC or adapter power detection (ACDET)
–0.3
8
V
AC power indicator (ACPRES)
–0.3
8
V
AC adapter power select (ACSEL)
–0.3
8
V
Depleted battery level (BATDEP)
–0.3
8
V
Battery charge current programming voltage (SRSET)
–0.3
8
V
Charge enable (ENABLE)
–0.3
8
V
External override to an internal 0.5% precision reference (BATSET)
–0.3
8
V
Inverting input to the PWM comparator (COMP)
–0.3
8
V
Battery charge regulation voltage measurement input to the battery—voltage gm amplifier (BATP)
–0.3
8
V
Battery current differential amplifier output (IBAT)
–0.3
8
V
System load voltage input pin (VS)
–0.3
8
V
Depleted battery alarm output (ALARM)
–0.3
8
V
Gate drive output (PWM)
–0.3
20
V
Battery power source select output (BATDRV)
–0.3
20
V
AC or adapter power source selection output (ACDRV)
–0.3
20
V
Operating free–air temperature, TA
–40
85
°C
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SLUS452B – APRIL 2001 – REVISED NOVEMBER 2002
block diagram
VHSP
VCC
20
22
VREF
7
VREF = 5 V
0.5%
ACPRES
VCC/2
2
VCC > 15 V
REF1 = 1.22 V
ACPRES
1
REF2 = 1.25 V
0.5%
ACPRES
HYST = 6%
ACDET
VOLTAGE
REFERENCE
+
VCC
300 kHz
S
Q
R
Q
2V
REF1 = 1.22 V
ACSEL
3
ENABLE
8
OSC
PWM
LOGIC
LEVEL
SHIFT
HIGH–SIDE
DRIVE
21
PWM
13
BATP
9
BATSET
16
SRP
15
SRN
5
SRSET
24
ACDRV
23
BATDRV
17
GND
14
IBAT
+
VHSP
5V
100 µA
COMP
BATTERY
VOLTAGE
ERROR
AMPLIFIER
10
VCC
2 kΩ
ACP
12
+
ACN
11
ACSET
6
ac
CURRENT
ERROR
AMPLIFIER
+
SRN
4
DEPLETED
BATTERY
COMPARATOR
BATP
VS
18
ALARM
19
2 kΩ
+
+
VCC
+
50 kΩ
ADAPTER
SELECT
DRIVE
NO BATTERY
COMPARATOR
+
VHSP
2
+
SWITCH TO
BATTERY
0.25 V
1.25 V
0.5%
BATTERY
CURRENT
ERROR
AMPLIFIER
0.8 x REF1
REF1=1.22 V
+
+
25 kΩ
BATDEP
5V
ACPRES
ACSEL
1
1 bq24700 ONLY
VCC
BATTERY SELECT
LOGIC
AND
ANTI–CROSS
CONDUCT
ACDRV
ACSEL
BATTERY
SELECT
DRIVE
SRN
VREF
SRP
SRN
+
A=20
2 bq24701 ONLY
UDG–00137
4
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SLUS452B – APRIL 2001 – REVISED NOVEMBER 2002
electrical characteristics (TA = TOPR, 7.0 Vdc
otherwise specified)
VCC
20.0 Vdc, all voltages relative to Vss) (unless
quiescent current
PARAMETER
IDDOP
TEST CONDITIONS
Total chip operating current, switching and no
load on PWMB
ISLEEP Total battery sleep current, ac not present
ACPRES = High, PWM ON, VCC = 30 V
MIN
TYP
MAX
1
3
6
mA
15
22
µA
ACPRES = Low, VCC = SRN = 18 V
UNIT
logic interface dc characteristics
PARAMETER
VOL
VIL
TEST CONDITIONS
Low-level output voltage (ACPRES, ALARM)
MIN
TYP
IOL = 1 mA
Low–level input voltage (ACSEL, ENABLE)
VIH
High-level input voltage (ACSEL, ENABLE)
ISINK1 Sink current (ACPRES)
ISINK2 Sink current (ALARM)
MAX
0.4
V
0.8
V
1.8
VOL = 0.4
VOL = 0.4
UNIT
V
2
5
8
mA
0.75
1.5
3.5
mA
pwm oscillator
PARAMETER
fOSC(PWM)
TEST CONDITIONS
Oscillator frequency
MIN
TYP
MAX
0°C ≤ TA ≤ 85°C
260
300
340
–40°C ≤ TA ≤ 0°C
240
300
340
Maximum duty cycle
UNIT
kHz
100%
Input voltage for maximum dc (COMP)
3.8
V
Minimum duty cycle
0%
Input voltage for minimum dc (COMP)
0.8
VRAMP
(peak to peak)
Oscillator ramp voltage (peak-to-peak)
VIK(COMP)
Internal input clamp voltage
(tracks COMP voltage for maximum dc)
IS(COMP)
Internal source current (COMP)
0°C ≤ TA ≤ 85°C
1.85
2.15
2.30
–40°C ≤ TA ≤ 0°C
1.60
2.15
2.30
3.8
4.5
70
110
140
µA
MIN
TYP
MAX
UNIT
Error amplifier = OFF, VCOMP = 1 V
V
leakage current
PARAMETER
TEST CONDITIONS
IL_ACDET
IL_SRSET
Leakage current, ACDET
1
µA
Leakage current, SRSET
1
µA
IL_ACSET
IL_BATDEP
Leakage current, ACSET
1
µA
Leakage current, BATDEP
1
µA
IL_VS
Leakage current, VS
1
µA
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SLUS452B – APRIL 2001 – REVISED NOVEMBER 2002
electrical characteristics (TA = TOPR, 7.0 Vdc
otherwise specified) (continued)
VCC
20.0 Vdc, all voltages relative to Vss) (unless
battery current-sense amplifier
PARAMETER
gm
CMRR
TEST CONDITIONS
Transconductance gain
MIN
TYP
MAX
UNIT
90
150
210
mA/V
Common-mode rejection ratio
See Note 1
90
VICR
Common-mode input (SRP) voltage
range
VCC = SRN + 2 V
ISINK
Sink current (COMP)
COMP = 1 V,
(SRP – SRN) = 10 mV
Input bias current (SRP)
VSRP = 16 V,
SRSET = 0 V, VCC = 20
IIB
Input bias current (SRN)
VSRP = 16 V,
SRSET = 0 V, VCC = 20
VSET
Battery current programming voltage
(SRSET)
AV
Battery current set gain
0.65 V ≤ SRSET ≤ 2.5 V, 8 V ≤ SRN ≤ 16 V,
–40°C ≤ TA ≤ 85°C,
See Note 2
Total battery current
current-sense
sense mid
mid-scale
scale
accuracy
SRSET = 1.25 V, TA = 25°C, See Note 3
SRSET = 1.25 V, –40°C ≤ TA ≤ 85°C, See Note 3
–5%
5%
–6%
6%
current-sense
full-scale
Total battery current
sense full
scale
accuracy
SRSET = 2.5 V, TA = 25°C, See Note 3
SRSET = 2.5 V, –40°C ≤ TA ≤ 85°C, See Note 3
–3%
3%
–4%
4%
5
0.5
18.2
V
1.5
2.5
mA
6
10
200
300
0
24
dB
25
µA
A
2.5
V
26
V/V
NOTES: 1. Ensured by design. Not production tested.
1
2. I
+ SRSET
BAT
A
R
V
SENSE
3. Total battery-current set is based on the measured value of (SRP–SRN) = ∆m, and the calculated value of (SRP–SRN) = ∆C, using
(Dm * Dc)
the measured gain, AV. DC + SRSET , Total accuracy in % +
100
Dc
A
V
6
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SLUS452B – APRIL 2001 – REVISED NOVEMBER 2002
electrical characteristics (TA = TOPR, 7.0 Vdc
otherwise specified) (continued)
VCC
20.0 Vdc, all voltages relative to Vss) (unless
adapter current-sense amplifier
PARAMETER
gm
CMRR
TEST CONDITIONS
Transconductance gain
Common-mode rejection ratio
ISINK
Sink current (COMP)
COMP = 1 V,
Input bias current (ACP, ACN)
ACP = ACN = 20 V, SRSET = 0 V,
VCC = 20 V,
ACSET = 1.25 V
Input bias current accuracy ratio
(ACP, ACN)
ACP = ACN = 20 V,
ACSET = 1.25 V
AC current programming voltage
(ACSET)
AV
AC current set gain
MAX
UNIT
90
150
210
mA/V
90
Common-mode input voltage range
(ACP)
VSET
TYP
See Note 1
VICR
IIB
MIN
7.0
(ACP – ACN) = 10 mV
VCC = 20 V,
dB
VCC+0.2
0.5
1.5
2.5
mA
15
25
35
µA
0.95
1.00
1.05
0
2.5
V
26.5
V/V
0.65 V ≤ ACSET ≤ 2.5 V, 12 V ≤ ACP ≤ 20 V,
–40°C ≤ TA ≤ 85°C, See Note 4
24.5
Total ac current
current-sense
sense mid
mid-scale
scale
accuracy
ACSET = 1.25 V,
–5%
5%
–6%
6%
Total ac current
current-sense
sense full
full-scale
scale
accuracy
ACSET = 2.5 V,
–3.5%
3.5%
–4%
4%
TA = 25°C, See Note 5
ACSET = 1.25 V, –40°C ≤ TA ≤ 85°C, See Note 5
ACSET = 2.5 V,
TA = 25°C,
See Note 5
–40°C ≤ TA ≤ 85°C, See Note 5
V
25.5
battery voltage error amplifier
PARAMETER
TEST CONDITIONS
gm
CMRR
Transconductance gain
VICR
VIT
BATSET common-mode input voltage range
ISINK
VFB
Common-mode rejection ratio
MIN
TYP
MAX
UNIT
75
135
195
mA/V
See Note 1
Internal reference override input threshold voltage
Error-amplifier
Error
am lifier precision
recision reference voltage
dB
2.5
V
0.20
0.25
0.30
V
0.5
1.5
2.5
mA
TA = 25°C
0°C ≤ TA ≤ 70°C
1.241
1.246
1.251
1.239
1.246
1.252
–40°C ≤ TA ≤ 85°C
1.234
1.246
1.254
COMP = 1 V,
(BATP – BATSET) = 10 mV,
BATSET = 1.25 V
Sink current COMP
90
1
V
NOTES: 1. Ensured by design. Not production tested.
1
2. I
+ SRSET
BAT
A
R
V
SENSE
3. Total battery-current set is based on the measured value of (SRP–SRN) = ∆m, and the calculated value of (SRP–SRN) = ∆C, using
(Dm * Dc)
the measured gain, AV. Dc + SRSET , Total accuracy in % +
100
Dc
A
V
1
4. Calculation of the AC current: I
+ ACSET
AC
A
R
V
SENSE
5. Total ac-current set accuracy is based on the measured value of (ACP–ACN) = ∆c, using the measured gain, AV.
(Dm * Dc)
Dc + ACSET , Total accuracy in % +
100
Dc
A
V
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SLUS452B – APRIL 2001 – REVISED NOVEMBER 2002
electrical characteristics (TA = TOPR, 7.0 Vdc
otherwise specified) (continued)
VCC
20.0 Vdc, all voltages relative to Vss) (unless
battery current output amplifier
PARAMETER
TEST CONDITIONS
MIN
5
GTR
Transfer gain
(SRP – SRN) = 50 mV, See Note 6
VIBAT
Battery current readback output voltage
(IBAT)
(SRP – SRN) = 50 mV, SRP = 12 V,
VCC = 18 V,
TA = 25°C
Line rejection voltage
TA = 25°C
0.97
TYP
1.00
MAX
UNIT
18.2
V
1.03
V
10
mV/V
CM
Common-mode input range (SRP)
5
18.2
V
VO(IBAT)
Battery current output voltage range
(IBAT)
0
2.5
V
IS(O)
Output source current (IBAT)
(SRP – SRN) = 100 mV
1200
µA
–4%
4%
Total batter
battery ccurrent
rrent readback mid
mid-scale
scale
accuracy
(SRP – SRN) = 50 mV, TA = 25°C, See Note 7
(SRP – SRN) = 50 mV, –40°C ≤ TA ≤ 85°C,
See Note 7
–6%
6%
(SRP – SRN) = 100 mV, TA = 25°C, See Note 7
(SRP – SRN) = 100 mV, –40°C ≤ TA ≤ 85°C,
See Note 7
–6%
6%
Total battery
batter current
c rrent readback full-scale
f ll scale
accuracy
–8%
8%
150
600
5-V voltage reference
PARAMETER
VREF
TEST CONDITIONS
O tp t voltage
Output
oltage (VREF)
MIN
TYP
MAX
UNIT
0°C ≤ TA ≤ 70°C
5.000
5.030
5.060
V
–40°C ≤ TA ≤ 85°C
4.960
5.030
5.070
V
0.15
0.37
mV/V
1.0
2.5
mV/mA
8
18
30
mA
MIN
TYP
MAX
UNIT
14.5
15.5
16.5
V
–7.2%
–6.5%
–6%
0.45
0.50
0.55
Line regulation
1 mA ≤ ILOAD ≤ 5 mA
Load regulation
Short circuit current
half supply regulator
PARAMETER
VHSP(on)
TEST CONDITIONS
VCC up-threshold for half supply
regulation
VCC hysteresis for half supply regulation
VHSP/VCC
VHSP
Voltage regulation
VCC ≥ VHSP(on), 16.5 V ≤ VCC ≤ 20 V
VCC < VHSP(on),
7 V ≤ VCC ≤ 14.5 V
2.0
V
V
IBAT
+
TR
(SRP * SRN)
7. Total battery current readback accuracy is based on the measured value of VIBAT, VIBATm, and the calculated value of VIBAT,
VIBATc, using the measured value of the transfer gain, GTR.
V
*V
IBATc 100
V
+ (SRP * SRN) GTR Total Accuracy in % + IBATm
IBATc
V
IBATm
NOTES: 6. Battery readback transfer gain G
8
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SLUS452B – APRIL 2001 – REVISED NOVEMBER 2002
electrical characteristics (TA = TOPR, 7.0 Vdc
otherwise specified) (continued)
VCC
20.0 Vdc, all voltages relative to Vss) (unless
MOSFET gate drive
PARAMETER
TEST CONDITIONS
TYP
MAX
UNIT
VCC = 18 V
VCC = 18 V
150
250
Ω
60
120
Ω
VCC = 18 V
VCC = 18 V
200
370
Ω
Battery driver RDS(on) low
100
170
Ω
Time delay from ac driver off to battery driver on
ACSEL 2.4 V ⇓ 0.2 V
0.5
1.5
µs
Time delay from battery driver off to ac driver on
ACSEL 0.2 V ⇑ 2.4 V
1.0
2.0
µs
high level output voltage
PWM driver high-level
IOUT = –10 mA, VCC = 18 V
IOUT = –100 mA, VCC = 18 V
AC driver RDS(on) high
AC driver RDS(on) low
Battery driver RDS(on) high
tDa
tDb
VOH
MIN
–0.12
–0.07
–1.2
–0.7
7
14
Ω
VHSP+0.04
VHSP+0.5
VHSP+0.1
VHSP+0.9
V
4
8
Ω
PWM driver RDS(on) high
VOL
IOUT = 10 mA, VCC = 18 V
IOUT = 100 mA, VCC = 18 V
PWM dri
driver
er lo
low-level
le el o
output
tp t voltage
oltage
V
PWM driver RDS(on) low
selector
PARAMETER
TEST CONDITIONS
VACPRES
VIT(ACPRES)
AC presence detect voltage
See Note 9
td(ALMON)
ACSEL high to alarm set high in ac fault time delay
ACSEL 0.2 V ⇑ 2.4 V
td(ALMOFF)
ACSEL low to alarm reset low in ac fault time delay
SRN = SRP = 8 V,
ACSEL 2.4 V ⇓ 0.2 V
VBATDEP
VNOBAT
Battery depletion ALARM trip voltage
See Note 8
No battery detect, switch to ACDRV
See Note 8
tBATSEL
Battery select time (ACSEL low to BATDRV low)
VS < BATP,
ACSEL 2.4 V ⇓ 0.2 V
tACSEL
VVS
AC select time (ACSEL high to ACDRV low)
ACSEL 0.2 V ⇑ 2.4 V
VS voltage to enable BATDRV
BATP = 1 V
AC presence hysteresis
VIT(VS)
VS voltage hysteresis
VS > BATP
NOTES: 8. Refer to Table 1 to determine the logic operation of the bq24700 and the bq24701.
MIN
TYP
MAX
UNIT
1.165
1.220
1.275
V
40
80
120
mV
5
10
µs
2
10
µs
1.165
1.220
1.275
V
0.87
0.98
1.07
V
0.2
3.0
µs
0.2
3.0
µs
0.96
1.02
V
30
110
mV
9. Maximum ac adapter voltage (VCC) and AC presence detect voltage are 18 V.
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Terminal Functions
TERMINAL
NAME
NO.
I/O
DESCRIPTION
ACDET
1
I
AC or adapter power detection
ACDRV
24
O
AC or adapter power source selection output
ACN
11
I
Negative differential input
ACP
12
I
Positive differential input
ACPRES
2
O
AC power indicator
ACSEL
3
I
AC adapter power select
ACSET
6
I
Adapter current programming voltage
ALARM
19
O
Depleted battery alarm output
BATDEP
4
I
Depleted battery level
BATDRV
23
O
Battery power source select output
BATP
13
I
Battery charge regulation voltage measurement input to the battery-voltage gm amplifier
BATSET
9
I
External override to an internal 0.5% precision reference
COMP
10
O
Inverting input to the PWM comparator
ENABLE
8
I
Charge enable
GND
17
O
Supply return and ground reference
IBAT
14
O
Battery current differential amplifier output
PWM
21
O
Gate drive output
SRN
15
I
Negative differential battery current sense amplifier input
SRP
16
I
Positive differential battery current sense amplifier input
SRSET
5
I
Battery charge current programming voltage
VCC
22
I
Operational supply voltage
VHSP
20
O
Voltage source to drive gates of the external MOSFETs
VREF
7
O
Precision voltage 5-V, ±0.6% reference
VS
18
I
System (load) voltage input pin
pin assignments
ACDET: AC or adapter power detection. This input pin is used to determine the presence of the ac adapter.
When the voltage level on the ACDET pin is less than 1.20 V, the bq24700/bq24701 is in sleep mode, the PWM
control is disabled, the BATDRV is driven low and the ACDRV is driven high. This feature can be used to
automatically select battery as the system’s power source.
ACDRV: AC or adapter power source select output. This pin drives an external P-channel MOSFET used to
switch to the ac wall-adapter as the system’s power source. When the ACSEL pin is high while the voltage on
the ACDET pin is greater than 1.20 V, the output ACDRV pin is driven low (VHSP). This pin is driven high (VCC)
when the ACDET is less than 1.20 V.
ACN, ACP: Negative and positive differential inputs, respectively for ac-to-dc adapter current sense resistor.
ACPRES: This open-drain output pin is used to indicate the presence of ac power. A logic high indicates there
is a valid ac input. A low indicates the loss of ac power. ACPRES is high when the voltage level on the ACDET
pin is greater than 1.20 V.
ACSEL: AC adapter power select. This input selects either the ac adapter or the battery as the power source.
A logic high selects ac power, while a logic low selects the battery.
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pin assignments (continued)
ACSET: Adapter current programming voltage. This input sets the system current level at which dynamic power
management occurs. Adapter currents above this programmed level activate the dynamic power management
and proportionally reduce the available power to the battery.
ALARM: Depleted battery alarm output. This open-drain pin indicates that a depleted battery condition exists.
A pullup on ALARM goes high when the voltage on the BATDEP pin is below 1.20 V. On the bq24700, the
ALARM output also activates when the selector inputs do not match the selector state.
BATDEP: Depleted battery level. A voltage divider network from the battery to BATDEP pin is used to set the
battery voltage level at which depletion is indicated by the ALARM pin. See ALARM pin for more details. A
battery depletion is detected when BATDEP is less than 1.2 V. A no-battery condition is detected when the
battery voltage is < 80% of the depleted threshold. In a no-battery condition, the bq24700 automatically selects
ac as the input source. If ENABLE = 1, the PWM remains enabled.
BATDRV: Battery power source select output. This pin drives an external P-channel MOSFET used to switch
the battery as the system’s power source. When the voltage level on the ACDET pin is less than 1.2 V, the output
of the BATDRV pin is driven low, GND. This pin is driven high (VCC) when ACSEL is high and ACDET > 1.2 V.
BATP: Battery charge regulation voltage measurement input to the battery-voltage gm amplifier. The voltage
on this pin is typically derived from a voltage divider network connected across the battery. In a voltage loop,
BATP is regulated to the 1.25 V, ±0.5% precision reference of the battery voltage gm amplifier.
BATSET: An external override to an internal precision 0.5% reference. When BATSET is > 0.25 V, the voltage
level on the BATSET pin sets the voltage charge level. When BATSET ≤ 0.25 V, an internal 1.25-V, ±0.5%
reference is connected to the inverting input of the battery error amplifier. To ensure proper battery voltage
regulation with BATSET, BATSET must be > 1.0 V. Simply ground BATSET to use the internal reference.
COMP: The inverting input to the PWM comparator and output of the gm amplifiers. A type II compensation
network between COMP and GND is recommended.
ENABLE: Charge enable. A high on this input pin allows PWM control operation to enable charging while a
low on this pin disables and forces the PWM output to a high state. Battery charging is initiated by asserting a
logic 1 on the ENABLE pin.
NOTE:The ENABLE pin should be asserted high only after ACDET has been asserted high and
VREF has been established. When ac is lost, and the bq24700/bq24701 drives ACPRES low, the
host must assert the ENABLE low.
GND: Supply return and ground reference
IBAT: Battery current differential amplifier output. The output of this pin produces a voltage proportional to the
battery charge current. This voltage is suitable for driving an ADC input.
PWM: Gate drive output pin drives the P-channel MOSFET for PWM control. The PWM control is active when
ACPRES, ACSEL, and ENABLE are high. PWM is driven low to VHSP and high to VCC.
SRN, SRP: Differential amplifier inputs for battery current sense. These pins feed back the battery charge
current for PWM control. SRN is tied to the battery terminal. Care must be taken to keep SRN and SRP below
their absolute maximum rating, especially when the battery is removed. Refer to the application section, under
ACDET operation, for further detail outlining the various connection configurations which help keep SRN and
SRP within safe operating regions.
SRSET: Battery charge current programmed voltage. The level on this pin sets the battery charge current limit.
VCC: Operational supply voltage.
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pin assignments (continued)
VHSP: The VHSP pin is connected to a 10-µF capacitor (close to the pin) to provide a stable voltage source
to drive the gates of the external MOSFETs. VHSP is equal to (0.5 × VCC) for VCC ≥ 15 V and 0 V for VCC < 15
V (refer to Figure 12). An 18-V Zener diode should be placed between VCC and VHSP for VCC > 20 V to prevent
MOSFET overstress during start-up.
VREF: Bypassed precision voltage 5-V, ±0.6% output. It can be used to set fixed levels on the inverting inputs
of any one of the three error amplifiers if desired. The tight tolerance is suitable for charging lithium-ion batteries.
A 3.3-µF (or higher) capacitor should be placed close to the pin.
VS: System (Load) voltage input pin. The voltage on this pin indicates the system voltage in order to insure a
break before make transition when changing from ac power to battery power. The battery is protected from an
over-voltage condition by disabling the P-channel MOSFET connected to the BATDRV pin if the voltage at VS
is greater than BATP. This function can be eliminated by grounding the VS pin.
APPLICATION INFORMATION
D1
R5
ADAPTER MBRD640CT 0.025
SUPPLY
DPAK
1W
33 µH
D05022p–333
Q2
IRFR5305
Q1
IRFR5305
100 Ω
220 µF
30 V
bq24700PW
100 Ω
11
ACN
12
ACP
1
ACDET
ACDRV
R1
499 kΩ
D1
MBRD640CT
DPAK
24
1 µF
VBAT
R6
0.05
0.5 W
22
PWM
21
TO SYSTEM
D4
17 V
R7
523 kΩ
4.7 Ω
VCC
Q3
IRFR5305
12.6 V +
C5, C6
22 µF
x2
35 V
D4
17 V
R14
523 kΩ
4.7 µF
100 kΩ
R10
20 Ω
8
ENABLE
SRP
16
3
ACSEL
SRN
15
19
ALARM
BATP
13
5
SRSET
BATDRV
23
6
ACSET
VS
18
2
ACPRES
VHSP
20
14
IBAT
BATSET
9
7
VREF
BATDEP
4
R9
57.6 kΩ
R15
57.6 kΩ
10 Ω
C3 10µ F
B330
100 kΩ
B330
J1
20 kΩ
5VREF
C7
3.3 µF
C8
150 pF
10
VCC
499 kΩ
GND
C9
4.7 µF
D3
18 V
17
VBAT
C4
10 µF
35 V
180 pF
76.8 kΩ
COMP
R13
100 Ω
UDG–00138
CHARGE VOLTAGE SETPOINT
Figure 1. Typical Notebook Charge Management Application
12
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APPLICATION INFORMATION
dynamic power management
The dynamic power management (DPM) feature allows a cost effective choice of an ac wall-adapter that
accommodates 90% of the system’s operating-current requirements. It minimizes battery charge time by
allocating available power to charge the battery (i.e. IBAT = IADPT – ISYS). If the system plus battery charge
current exceeds the adapter current limit, as shown in Figure 2, the DPM feature reduces the battery charge
current to maintain an overall input current consumption within user defined power capability of the wall-adapter.
As the system’s current requirements decrease, additional current can be directed to the battery, thereby
increasing battery charge current and minimizing battery charge time.
The DPM feature is inherently designed into the PWM controller by inclusion of the three control loops,
battery-charge regulation voltage, battery-charge current, and adapter-charge current, refer to Figure 3. If any
of the three user programmed limits are reached, the corresponding control loop commands the PWM controller
to reduce duty cycle, thereby reducing the battery charge current.
ADAPTER CURRENT LIMIT
ADAPTER CURRENT
SYSTEM CURRENT
BATTERY CHARGE CURRENT
NO
CHARGE
MAXIMUM
CHARGE CURRENT
DYNAMIC POWER
MANAGEMENT
MAXIMUM
CHARGE CURRENT
UDG–00113
Figure 2. Dynamic Power Management
ACDET operation
The ACDET function senses the loss of adequate adapter power. If the voltage on ACDET drops below the
internal 1.2 V reference voltage, a loss of ADAPTER power is declared and the bq24700/bq24701 switches to
battery power as the main system power. In addition, the bq24700/bq24701 shuts down its 5-V VREF and enters
a low power sleep mode. Under normal operation with a battery present, the low impedance battery node
absorbs excess energy stored in the system capacitors (from the higher VADPT voltage) and quickly bring the
system voltage down to the battery voltage level. However, in conditions where the battery has been removed
or appears high impedance due to battery protector operation, the residual system energy stored in the load
capacitors due to the higher VADPT level is directly coupled to the SRN and SRP terminals when the battery
switch-over occurs. This presents a problem for VADPT voltages greater than the absolute maximum voltage
rating of the SRN and SRP pins.
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APPLICATION INFORMATION
ACDET sense point
The ACDET function senses adapter voltage via a resistor divider (refer to the Application Circuit). The location
of the ACDET sense node depends on the maximum adapter voltage capability. For operation with VADPT < 18
V, the ACDET sense node can be at the anode of the input blocking diode. Since the VADPT voltage does not
exceed the absolute maximum rating of the SRN pin, SRN stays within safe operating range. For operation with
VADPT ≥ 18 V, the ACDET sense node should be at the cathode of the input blocking diode. Moving the ACDET
sense point to the cathode of the input diode ensures that the bq24700/bq24701 remains active after adapter
power is lost until the load capacitors have discharged to a safe level to protect the SRN and SRP pins. In either
case, it is assumed that the ACDET level is set for VADPT < 17 V.
alternative method
Alternatively, the battery select MOSFET and its associated gate drive protection circuitry could be replaced
with a Schottky. The Schottky allows the ACDET sense point to be moved to the anode side of the input diode,
for VADPT ≥ 18 V, since it blocks the system voltage from the SRN and SRP pins. The bq24700/bq24701 would
retain all functionality with fewer components at the expense of lower battery efficiency and a higher drop-out
voltage.
battery charger operation
The bq24700/bq24701 fixed-frequency, PWM controller is designed to provide closed-loop control of battery
charge-current (ICH) based on three parameters, battery-float voltage (VBAT), battery-charge current, and
adapter charge current (IADPT). The bq24700/bq24701 is designed primarily for control of a buck converter
using a high side P-channel MOSFET device (SW, refer to Figure 3).
The three control parameters are voltage programmable through resistor dividers from the bq24700/bq24701
precision 5-V reference, an external or internal precision reference, or directly via a DAC interface from a
keyboard controller.
Adapter and battery-charge current information is sensed and fed back to two transconductance (gm ) amplifiers
via low-value-sense resistors in series with the adapter and battery respectively. Battery voltage information is
sensed through an external resistor divider and fed back from the battery to a third gm amplifier.
NOTE:The ENABLE pin should be asserted high only after ACDET has been asserted high and
VREF has been established. When ac is lost, and the bq24700/bq24701 drives ACPRES low, the
host must assert the ENABLE low.
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APPLICATION INFORMATION
SW
ISW
+
VADPT
VBAT
CLK
OSC
RAMP
ENABLE
S
Q
R
Q
LATCH OUT
VCC
LEVEL
SHIFT
5V
100 µA
PWM COMPARATOR
PWM
DRIVE
21
PWM
VHSP
FROM ENABLE LOGIC
COMP
10
+
13
BATP
ZCOMP
ENABLE
BATTERY
VOLTAGE
+
1.25 V
BATTERY CHARGE
CURRENT
ADP CURRENT
gm
AMPLIFIERS
UDG–00114
Figure 3. PWM Controller Block Diagram
PWM operation
The three open collector gm amplifiers are tied to the COMP pin (refer to Figure 3), which is internally biased
up by a 100-µA constant current source. The voltage on the COMP pin is the control voltage (VC) for the PWM
comparator. The PWM comparator compares VC to the sawtooth ramp of the internally fixed 300-kHz oscillator
to provide duty cycle information for the PWM drive. The PWM drive is level-shifted to provide adequate gate
voltage levels for the external P-channel MOSFET. Refer to PWM selector switch gate drive section for gate
drive voltage levels.
softstart
Softstart is provided to ensure an orderly start-up when the PWM is enabled. When the PWM controller is
disabled (ENABLE = Low), the 100-µA current source pullup is disabled and the COMP pin is actively pulled
down to GND. Disabling the 100-µA pullup reduces current drain when the PWM is disabled. When the
bq24700/bq24701 PWM is enabled (ENABLE = High), the COMP pin is released and the 100-µA pullup is
enabled (refer to Figure 3). The voltage on the COMP pin increases as the pullup charges the external
compensation network connected to the COMP pin. As the voltage on the COMP pin increases the PWM duty
cycle increases linearly as shown in Figure 4.
NOTE:The ENABLE pin should be asserted high only after ACDET has been asserted high and
VREF has been established. When ac is lost, and the bq24700/bq24701 drives ACPRES low, the
host must assert the ENABLE low.
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APPLICATION INFORMATION
PERCENT DUTY CYCLE
vs
COMPENSATION VOLTAGE
100
90
Percent Duty Cycle – %
80
70
60
50
40
30
20
10
0
1.2
1.7
2.2
2.7
3.2
VCOMP – Compensation Voltage – V
Figure 4
As any one of the three controlling loops approaches the programmed limit, the gm amplifier begins to shunt
current away from the COMP pin. The rate of voltage rise on the COMP pin slows due to the decrease in total
current out of the pin, decreasing the rate of duty cycle increase. When the loop has reached the programmed
limit the gm amplifier shunts the entire bias current (100 µA) and the duty cycle remains fixed. If any of the control
parameters tries to exceed the programmed limit, the gm amplifier shunts additional current from the COMP pin,
further reducing the PWM duty cycle until the offending parameter is brought into check.
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APPLICATION INFORMATION
I
CH
(avg)
I
CH
PWM
V
S
V
C
CLK
UDG–00115
Figure 5. Typical PWM Waveforms in a Buck Converter (Including Startup)
setting the battery charge regulation voltage
The battery charge regulation voltage is programmed through the BATSET pin, if the internal 1.25-V precision
reference is not used. The BATSET input is a high-impedance input that is driven by either a keyboard controller
DAC or via a resistor divider from a precision reference (see Figure 6).
The battery voltage is fed back to the gm amplifier through a resistor divider network. The battery charge
regulation voltage can be defined as:
V
BATTERY
+
(R1 ) R2)
V
R2
BATSET V
(1)
The overall accuracy of the battery charge regulation voltage is a function of the bypassed 5-V reference voltage
tolerance as well as the tolerances on R1 and R2. The precision voltage reference has a 0.5% tolerance making
it suitable for the tight battery voltage requirements of Li-ion batteries. Tolerance resistors of 0.1% are
recommended for R1 and R2 as well as any resistors used to set BATSET.
The bq24700/bq24701 provides the capability of using an internal precision voltage reference (1.25 Vdc)
through the use of a multiplexing scheme, refer to Figure 6, on the BATSET pin. When BATSET voltage is less
than 0.25 V, an internal 1.25-V, 0.5% reference is switched in and the BATSET pin is switched out from the gm
amplifier input. When the BATSET voltage is greater than 0.25 V, the BATSET pin voltage is switched in to the
input of the gm amplifier and the 1.25 V voltage reference is switched out.
NOTE:The minumum recommended BATSET is 1.0 V, if BATSET is used to set the voltage loop.
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APPLICATION INFORMATION
VBAT
BATP
COMP
13
gm AMPLIFIER
9
+
BATSET
10
1.25 V
0.25 V
1.25 V
VBAT
(a) VBATSET < 0.25 V
R1
VREF = 5 V
COMP
BATP
13
gm AMPLIFIER
9
+
R2
1.25 V
10
BATSET
0.25 V
1.25 V
(b) VBATSET > 0.25 V
UDG–00116
Figure 6. Battery Error Amplifier Input Multiplexing Scheme
programming the battery charge current
The battery charge current is programmed via a voltage on the SRSET pin. This voltage can be derived from
a resistor divider from the 5-V VREF or by means of an DAC. The voltage is converted to a current source that
is used to develop a voltage drop across an internal offset resistor at one input of the SR gm amplifier. The charge
current is then a function of this voltage drop and the sense resistor (RS), refer to Figure 7.
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APPLICATION INFORMATION
RS
COMP 10
SRP
2 kΩ
16
+
VREF
SRN
15
SRSET
5
+
50 kΩ
UDG–00117
Figure 7. Battery Charge Current Input Threshold Function
The battery charge current can be defined as:
I
V
+ SRSET
BAT
25 R
S
(2)
where VSRSET is the programming voltage on the SRSET pin. VSRSET maximum is 2.5 V.
programming the adapter current
Like the battery charge current described previously, the adapter current is programmed via a voltage on the
ACSET pin. That voltage can either be from an external resistor divider from the 5-V VREF or from an external
DAC. The adapter current is defined as:
I
ADPT
+
V
ACSET
25 R
S2
(3)
component selection
MOSFET selection
MOSFET selection depends on several factors, namely, gate-source voltage, input voltage and input current.
The MOSFET must be a P-channel device capable of handling at least 20-V gate-to-source with a drain-source
breakdown of VBV~ VIN+1V. The average input current can be approximated by:
I
(avg) ^
IN
ǒVO
I
Ǔ
O
V
IN
1.2
A
(4)
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APPLICATION INFORMATION
The RMS current through the MOSFET is defined as:
I
(RMS) + I (avg)
IN
IN
ǸD1
A
RMS
(5)
Schottky rectifier (freewheeling)
The freewheeling Schottky rectifier must also be selected to withstand the input voltage, VIN. The average
current can be approximated from:
I
(avg) + I
D1
O
(1 * D) A
(6)
choosing an inductance
Low inductance values result in a steep current ramp or slope. Steeper current slopes result in the converter
operating in the discontinuous mode at a higher power level. Steeper current slopes also result in higher output
ripple current, which may require a higher number, or more expensive capacitors to filter the higher ripple
current.
In addition, the higher ripple current results in an error in the sensed battery current particularly at lower charging
currents. It is recommended that the ripple current not exceed 20% to 30% of full scale dc current.
L+
ǒVIN * VBATǓ
fs
0.2
I
V
BAT
V
IN
FS
(7)
Too large an inductor value results in the current waveform of Q1 and D1 in Figure 8 approximating a
squarewave with an almost flat current slope on the step. In this case, the inductor is usually much larger than
necessary, which may result in an efficiency loss (higher DCR) and an area penalty.
selecting an output capacitor
For this application the output capacitor is used primarily to shunt the output ripple current away from the battery.
The output capacitor should be sized to handle the full output ripple current as defined as:
I c (RMS) +
ǒVIN * VBATǓ
fs
L
D
Ǹ12
(8)
selecting an input capacitor
The input capacitor is used to shunt the converter ripple current on the input lines. The capacitor(s) must have
a ripple curent (RMS) rating of:
I
20
RMS
+I
V
IN(avg)
IN
V
O
Ǹ ǒ
V
Ǔ
V
IN 1 * IN
V
V
O
O
A
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APPLICATION INFORMATION
compensating the loop
For the bq24700/bq24701 used as a buck converter, the best method of compensation is to use a Type II
compensation network from the output of the transconductance amplifiers (COMP pin) to ground (GND) as
shown in Figure 8. A Type II compensation adds a pole-zero pair and an addition pole at dc.
100 µA
COMP
gm
AMPLIFIER
+
10
RCOMP
CP
CZ
+
gm
AMPLIFIER
+
gm
AMPLIFIER
bq24700
UDG–00118
Figure 8. Type II Compensation Network
The Type II compensation network places a zero at
F +1
Z
2
p
R
p
R
COMP
C
Z
Hz
(10)
and a pole at
F +1
P
2
COMP
C
P
Hz
(11)
For this battery charger application the following component values: CZ = 4.7 µF, CP = 150 pF, and
RCOMP = 100Ω, provides a closed loop response with more than sufficient phase margin.
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APPLICATION INFORMATION
selector operation
The bq24700/bq24701 allows the host controller to manually select the battery as the system’s main power
source, without having to remove adapter power. This allows battery conditioning through smart battery learn
cycles. In addition, the bq24700/bq24701 supports autonomous supply selection during fault conditions on
either supply. The selector function uses low RDS(on) P-channel MOSFETs for reduced voltage drops and longer
battery run times. Note: Selection of battery power whether manual or automatic results in the suspension of
battery charging.
ADAPTER SELECT SWITCH
ADAPTER
INPUT
SYSTEM
LOAD
(bq24700)
PWM
BATTERY
CHARGER
BAT
ACDRV
(bq24700) 24
BATTERY
SELECTOR
BATDRV
CONTROL 23
BATTERY
SELECT
SWITCH
UDG–00119
Figure 9. Selector Control Switches
autonomous selection operation
Adapter voltage information is sensed at the ACDET pin via a resistor divider from the adapter input (refer to
ACDET operation section). The voltage on the ACDET pin is compared to an internally fixed threshold. An
ACDET voltage less than the set threshold is considered as a loss of adapter power regardless of the actual
voltage at the adapter input. Information concerning the status of adapter power is fed back to the host controller
through ACPRES. The presence of adapter power is indicated by ACPRES being set high. A loss of adapter
power is indicated by ACPRES going low regardless of which power source is powering the system. During a
loss of adapter power, the bq24700/bq24701 obtains operating power from the battery through the body diode
of the P-channel battery select MOSFET. Under a loss of adapter power, ACPRES (normally high) goes low,
if adapter power is selected to power the system, the bq24700/bq24701 automatically switches over to battery
power by commanding ACDRV high and BATDRV low and ALARM goes high. During the switch transition
period, battery power is supplied to the load via the body diode of the battery select P-channel MOSFET. When
adapter power is restored, the bq24700/bq24701 configures the selector switches according to the state of
signals; ACSEL, and ACPRES. If the ACSEL pin is left high when ac power is restored, the bq24700/bq24701
automatically switches back to ac power and the ALARM pin goes low. To remain on battery power after ac
power is restored, the ACSEL pin must be brought low.
Conversely, if the battery is removed while the system is running on battery power and adapter power is present,
the bq24700/bq24701 automatically switches over to adapter power by commanding BATDRV high and
ACDRV low. Note: For the bq24700 any fault condition that results in the selector MOSFET switches not
matching their programmed states is indicated by the ALARM pin going high. Please refer to Battery Depletion
Detection Section for more information on the ALARM discrete.
22
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SLUS452B – APRIL 2001 – REVISED NOVEMBER 2002
APPLICATION INFORMATION
smart learn cycles when adapter power is present
Smart learn cycles can be conducted when adapter power is present by asserting and maintaining the ACSEL
pin low. The adapter power can be reselected at the end of the learn cycle by a setting ACSEL to a logic high,
provided that adapter power is present. Battery charging is suspended while selected as the system power
source.
When selecting the battery as the system primary power source, the adapter power select MOSFET turns off,
in a break-before-make fashion, before the battery select MOSFET turns on. To ensure that this happens under
all load conditions, the system voltage (load voltage) can be monitored through a resistor divider on the VS pin.
This function provides protection against switching over to battery power if the adapter selector switch were
shorted and adapter power present. This function can be eliminated by grounding the VS pin. During the
transition period from battery to adapter or adapter to battery, power is supplied to the system through the body
diode of the battery select switch.
battery depletion detection
The bq24700/bq24701 provides the host controller with a battery depletion discrete, the ALARM pin, to alert
the host when a depleted battery condition occurs. The battery depletion level is set by the voltage applied to
the BATDEP pin through a voltage divider network. The ALARM output asserts high and remains high as long
as the battery deplete condition exists regardless of the power source selected.
For the bq24700, the host controller must take appropriate action during a battery deplete condition to select
the proper power source. The bq24700 remains on the selected power source. The bq24700, however,
automatically reverts over to adapter power, provided the adapter is present, during a deep discharge state. The
battery is considered as being in a deep discharge state when the battery voltage is less than (0.8 × depleted
level).
The bq24701 automatically switches back to adapter power if a battery deplete condition exists, provided that
the adapter is present. Feature sets for the bq24700 and bq24701 are detailed in Table 1.
Table 1. Available Options
Condition
–40 C TA 85 C
Selector Operation
bq24700PW
bq24701PW
Battery as Power Source
Battery removal
Automatically selects ac
Automatically selects ac
Battery reinserted
Selection based on selector inputs
Battery is selected when ac is
removed
AC removal
Automatically selects battery
Automatically selects battery
AC reinserted
Selection based on selector inputs
Selection based on selector inputs
Battery as power source
Sends ALARM signal
Automatically selects ac
Sends ALARM signal
AC as power source
Sends ALARM signal
Sends ALARM signal
Depleted battery condition
Depleted battery condition
ac as Power Source
Depleted Battery Condition
ALARM Signal Active
Selector inputs do not match selector outputs
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23
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SLUS452B – APRIL 2001 – REVISED NOVEMBER 2002
APPLICATION INFORMATION
selector/ALARM timing example
The selector and ALARM timing example in Figure 10 illustrates the battery conditioning support.
NOTE:For manual selection of wall power as the main power source, both the ACPRES and
ACSEL signals must be a logic high.
ACPRES
ACSEL
ACDRV
BATDRV
ALARM
BATTERY
DEPLETE
CONDITION
bq24701 ONLY
UDG–00122
ACSEL
(ACPRES)
tBATSEL
ACDRV
tACSEL
BATDRV
BATDEP< 1 V
t
ACSEL
BATDRV
tBATSEL
ACDRV
UDG–00120
Figure 10. Battery Selector and ALARM Timing Diagram
24
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SLUS452B – APRIL 2001 – REVISED NOVEMBER 2002
APPLICATION INFORMATION
PWM selector switch gate drive
Because the external P-channel MOSFETs (as well as the internal MOSFETs) have a maximum gate-source
voltage limitation of 20 V, the input voltage, VCC, cannot be used directly to drive the MOSFET gate under all
input conditions. To provide safe MOSFET-gate-drive at input voltages of less than 20 V, an intermediate gate
drive voltage rail was established (VSHP). As shown in Figure 11, VSHP has a stepped profile. For VCC
voltages of less than 15 V, VSHP = 0 and the full VCC voltage is used to drive the MOSFET gate. At input
voltages of greater than 15 V, VSHP steps to approximately one-half the VCC voltage. This ensures adequate
enhancement voltage across all operating conditions.
The gate drive voltage, Vgs, vs VCC for the PWM, and ac selector P-channel MOSFETs are shown in Figure 11.
MOSFET GATE DRIVE VOLTAGE
vs
INPUT VOLTAGE
Vgs – Gate Drive – V
15
10
7.5
PWM
ACDRV
4
ACDRV and PWM
0
0
4
7
10
15
20
VCC – Input Voltage – V
25
30
Figure 11
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SLUS452B – APRIL 2001 – REVISED NOVEMBER 2002
TYPICAL CHARACTERISTICS
ERROR AMPLIFIER REFERENCE
vs
JUNCTION TEMPERATURE
BYPASSED 5-V REFERENCE
vs
JUNCTION TEMPERATURE
5.06
5.05
1.248
VREF – 5-V Reference –V
REF2 – Error Amplifier Reference –V
1.250
1.246
1.244
5.04
5.03
5.02
5.01
1.242
5.00
1.240
–40
–20
0
20
40
60
80
TJ – Junction Temperature – _C
4.99
–40
100
–20
Figure 12
0
20
40
60
80
TJ – Junction Temperature – C
100
Figure 13
TOTAL SLEEP CURRENT
vs
JUNCTION TEMPERATURE
OSCILLATOR FREQUENCY
vs
JUNCTION TEMPERATURE
25
300
295
20
f – Oscillator Frequency –kHz
ISLEEP – Battery Sleep Current –µA
VBATTERY = 18 V
15
10
290
285
280
275
5
270
0
–40
–20
0
20
40
60
TJ – Junction Temperature – C
80
100
265
–40
–20
Figure 14
26
0
20
40
60
80
TJ – Junction Temperature – C
Figure 15
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SLUS452B – APRIL 2001 – REVISED NOVEMBER 2002
TYPICAL CHARACTERISTICS
BATTERY CURRENT SET ACCURACY
vs
BATTERY CURRENT SET VOLTAGE
AC CURRENT SET ACCURACY
vs
AC CURRENT SET VOLTAGE
20
25
SRSET Full Scale = 2.5 V
= Max Programmed Current
TJ = 25°C
AC Current Set Accuracy –%
Battery Current Set Accuracy –%
25
15
10
5
0
ACSET Full Scale = 2.5 V
= Max Programmed Current
TJ = 25°C
20
15
10
5
0
0.25 0.50 0.75 1.00 1.25 1.50 1.75 2.00 2.25 2.50
0.25 0.50 0.75 1.00 1.25 1.50 1.75 2.00 2.25 2.50
VACSET – AC Current Set Voltage – V
VSRSET – Battery Current Set Voltage – V
Figure 16
Figure 17
BATTERY IBAT READBACK
vs
(SRP–SRN) VOLTAGE
HALF SUPPLY REGULATOR VOLTAGE
vs
INPUT VOLTAGE
15.0
TJ = 25°C
12.5
20
VHSP – Half Supply –V
IBAT – Current Readback –%
25
15
10
5
10.0
7.5
5.0
2.5
0
25
50
75
100
(SRP–SRN) – Battery Current Sense Voltage – mV
0
6
Figure 18
10
14
18
22
VCC – Input Voltage – V
26
30
Figure 19
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SLUS452B – APRIL 2001 – REVISED NOVEMBER 2002
PARAMETER MEASUREMENT INFORMATION
VCC = 12 V
CL = 1 nF
TJ = 25_C
VCC = 20 V
CL = 1 nF
TJ = 25_C
Figure 20. PWMB Rise and Fall Times
Figure 21. PWMB Rise and Fall Times
BATDRV
BATDRV
VCC = 12 V
TJ = 25_C
ACDRV
VCC = 20 V
TJ = 25_C
ACDRV
ACSEL
ACSEL
Figure 22. Power Source Select Output
Break Before Make
28
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Figure 23. Power Source Select Output
Break Before Make
• DALLAS, TEXAS 75265
PACKAGE OPTION ADDENDUM
www.DataSheet4U.com
www.ti.com
27-May-2005
PACKAGING INFORMATION
Orderable Device
Status (1)
Package
Type
Package
Drawing
Pins Package Eco Plan (2)
Qty
BQ24700PW
NRND
TSSOP
PW
24
BQ24700PWR
NRND
TSSOP
PW
24
BQ24701PW
NRND
TSSOP
PW
24
BQ24701PWR
NRND
TSSOP
PW
24
70
Lead/Ball Finish
MSL Peak Temp (3)
Green (RoHS &
no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
2000 Green (RoHS &
no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
Green (RoHS &
no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
2000 Green (RoHS &
no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
60
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in
a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS) or Green (RoHS & no Sb/Br) - please check
http://www.ti.com/productcontent for the latest availability information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements
for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered
at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame
retardants (Br or Sb do not exceed 0.1% by weight in homogeneous material)
(3)
MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder
temperature.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is
provided. TI bases its knowledge and belief on information provided by third parties, and makes no representation or warranty as to the
accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and continues to take
reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on
incoming materials and chemicals. TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited
information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI
to Customer on an annual basis.
Addendum-Page 1
MECHANICAL DATA
www.DataSheet4U.com
MTSS001C – JANUARY 1995 – REVISED FEBRUARY 1999
PW (R-PDSO-G**)
PLASTIC SMALL-OUTLINE PACKAGE
14 PINS SHOWN
0,30
0,19
0,65
14
0,10 M
8
0,15 NOM
4,50
4,30
6,60
6,20
Gage Plane
0,25
1
7
0°– 8°
A
0,75
0,50
Seating Plane
0,15
0,05
1,20 MAX
PINS **
0,10
8
14
16
20
24
28
A MAX
3,10
5,10
5,10
6,60
7,90
9,80
A MIN
2,90
4,90
4,90
6,40
7,70
9,60
DIM
4040064/F 01/97
NOTES: A.
B.
C.
D.
All linear dimensions are in millimeters.
This drawing is subject to change without notice.
Body dimensions do not include mold flash or protrusion not to exceed 0,15.
Falls within JEDEC MO-153
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