Chapter 12 - Modulation Sources (What and How We Communicate)

Chapter 12 - Modulation Sources (What and How We Communicate)
Modulation Sources
(What and How We Communicate)
12
odulation Sources”—what does that mean? An engineer might simply call this chapter
Baseband. Engineers use that term to distinguish information before it’s used to modulate
a carrier. So, this chapter covers the various kinds of information we impress on RF
(audio, video, digital, remote control) before that information has been moved to some intermediate
frequency (IF) or the desired RF.
Baseband carries the connotation “at or near dc” because the final RF is usually much higher than the
baseband frequency, yet that is misleading. For example, a baseband ATV signal usually extends up to
5 MHz, which is hardly dc. Nonetheless, compared to the operating frequencies (52 to 806 MHz for
broadcast, 420 MHz and higher for amateur) it is practically dc.
Here we will discuss characteristics of the information (such as bandwidth), how we prepare it for
transmission, optimize the transfer and process it after reception.
Nearly all of the processing discussed in this chapter can be implemented with the emerging digitalsignal-processing (DSP) technology. For example, the CLOVER-II system described later in this chapter uses DSP to vary the modulation scheme as required by propagation conditions. Look to the Digital
Signal Processing chapter for further information about DSP techniques.
“M
BANDWIDTH
Whenever information is added to a carrier (we say the carrier is modulated), sidebands are produced.
Sidebands are the frequency bands on both sides of a carrier resulting from the baseband signal varying
some characteristic of the carrier. The modulation process creates two sidebands: the upper sideband
(USB) and the lower sideband (LSB). The width of each sideband is generally equal to the highest
frequency component in the baseband signal. In some modulation systems, the width of the sidebands
may greatly exceed the highest baseband frequency component.
The USB and LSB are mirror images of each other and carry indentical information. Some modulation
systems transmit only one sideband and partially or completely suppress the other in order to conserve
bandwidth.
According to FCC Rules, occupied bandwidth is:
The frequency bandwidth such that, below its lower and above its upper frequency limits, the mean powers
radiated are each equal to 0.5 percent (–23 dB) of the total mean power radiated by a given emission.
In some cases a different relative power level may be specified; for example, –26 dB (0.25%) is used
to define bandwidth in §97.3(a)(8) of the FCC rules.
Modulation Sources (What and How We Communicate)
12. 1
Occupied bandwidth is not always easy for amateurs to determine. It can be measured on a spectrum
analyzer, which is not available to most amateurs. Occupied bandwidth can also be calculated, but the
calculations require an understanding of the mathematics of information theory and are not covered in
this book.
The FCC has defined necessary bandwidth as:
For a given class of emission, the minimum value of the occupied bandwidth sufficient to ensure the
transmission of information at the rate and with the quality required for the system employed, under
specified conditions.
12.2
Chapter 12
Voice Modes
AMPLITUDE MODULATION (AM)
AM voice was the second mode used in Amateur Radio (after Morse code). AM techniques are the
basis for several other modes, such as single-sideband voice and AFSK. This material was supplied by
Jeff Bauer, WA1MBK.
AM is a mixing process. When RF and AF signals are combined in a standard AM modulator, four output
signals are generated: the original RF signal (carrier), the original AF signal, and two sidebands, whose
frequencies are the sum and difference of the original RF and AF signals, and whose amplitudes are proportional to that of the original AF signal. The sum component is called the upper sideband (USB). It is direct:
A frequency increase of the modulating AF causes a frequency increase in the RF output. The difference
component is called the lower sideband (LSB), which is inverted: A frequency increase in the modulating AF
produces a decrease in the output frequency. The amplitude and frequency of the carrier are unchanged by
the modulation process, and the original AF signal is rejected by the RF output network. The RF envelope
(sum of sidebands and carrier), as viewed on an oscilloscope, has the shape of the modulating waveform.
Fig 12.1B shows the envelope of an RF signal that is 20% modulated by an AF sine wave. The envelope
varies in amplitude because it is the vector sum of the carrier and the sidebands. A spectrum analyzer
or selective receiver will show the carrier to be constant. The spectral photograph also shows that the
bandwidth of an AM signal is twice the highest frequency component of the modulating wave.
An AM signal cannot be frequency multiplied without special processing because the phase/frequency
relationship of the modulating-waveform components would be severely distorted. For this reason, once
an AM signal has been generated, its frequency can be changed only by heterodyning.
All of the information in an AM signal is contained in the sidebands, but two-thirds of the RF power
is in the carrier. If the carrier is
suppressed in the transmitter
and reinserted (in the proper
phase) in the receiver, significant advantages accrue. When
the reinserted carrier is strong
compared to the incoming
double-sideband signal (DSB),
exalted carrier reception is
achieved, and distortion from
(A)
selective fading is reduced
greatly. A refinement called
synchronous detection uses a
PLL to reject interference.
Suppressing the carrier also
eliminates the heterodyne interference common with adjacent AM signals. More important, eliminating the carrier
increases overall transmitter
(B)
efficiency. Transmitter power
Fig 12.1—Electronic displays of AM signals in the frequency and
requirements are reduced by
time domains. A shows an unmodulated carrier or single-tone SSB
66%, and the remaining 34%
signal. B shows a full-carrier AM signal modulated 20% with a sine
has a light duty cycle.
wave.
Modulation Sources (What and How We Communicate)
12. 3
Mathematics of AM
AM can happen at low levels (as in a driver or predriver stages of a transmitter) or high levels, in the
final output stage. The numbers are consistent for both methods.
For example, to 100% modulate a 10 W RF carrier, 5 W of clean AF is required from the modulator.
Good engineering calls for a 25% overdesign; thus 6.25 W of AF allows plenty of system headroom. The
circuitry can then “loaf along” at the 100% level.
Overmodulation
Overmodulation occurs when more audio is impressed on a carrier than is needed for 100% modulation. It is also known as flattopping. Overmodulation causes distortion of the information conveyed and
produces splatter (spurious emissions) on adjacent frequencies. Splatter interferes with others sharing
our already-crowded bands: Prevent overmodulation at all times.
Years ago amateurs used ingenious ways to detect and prevent or control overmodulation. Nowadays
with solid-state, large-scale integration (LSI) chips and microprocessor control, bullet-proof
overmodulation prevention can be designed into transmitters. The most familiar method is called ALC,
for automatic level control.
Although modern use of full-carrier AM on the amateur bands is very limited, there is a core group
of AM aficionados experimenting with pulse duration modulation (PDM). This system was pioneered
in AM broadcast transmitters.
This form of high-level modulation differs from conventional AM in that the PDM modulator operates
in switching mode, with audio information contained during on-pulses. The audio amplitude is therefore
determined by the duty cycle of the modulator or switching tube. Those interested in further reading on
the topic should look in William Orr’s (W6SAI) Radio Handbook (published by Howard W. Sams and
Co) and the AM Press/Exchange (for contact information, see the Address List in the References
chapter).
Balanced Modulators
The carrier can be suppressed or nearly eliminated by using a balanced modulator or an extremely
sharp filter. Contemporary amateur transmitters often use both methods.
The basic principle of any balanced modulator is to introduce the carrier in such a way that only the
sidebands will appear in the output. The balanced-modulator circuit chosen by a builder depends on
constructional considerations, cost and the active devices to be employed.
In any balanced-modulator circuit, there is (theoretically) no output when no audio signal is applied.
When audio is applied, the balance is upset, and one branch conducts more than the other. Since any
modulation process is the same as “mixing,” sum and difference frequencies (sidebands) are generated.
The modulator is not balanced for the sidebands, and they appear in the output.
SINGLE-SIDEBAND (SSB)
A further improvement in communications effectiveness can be obtained by transmitting only one of
the sidebands. When the proper receiver bandwidth is used, a single-sideband (SSB) signal will show
an effective gain of up to 9 dB over an AM signal of the same peak power. Because the redundant
information is eliminated, the required bandwidth of an SSB signal is half that of a comparable AM or
DSB emission. Unlike DSB, the phase of the local carrier generated in the receiver is unimportant.
Table 12.1 shows the qualities of a good SSB signal.
SSB Generation: The Filter Method
If the DSB signal from the balanced modulator is applied to a narrow band-pass filter, one of the
12.4
Chapter 12
sidebands can be greatly attenuated. Because a filter cannot have infinitely steep skirts,
Parameter
Suggested Standard
the response of the filter must
Carrier suppression
At least 40-dB below PEP
begin to roll off within about
Opposite-sideband suppression
At least 40-dB below PEP
300 Hz of the phantom carrier
Hum and noise
At least 40-dB below PEP
to obtain adequate suppression
Third-order intermodulation distortion
At least 30-dB below PEP
Higher-order intermodulation distortion At least 35-dB below PEP
of the unwanted sideband. This
Long-term frequency stability
At most 100-Hz drift per hour
effect limits the ability to transShort-term frequency stability
At most 10-Hz P-P deviation in
mit bass frequencies, but those
a 2-kHz bandwidth
frequencies have little value in
voice communications. The filter rolloff can be used to obtain an additional 20 dB of carrier suppression. The bandwidth of an SSB
filter is selected for the specific application. For voice communications, typical values are 1.8 to 3.0 kHz.
Fig 12.2 illustrates two variations of the filter method of SSB generation. In A, the heterodyne
oscillator is represented as a simple VFO, but may be a premixing system or synthesizer. The scheme
at B is perhaps less expensive than that of A, but the heterodyne-oscillator frequency must be shifted
when changing sidebands in order to maintain dial calibration.
The ultimate sense (direct or inverted) of the final output signal is influenced as much by the relationship
of the heterodyne oscillator frequency to the fixed SSB frequency as by the filter or carrier frequency
selection. The heterodyne-oscillator frequency must be chosen to allow the best image rejection. This consideration requires that the heterodyne-oscillator frequency be above the fixed SSB frequency on some bands
and below it on others. To reduce circuit complexity, early amateur filter-method SSB transmitters used a
9-MHz IF and did not include a sideband switch. The result was that the output was LSB on 160, 75 and 40
m, and USB on the higher bands. This convention persists today, despite the flexibility of most modern
amateur SSB equipment. Appropriate filtering methods and
filters for SSB generation are
discussed in the Filters chapter.
Table 12.1
Guidelines for Amateur SSB Signal Quality
SSB Generation: The
Phasing Method
Fig 12.3 shows another
method to obtain an SSB signal.
The audio and carrier signals are
each split into equal components
with a 90º phase difference
(called quadrature) and applied
to balanced modulators. When
the DSB outputs of the modulators are combined, one sideband
is reinforced and the other is canceled. The figure shows sideband selection by means of transposing the audio leads, but the
same result can be achieved by
switching the carrier leads.
The phase shift and ampli-
Fig 12.2—Block diagrams of filter-method SSB generators. They differ
in the manner that the upper and lower sideband are selected.
Modulation Sources (What and How We Communicate)
12. 5
Fig 12.3—Block diagram of a phasing SSB generator.
tude balance of the two channels must be very accurate if the
unwanted sideband is to be adequately attenuated. Table 12.2
shows the required phase accuracy of one channel (AF or RF) for
various levels of opposite sideband suppression. The numbers
given assume perfect amplitude balance and phase accuracy in the
other channel.
The table shows that a phase accuracy of ±1º is required to
satisfy the criteria tabulated at the beginning of this chapter. It is
difficult to achieve this level of accuracy over the entire speech
band. Note, however, that speech has a complex spectrum with a
large gap in the octave from 700 to 1400 Hz. The phase-accuracy
tolerance can be loosened to ±2º if the peak deviations can be
made to occur within that spectral gap.
The major advantage of the phasing system is that the SSB
signal can be generated at the operating frequency without the
need for heterodyning. Phasing can be used to good advantage
even in fixed-frequency systems. A loose-tolerance (±4º) phasing
exciter followed by a simple two-pole crystal filter can generate
a high-quality signal at very low cost.
Table 12.2
Unwanted Sideband
Suppression as a Function of
Phase Error
Phase Error
(deg.)
0.125
0.25
0.5
1.0
2.0
3.0
4.0
5.0
10.0
15.0
20.0
30.0
45.0
Suppression
(dB)
59.25
53.24
47.16
41.11
35.01
31.42
28.85
26.85
20.50
16.69
13.93
9.98
6.0
Audio Phasing Networks
It would be difficult to design a two-port network having a quadrature (90º) phase relationship
between input and output with constant-amplitude response over a decade of bandwidth. A practical
approach, pioneered by Robert Dome, W2WAM, is to use two networks having a differential phase shift
of 90º. This differential can be closely maintained in a simple circuit if precision components are used.
Numerous circuits have been developed to synthesize the required 90º phase shift electronically.
Active-filter techniques are used in many of these systems; use precision components for good results.
RF Phasing Networks
If the SSB signal is to be generated at a fixed frequency, the RF phasing problem is trivial; any method
that produces the proper phase shift can be used. If the signal is produced at the operating frequency,
problems similar to those in the audio networks must be overcome.
A differential RF phase shifter is shown in Fig 12.4. The amplitudes of the quadrature signals won’t
12.6
Chapter 12
be equal over an entire phone
band, but this is of little consequence as long as the signals
are strong enough to saturate
the modulators.
Where percentage bandwidths are small, such as in the
144.1- to 145-MHz range, the RF
phase shift can be obtained conFig 12.4—A simple RF phase shifter using transmission lines. It is
veniently with transmission-line practical at VHF and UHF. Examples: If L1 and L2 are made from
RG-174, L1 is 69.1 inches longer than L2 at 28.5 MHz. 13.7 inches
methods. If one balanced-modulonger at 144.2 MHz and 8.86 inches longer at 222.1 MHz.
lator feed line is made an electrical quarter wavelength longer
than the other, the two signals
will be 90º out of phase. (It is
important that the cables be
properly terminated.)
One method for obtaining a
90º phase shift over a wide
bandwidth is to generate the
quadrature signals at a fixed frequency and heterodyne them individually to any desired operating frequency. Quadrature
hybrids having multioctave
bandwidths are manufactured
commercially, by Mini-Circuits
Labs and others.
Another practical approach
uses two VFOs in a masterslave PLL system. Many phase
Fig 12.5—A block diagram of a PLL phase-shifting system that can
detectors lock the two signals
in phase quadrature. A doubly maintain quadrature (90° phase difference) over a wide frequency
range. The doubly balanced mixer is used as a phase detector.
balanced mixer also has this
property. One usually thinks of
a PLL as having a VCO locked to a reference signal, but a phase differential can be controlled independently of the oscillator. The circuit in Fig 12.5 illustrates this principle. Two digital phase shifters are
sketched in Fig 12.6. If ECL ICs are used, this system can work over the entire HF spectrum.
Independent-Sideband (ISB)
If two SSB exciters, one USB and the other LSB, share a common carrier oscillator, two channels of
information can be simultaneously transmitted from one antenna. Methods for ISB generation in filter
and phasing transmitters are shown in Fig 12.7.
The most obvious amateur application for ISB is the transmission of SSTV with simultaneous audio
commentary. On the VHF bands, other combinations are possible, such as voice and code or SSTV and RTTY.
Amplitude Compandored Single Sideband (ACSSB)
When SSB was tried in the Land Mobile Service, several problems arose. One was that users (who are
Modulation Sources (What and How We Communicate)
12. 7
not trained operators) couldn’t
master the control known as
CLARIFIER to land-mobile users
or receiver incremental tuning,
RIT, to amateurs. In addition,
users were annoyed by SSB’s
fading and noise performance,
compared to that of FM.
So, to get the spectrum savings of SSB over FM, LandMobile Service engineers came
up with a form of SSB that satisfied the users accustomed to FM.
At present, there is almost no
amateur use of this modulation.
Fig 12.6—Digital RF phase-shift networks. Circuit A uses JK flipflops; B uses D flip-flops. The carrier frequency must be
quadrupled before processing.
Fig 12.7—Independent-sideband generators. A shows a filter system, B a phasing system. The “RF
combiner” may be either a hybrid combiner or a summing amplifier.
12.8
Chapter 12
FREQUENCY MODULATION (FM)
When the frequency of the carrier is varied in accordance with the variations in a modulating signal,
the result is frequency modulation (FM). Varying the phase of the carrier current is called phase modulation (PM). Frequency and phase modulation are not independent, since the frequency cannot be varied
without also varying the phase, and vice versa. This section was written by Dean Straw, N6BV.
The primary advantage of FM is its ability to produce a high signal-to-noise ratio when receiving a
signal of only moderate strength. This has made FM popular for mobile communications services and
high-quality broadcasting. However, because of the wide bandwidth required and the distortion suffered
in skywave propagation, the use of FM has generally been limited to frequencies higher than 29 MHz.
When compared to AM or SSB, FM has some impressive advantages for VHF operation. In an FM
transmitter, modulation takes place in a low-level stage. Amplifiers following the modulator can be
operated Class C for best efficiency, since operation need not be linear. The frequency tolerances needed
for channelized FM operation are much less severe than for SSB, helping to keep cost down.
The effectiveness of FM and PM for communication purposes depends almost entirely on the methods
used for receiving. If the FM receiver responds to frequency and phase changes but is insensitive to
amplitude changes, it can discriminate against many forms of noise.
Fig 12.8 is a representation of frequency modulation. When an audio modulating signal is applied, the
carrier frequency is increased during one half cycle of the modulating signal and decreased during the
half cycle of opposite polarity. In this figure RF cycles occupy less
time (higher frequency) when the modulating signal is positive,
and more time (lower frequency) when the modulating signal is
negative. The change in the carrier frequency is called frequency
deviation and is proportional to the instantaneous amplitude of the
modulating signal. The deviation is small when the instantaneous
amplitude of the modulating signal is small and is greatest when
the modulating signal reaches its peak, either positive or negative.
Phase Modulation (PM)
If the phase of the current in a circuit shifts there is an instantaneous
frequency change during the time the phase is shifting. The amount
of frequency change is directly proportional to how rapidly the phase
is shifting and to the total amount of the phase shift. The rapidity of
the phase shift is directly proportional to the frequency of the modulating signal. In a properly operating PM system, the amount of phase
shift is proportional to the instantaneous amplitude of the modulating
signal. Phase modulators have a built-in preemphasis, where deviation increases with modulating frequency.
FM AND PM SIDEBANDS
The sidebands generated by FM and PM occur at integral multiples of the modulating frequency on either side of the carrier.
This is in contrast to AM, where a modulating frequency will
produce a single set of sidebands on either side of the carrier
frequency. An FM or PM signal therefore inherently occupies a
wider channel than AM. The number of additional sidebands that
occur in FM and PM depend on the relationship between the
modulating frequency and the frequency deviation. The ratio
Fig 12.8—Graphical representation of frequency modulation. In
the unmodulated carrier (A) each
RF cycle occupies the same
amount of time. When the modulating signal (B) is applied, the
radio frequency is increased and
decreased according to the
amplitude and polarity of the
modulating signal (C).
Modulation Sources (What and How We Communicate)
12. 9
between the frequency deviation, in hertz, and the modulating frequency, also in hertz, is called the
modulation index.
χ=
D
=φ
m
(1)
where
χ = modulation index
D = peak deviation (1/2 difference between maximum and minimum frequency)
m = modulation frequency in hertz
φ = phase deviation in radians (a radian = 180°/π or approximately 57.3°).
For example, the maximum frequency deviation in an FM transmitter is 3000 Hz either side of the
carrier frequency. The modulation index when the modulation frequency is 1000 Hz is 3000/1000 = 3.0.
At the same deviation with 3000 Hz modulation, the index would be 1; at 100 Hz it would be 30 and so
on.
Given a constant input level to the modulator, in PM the modulation index is constant regardless of
the modulating frequency. In FM it varies with the modulating frequency, as shown above. In an FM
system the ratio of the maximum carrier-frequency deviation to the highest modulating frequency used
is called the deviation ratio. Thus
deviation ratio =
D
M
(2)
where
D = peak deviation
M = maximum modulation
frequency in hertz.
The deviation ratio used
above 29 MHz for narrow-band
FM is 5000 Hz (maximum deviation) divided by 3000 Hz
(maximum modulating frequency) or 1.67.
Fig 12.9 shows how the
amplitudes of the carrier and
the various sidebands vary
with the modulation index for
single-tone modulation. The
first pair of sidebands are displaced from the carrier by an
amount equal to the modulating frequency, the second by
twice the modulating frequency, and so on. For example, if the modulating frequency is 2000 Hz and the
carrier frequency is 29,500
kHz, the first sideband pair is
12.10
Chapter 12
Fig 12.9—Amplitude variation of the carrier and sideband pairs
with modulation index. This is a graphical representation of mathematical functions developed by F. W. Bessel. Note that the carrier
completely disappears at modulation indexes of 2.405, 5.52 and
8.654.
at 29,498 and 29,502 kHz, the second pair is at 29,496 and 29,504 kHz, the third at 29,494 and
29,506 kHz, and so on. The amplitudes of these sidebands depend on the modulation index, not on
the frequency deviation.
The carrier strength varies with the modulation index—at a modulation index of 2.405, the
carrier disappears entirely. As the index is raised further, the carrier level becomes negative, since
its phase is reversed compared to the phase without modulation. In FM and PM the energy going
into the sidebands is taken from the carrier—the total power remains the same regardless of the
modulation index. Since there is no change in amplitude with modulation, an FM or PM signal can
be amplified without distortion by an ordinary Class-C amplifier, either as a straight-through
amplifier or frequency-multiplier stage.
If the modulated signal is passed through one or more frequency multipliers, the modulation index is
multiplied by the same factor as the carrier frequency. For example, if modulation is applied on 3.5 MHz
and the final output is on 28 MHz, the total frequency multiplication is eight times. If the frequency
deviation is 500 Hz at 3.5 MHz, it will be 4000 Hz at 28 MHz. Frequency multiplication offers a means
for obtaining practically any desired amount of frequency deviation, whether or not the modulator itself
is capable of giving that much deviation without distortion.
If the modulation index (with single-tone modulation) does not exceed 0.6 or 0.7, the most important
extra sideband, the second, will be at least 20 dB below the unmodulated carrier level. This represents
an effective channel width about equal to an AM signal. The energy in speech is distributed among many
audio frequencies. On average, the modulation index for any one frequency component is smaller than
that for a single audio tone having the same peak amplitude. Thus, the effective modulation index for
speech can be somewhat higher while retaining the same average bandwidth. The rule-of-thumb for
determination of bandwidth requirements for an FM system using narrow-band (5 kHz deviation)
modulation is
Bn = 2 (M + D)
(3)
where
Bn = necessary bandwidth in hertz
M = maximum modulation frequency in hertz
D = peak deviation in hertz.
For narrow-band FM, the bandwidth equals 2 × (3000 + 5000) = 16000 Hz. Additional bandwidth may
be needed to compensate for cumulative errors in the transmitter and receiver frequencies.
FM vs Phase Modulation (PM)
FM cannot be applied to an amplifier stage, but phase modulation (PM) can. PM is therefore readily
adaptable to transmitters employing oscillators of high stability, such as the crystal-controlled oscillators. The amount of phase shift that can be obtained with good linearity yields a maximum practicable
modulation index of about 0.5. Because phase shift is proportional to the modulating frequency, this
index can be used only at the highest frequency present in the modulating signal, assuming that all
frequencies will at one time or another have equal amplitudes.
The frequency response of the speech-amplifier system above 3000 Hz must be sharply attenuated to
prevent splatter on adjacent channels. Due to its inherent preemphasis, PM received on an FM receiver
sounds “tinny.” The audio must be processed for PM to have the same modulation-index characteristic
as an FM signal. The speech-amplifier frequency-response curve is thus shaped so the output voltage is
inversely proportional to frequency over most of the voice range. When this is done the maximum
modulation index can only be used below a relatively low audio frequency, perhaps 300 to 400 Hz in
voice transmission, and must decrease in proportion to an increase in frequency. The net result is that
Modulation Sources (What and How We Communicate)
12. 11
the maximum linear frequency deviation is only one or two hundred hertz. In order to increase the
deviation up to narrowband level, we must typically multiply the frequency by eight or more.
GENERATING FM
Direct FM
A simple circuit for producing direct FM in amateur transmitters is the reactance modulator. An
active device is connected to the RF tank circuit of an oscillator to act as a variable inductance or
capacitance. Fig 12.10A is a representative circuit using a MOSFET. This modulator acts as
though an inductance were connected across the tank. The frequency increases in proportion to the
amplitude of the current in this modulator. If the modulated oscillator is free running, it must
usually be operated on a relatively low frequency to maintain good carrier stability. Fig 12.10B
shows how a varactor may be used to FM a crystal oscillator directly. The supply voltage for either
modulator and oscillator should be regulated to reduce residual FM. The oscillator frequency is
multiplied up to the final output frequency.
In many modern frequency-synthesized transceivers, a VCO used in one of the phase-locked loops
(PLL) is often frequency modulated directly. A PLL consists of a phase detector, a filter, a dc amplifier
and a voltage-controlled oscillator (VCO). See Fig 12.11. The VCO runs at a frequency close to that
desired when the loop is in lock. The phase detector produces an error voltage if any frequency difference
exists between the VCO divided by the variable divider N and the reference signal. The error voltage
is applied to the VCO to keep it
locked on the carrier frequency
when there is no modulation
present. The loop bandwidth of
the PLL is made narrow enough
so that the audio can change the
VCO frequency, while the PLL
Fig 12.10—At A, reactance modulator using a high-transconductance MOSFET. At B, reactance modulator using a varactor diode.
12.12
Chapter 12
Fig 12.11—Simple phase-locked
loop (PLL) where VCO is FMed
directly. The loop filter is designed to be narrow enough so
that the loop will lock onto the
desired channel frequency,
while audio frequencies will
modulate the VCO outside the
loop bandwidth.
still keeps the unmodulated carrier frequency on-channel.
Indirect FM
The same type of reactance-modulator circuit used to vary the tuning of an oscillator tank in direct
FM can be used to vary the tuning of an amplifier tank. See Fig 12.12A. This varies the phase of the tank
current to create phase modulation. When audio shaping is used in the speech amplifier, an FM-compatible signal will be generated by the phase modulator. The phase shift that occurs when a circuit is
detuned from resonance depends on the amount of detuning and the Q of the circuit. The higher the Q,
the smaller the amount of detuning needed to secure a given number of degrees of phase shift. Since
reactance modulation of an amplifier stage results in simultaneous amplitude modulation, this must be
eliminated using succeeding Class-C limiting stages.
Speech Processing for FM
Several forms of speech processing produce worthwhile improvements in FM system performance.
The peak amplitude of the audio signal applied to an FM or PM modulator should be limited so that
transmitter cannot be driven into overdeviation. Peak limiting is often maintained using a simple audio
clipper between the speech amplifier and modulator. An audio low-pass filter with a cut-off frequency
between 2.5 and 3 kHz eliminates harmonics produced by the clipper. Since excessive clipping can cause
severe distortion of a voice signal, a more effective audio processor consists of a compressor followed
by a clipper and low-pass filter.
An audio shaping network called preemphasis is added to an FM
transmitter to attenuate the lower audio frequencies, spreading out
the energy evenly in the audio band. Preemphasis applied to an FM
transmitter gives the deviation characteristic of PM. The reverse
process, called deemphasis, is used at the receiver to restore the audio
to its original relative proportions. See Fig 12.12B and C.
RECEPTION OF FM SIGNALS
A block diagram of an FM receiver is shown in Fig 12.13B. The
Fig 12.12— At A, a phase-shifter
type of phase modulator. At B,
preemphasis and at C,
deemphasis circuits.
Fig 12.13—At A, block diagram of an AM receiver. At B, an FM
receiver. Dark borders outline the sections that are different in the
FM set.
Modulation Sources (What and How We Communicate)
12. 13
FM receiver employs a wide-bandwidth filter and an FM detector, and has one or more limiter stages
between the IF amplifier and the FM detector. The limiter and discriminator stages in an FM set can
eliminate a good deal of impulse noise, except noise that manages to acquire a frequency-modulation
characteristic.
FM receivers exhibit a characteristic known as the capture effect when QRM is present. The loudest
signal received, even if it is only two or three times stronger than other stations on the same frequency,
will be the only transmission demodulated.
Limiters
The circuit in the FM receiver that has the task of chopping
noise and amplitude modulation from an incoming signal is the
limiter. Most types of FM detectors respond to both frequency and
amplitude variations of the signal. Thus, the limiter stages preceding the detector are included so only the desired frequency modulation will be demodulated. This action can be seen in Fig 12.14.
For an amplifier to act as a limiter, the applied voltages are
chosen so that the stage overloads predictably, even with a small
amount of signal input. Limiting action in an FM receiver should
start with an RF input of 0.2 µV or less, so a large amount of gain
is required between the antenna terminal and the limiter stages.
ICs offer simplification of the IF system, as they pack a lot of gain
into a single package.
When sufficient signal arrives at the receiver to start limiting
action, the set quiets—that is, the background noise disappears.
The sensitivity of an FM receiver is rated in terms of the amount
of input signal required to produce a given amount of quieting,
usually 20 dB. Modern receivers achieve 20 dB quieting with 0.15
to 0.5 µV of input signal.
Fig 12.15A shows a two-stage limiter using discrete transistors. The base bias on either transistor may be varied to provide
limiting at a desired level. The input-signal voltage required to
start limiting action is called the limiting knee. This refers to the
point at which collector current ceases to rise with increased input
signal. Modern ICs have limiting knees of 100 mV for the circuit
shown in Fig 12.15B, using the RCA CA3028A or Motorola
MC1550G, or 200 mV for the MC1590G of Fig 12.15C. Because
high-gain ICs contain many active stages a single IC can provide
superior limiting performance compared to most discrete designs.
(A)
(B)
Fig 12.14—At A, input wave form
to a limiter stage shows AM and
noise. At B, the same signal, after
passing through two limiter
stages, is devoid of AM components.
Detectors
The first FM detector to gain popularity was the frequency discriminator. The characteristic of such a detector is shown in
Fig 12.16. When the FM signal has no modulation, and the carrier
is at point 0, the detector has no output. When audio input to the
FM transmitter swings the signal higher in frequency, the rectified
output increases in the positive direction. When the frequency
swings lower, the output amplitude increases in the negative direction. Over a range where the discriminator is linear (shown as
12.14
Chapter 12
Fig 12.16—The characteristic of
an FM discriminator.
Fig 12.15—Typical limiter circuits using (A) transistors, (B) a differential IC, (C) a high-gain linear IC.
Fig 12.17—Typical frequency-discriminator circuit used for FM
detection. T1 is a Miller 12-C45.
Modulation Sources (What and How We Communicate)
12. 15
Fig 12.18—A crystal discriminator, C1 and L1 are resonant at the
IF. C2 is equal in value to C3. C4 corrects any circuit imbalance so
equal amounts of signal are fed to the detector diodes.
the straight portion of the line), the conversion of FM to AM will also
be linear. A practical discriminator circuit is shown in Fig 12.17. Fig 12.19—At A, block diagram
Other Detector Designs
of a PLL demodulator. At B,
complete PLL circuit.
The difficulties often encountered in building and aligning LC
discriminators have inspired research that has resulted in a number of adjustment-free FM detector
designs. The crystal discriminator utilizes a quartz resonator, shunted by an inductor, in place of the
tuned-circuit secondary used in a discriminator transformer. A typical circuit is shown in Fig 12.18.
The PLL
The phase-locked loop (PLL) has made a significant impact on transmitter and receiver design, both
for frequency generation and for modulation/demodulation. It can act as an FM detector in a process
similar to that used for direct-frequency modulation in a transmitter PLL. As the VCO tracks the
frequency of an incoming signal, the voltage at the phase detector output becomes demodulated audio.
See Fig 12.19.
12.16
Chapter 12
Text (Digital) Modes
MORSE TELEGRAPHY (CW)
Telegraphy by on-off keying (OOK, or amplitude-shift keying ASK) of a carrier is the oldest radio
modulation system. It is also known as CW (for continuous wave). While CW is used by amateurs and
other communicators to mean OOK telegraphy by Morse code, parts of the electronics industry use CW
to signify an unmodulated carrier.
This discussion centers on aural reception of CW, but computers are used to send and receive CW as
well. A table of characters and their Morse equivalents appears in the References chapter.
TRANSMITTING
WPM vs Bauds
The speed of Morse telegraphy is usually expressed in WPM, rather than bauds, which are the common
measure in other digital modes. The following formulas relate WPM to bauds:
WPM = 2.4 × dot/s
(4)
WPM = 1.2 × B
(5)
where
WPM = telegraph speed in words per minute
2.4 = a constant calculated by comparing dots per second with plain language Morse code sending the
word “PARIS”
1.2 = a constant calculated by comparing the signaling rate in bauds with plain-language Morse code
sending the word “PARIS”
B = telegraph speed in bauds.
Thus a keying speed of 25 dot/s or 50 bauds is equal to 60 WPM.
Rise Time vs Bandwidth
Keying a carrier on and off produces double (upper and lower) sidebands corresponding to the period of
the keying pulse. A string of dits
at 50 baud will have sidebands at
multiples of 25 Hz above and below the carrier. The rise time of
the pulses affects the distribution
of power among the sidebands.
As rise time increases or pulse
rate decreases, the bandwidth of
the signal decreases. In addition,
the rise time affects how our ears
hear the signal.
League publications have
long promoted 5-ms rise and
fall times for CW keying envelopes (see Fig 12.20). This
shape is based on an assumed
necessary bandwidth of 150 Hz Fig 12.20—Optimum CW keying waveforms.
Modulation Sources (What and How We Communicate)
12. 17
for a 60-WPM (50-baud) pulse train and an equation relating necessary CW bandwidth to keying speed
in Appendix 6 of the CCIR Radio Regulations and §2.202 of the FCC rules. The relationship is shown
in Fig 12.21.
K is part of the bandwidth equation. Low K values produce softer keying, while high values sound
harder. The CCIR and FCC recommend K = 3 for nonfading circuits and K = 5 for fading circuits with
aural reception. K = 3, is the minimum used for comfortable aural reception, but K = 1 is useful for
machine recognition.
Given-a 150-Hz bandwidth, how fast can we communicate over a fading path? With an occupied
bandwidth of 150 Hz and K = 5, Fig 12.21 yields 36 WPM. Therefore, 5-ms rise and fall times are suitable
for up to 36 WPM on fading circuits and 60 WPM on nonfading circuits.
RECEIVING
For aural reception, a Morse-code OOK RF signal is not completely demodulated to its original dc
pulse, because only thumping would be heard. Instead, the signal is moved (by mixing) down to AF,
usually near 700 Hz.
Proper reception of a Morse-code transmission requires that the receiver bandwidth be at least that of
the necessary bandwidth plus
any frequency error. Thus, if
you have 150-Hz receiver
bandwidth, it would be necessary for you to carefully tune
your receiver to receive a 150Hz-bandwidth transmission. In
practice, it is common to use
500 or 250-Hz IF filters.
Many operators find that it is
easier to distinguish between
multiple signals as the frequency
of the desired signal is lowered
to 500 Hz or less. Some modern
transceivers provide a CW OFFSET adjustment to accommodate
this preference. The same result
can be achieved by adjusting the
RIT control, although the audio
from incoming signals will no
longer match the sidetone with
this technique.
Those who desire a narrower
bandwidth often use audio filters, either an op-amp audio- Fig 12.21—Keying speed vs rise and fall times vs bandwidth for
peak filter or a low-pass fading and nonfading communications circuits. For example, to
switched-capacitor. Such fil- optimize transmitter timing for 25 WPM on a nonfading circuit,
a vertical line from the WPM axis to the K = 3 line. From there
ters may be part of the radio or draw
draw a horizontal line to the rise/fall time axis (approximately
added as accessories. Look in 15 ms). Draw a vertical line from where the horizontal line crosses
the Filters chapter for projects. the bandwidth line and see that the bandwidth will be about 60 Hz.
12.18
Chapter 12
BAUDOT (ITA2) RADIOTELETYPE
The Baudot Code: ITA2
One of the first data communications codes to receive widespread use had five bits (traditionally called
“levels”) to present the alphabet, numerals, symbols and machine functions. In the US, we use International Telegraph Alphabet No. 2 (ITA2), commonly called Baudot, as specified in FCC §97.309(a)(1).
The code is defined in the ITA2 Codes table in the References chapter. In Great Britain, the almostidentical code is called Murray code. There are many variations in five-bit coded character sets, principally to accommodate foreign-language alphabets.
Five-bit codes can directly encode only 25 = 32 different symbols. This is insufficient to encode 26 letters,
10 numerals and punctuation. This problem can be solved by using one or more of the codes to select from
multiple code-translation tables. ITA2 uses a LTRS code to select a table of upper-case letters and a FIGS code
to select a table of numbers, punctuation and special symbols. Certain symbols, such as carriage return, occur
in both tables. Unassigned ITA2 FIGS codes may be used for the remote control of receiving printers. This
scheme can be expanded, as shown by the ASCII-over-AMTOR discussion latter in this chapter.
FCC rules provide that ITA2 transmissions must be sent using start-stop pulses as illustrated in
Fig 12.22. The bits in the figure are arranged as they would appear on an oscilloscope.
Speeds and Signaling Rates
The signaling speeds for all forms of RTTY are those used by the old TTYs: 60, 67, 75 or 100 WPM.
Table 12.3 relates speeds, signaling rates and pulse times. In
practice, the real speeds do not
exactly match their names. The
names have been rounded
through years of common usage. The Signaling Rates table
in the References chapter lists
names, signaling rates and data
patterns for common RTTY
speeds.
There’s a problem specifying signaling speed of RTTY
Fig 12.22—A typical Baudot timing sequence for the letter “D.”
because the length of the start
and stop pulses vary from that
of the data bits. The answer is
Table 12.3
to base the signaling speed on
Baudot Signaling Rates and Speeds
the shortest pulses used. The
Signaling
Data Pulse Stop Pulse Speed
Common
baud is a unit of signaling speed
Rate (bauds) (ms)
(ms)
(WPM)
Name
equal to one pulse (event) per
45.45
22.0
22.0
65.00
Western Union
second. The signaling rate, in
22.0
31.0
61.33
“60 speed”
22.0
33.0
60.61
45 bauds
bauds, is the reciprocal of the
50.00
20.0
30.0
66.67
European;
50 bauds
shortest pulse length. For ex56.92
17.57
25.00
76.68
“75 speed”
ample, the “Western Union,”
17.57
26.36
75.89
57 bauds
“60 speed” and “45 bauds”
74.20
13.47
19.18
100.00
“100 bauds”
13.47
20.21
98.98
74
bauds
speeds all signal at 1/0.022 =
100.0
10.00
15.00
133.33
100 bauds
45.45 bauds.
Modulation Sources (What and How We Communicate)
12. 19
Transmitter Keying
When TTYs and TUs (terminal units) roamed the airwaves, frequency-shift keying (FSK) was the
order of the day. DC signals from the TU controlled some form of reactance (usually a capacitor or
varactor) in a transmitter oscillator stage that shifted the transmitter frequency. Such direct FSK is still
an option with some new radios.
AFSK
Multimode communications processors (MCPs), however, generally connect to the radio AF input and
output, often through the speaker and microphone connectors, sometimes through auxiliary connectors.
They simply feed AF tones to the microphone input of an SSB transmitter or transceiver. This is called
AFSK for “audio frequency-shift keying.” When it is properly designed and adjusted, this method of
modulation cannot be distinguished from FSK on the air.
When using AFSK, make certain that audio distortion, carrier and unwanted sidebands do not cause
interference. Particularly when using the low tones discussed later, the harmonic distortion of the tones
should be kept to a few percent. Most modern AFSK generators are of the continuous-phase (CPFSK)
type. Older types of noncoherent-FSK (NCFSK) generators had no provisions for phase continuity and
produced sharp switching transients. The noise from phase discontinuity caused interference several
kilohertz around the RTTY signal.
Also remember that equipment is withstanding a 100% duty cycle for the duration of a transmission.
For safe operation, it is often necessary to reduce the transmitter power output (25 to 50% of normal)
from that safe for CW operation.
What are Low Tones?
US amateurs customarily use the same modems (2125 Hz mark, 2295 Hz space) for both VHF AFSK
and HF via an SSB transmitter. Because of past problems (when 850-Hz shift was used), some amateurs
use “low tones” (1275 Hz mark, 1445 Hz space). Both high and low tones can be used interchangeably
on the HF bands because only the amount of shift is important. The frequency difference is unnoticed
on the air because each operator tunes for best results. On VHF AFSK, however, the high and low tone
pairs are not compatible.
Transmit Frequency
It is normal to use the lower sideband mode for RTTY on SSB radio equipment. In order to tune to
an exact RTTY frequency, remember that most SSB radio equipment displays the frequency of its
(suppressed) carrier, not the frequency of the mark signal. Review your MCP’s manual to determine the
tones used and calculate an appropriate display frequency. For example, to operate on 14,083 kHz with
a 2125-Hz AFSK mark frequency, the SSB radio display (suppressed-carrier) frequency should be
14,083 kHz + 2.125 kHz = 14,085.125 kHz.
Receiving Baudot
Surplus Baudot-encoded teletypewriters (TTY, sometimes called the “green keys”) were the mainstay
of amateur RTTY from 1946 through around 1977. There are still some mechanical-TTY aficionados,
but most operators use computer-based terminals.
Some of the first popular home computers (VIC-20, Commodore 64, Apple II) were adapted to read
signals from “terminal units” or “TUs” required by TTYs. TUs translated receiver AF output into
20-mA current-loop signals to drive a polar relay in a TTY. An interface would translate the current-loop
signals (or sometimes the receiver AF) to levels appropriate for the computer. Software, unique to each
computer, would then decode the stream of marks and spaces into text. This technology was convoluted
12.20
Chapter 12
in that it required many different interfaces and software
packages to suit the computers
in use. Thankfully, it was soon
replaced by multi-mode communications processors.
MCPs accept AF signals
from a radio and translate them
into common ASCII text or
graphics file formats (see
Fig 12.23). Because the basic
interface is via ASCII, MCPs
are compatible with virtually
any PC running a simple terminal program. There may be
Fig 12.23—A typical MCP station. MCPs can do all available data
modes as well as SSTV and fax.
compatibility problems with
graphics formats, but those are
fairly well standardized. Many
MCPs handle CW, RTTY, ASCII, AMTOR, packet, fax and SSTV—multimode indeed!
AFSK Demodulators
An AFSK demodulator takes the shifting tones from the audio output of a receiver and produces TTY
keying pulses. FM is a common AFSK demodulation method. The signal is first band pass filtered to
remove out-of-band interference and noise. It is then limited to remove amplitude variations. The signal
is demodulated in a discriminator or a PLL. The detector output low pass filtered to remove noise at
frequencies above the keying rate. The result is fed to a circuit that determines whether it is a mark or
a space.
AM (limiterless) detectors, when properly designed, permit continuous copy even when the mark or
space frequency fades out completely. At 170-Hz shift, however, the mark and space frequencies tend
to fade at the same time. For this reason, FM and AM demodulators are comparable at 170-Hz shift.
At wider shifts (say 425 Hz and above), the independently fading mark and space can be used to
achieve an in-band frequency-diversity effect if the demodulator is capable of processing it. To conserve
spectrum, it is generally desirable to stay with 170-Hz shift for 45-baud Baudot and forego the possible
in-band frequency-diversity gain. Keep the in-band frequency-diversity gain in mind, however, for
higher signaling rates that would justify greater shift.
Diversity Reception
Another type of diversity can be achieved by using two antennas, two receivers and a dual demodulator. This setup is not as far fetched as it may sound; some amateurs are using it with excellent results.
One of the antennas would be the normal station antenna for that band. The second antenna could be
either another antenna of the same polarization located at least 3/8-wavelength away, or an antenna of
the opposite polarization located at the first antenna or anywhere nearby. A problem is to get both
receivers on the same frequency without carefully tuning each one. Some RTTY diversity enthusiasts
have located slaved receivers on the surplus market. ICOM produced the IC-7072 Transceiver Unit,
which slaves an IC-720(A) transceiver to an IC-R70 receiver. Other methods could include a computer
controlling two receivers so that both would track.
Two demodulators are needed for this type of diversity. Also, some type of diversity combiner or selector
is needed. Many commercial or military RTTY demodulators are equipped for diversity reception.
Modulation Sources (What and How We Communicate)
12. 21
The payoff for using diversity is a worthwhile improvement in copy. Depending on fading conditions,
adding diversity may be equivalent to raising transmitter power sevenfold (8 dB).
Baudot RTTY Bibliography
Contact information for suppliers named here appears in the References chapter Address List.
Ford, ARRL’s HF Digital Handbook (Newington, CT: ARRL, 1999).
DATACOM, British Amateur Radio Teleprinter Group (BARTG).
Henry, “Getting Started in Digital Communications,” Part 3, QST, May 1992.
Hobbs, Yeomanson and Gee, Teleprinter Handbook, Radio Society of Great Britain.
Ingram, RTTY Today, Universal Electronics, Inc.
Kretzman, The New RTTY Handbook, Cowan Publishing Corp.
Nagle, “Diversity Reception: an Answer to High Frequency Signal Fading,” Ham Radio, Nov 1979,
pp 48-55.
RTTY Journal.
Schwartz, “An RTTY Primer,” CQ magazine, Aug 1977, Nov 1977, Feb 1978, May 1978 and Aug 1978.
Tucker, RTTY from A to Z, Cowan Publishing Corp.
GLOSSARY OF DIGITAL COMMUNICATIONS TERMINOLOGY
ACK—Acknowledgment, the control signal sent to indicate the correct receipt of a transmission block.
Address—A character or group of characters that identifies a source or destination.
AFSK—Audio frequency-shift keying.
ALOHA—A channel-access technique wherein each packet-radio station transmits without first checking to
see if the channel is free; named after early packet-radio experiments at the University of Hawaii.
AMICON—AMSAT International Computer Network—Packet-radio operation on SSC L1 of AMSATOSCAR 10 to provide networking of ground stations acting as gateways to terrestrial packet-radio
networks.
AMRAD—Amateur Radio Research and Development Corporation, a nonprofit organization involved
in packet-radio development.
AMTOR—Amateur teleprinting over –radio, an amateur radioteletype transmission technique employing error correction as specified in several CCIR documents 476-2 through 476-4 and 625. CCIR Rec.
476-3 is reprinted in the Proceedings of the Third ARRL Amateur Radio Computer Networking
Conference, available from ARRL Hq.
ANSI—American National Standards Institute
Answer—The station intended to receive a call. In modem usage, the called station or modem tones
associated therewith.
ARQ—Automatic repeat request, an error-sending station, after transmitting a data block, awaits a reply
(ACK or NAK) to determine whether to repeat the last block or proceed to the next.
ASCII—American National Standard Code for Information Interchange, a code consisting of seven
information bits.
AX.25—Amateur packet-radio link-layer protocol. Copies of protocol specification are available from
ARRL Hq.
Backwave—An unwanted signal emitted between the pulses of an on/off-keyed signal.
Balanced—A relationship in which two stations communicate with one another as equals; that is, neither
is a primary (master) or secondary (slave).
Baud—A unit of signaling speed equal to the number of discrete conditions or events per second. (If the
duration of a pulse is 20 ms, the signaling rate is 50 bauds or the reciprocal of 0.02, abbreviated Bd).
12.22
Chapter 12
Baudot code—A coded character set in which five bits represent one character. Used in the US to refer
to ITA2.
Bell 103—A 300-baud full-duplex modem using 200-Hz-shift FSK of tones centered at 1170 and 2125 Hz.
Bell 202—A 1200-baud modem standard with 1200-Hz mark, 2200-Hz space, used for VHF FM packet
radio.
BER—Bit error rate.
BERT—Bit-error-rate test.
Bit stuffing—Insertion and deletion of 0s in a frame to preclude accidental occurrences of flags other
than at the beginning and end of frames.
Bit—Binary digit, a single symbol, in binary terms either a one or zero.
BLER—Block error rate.
BLERT—Block-error-rate test.
Break-in—The ability to hear between elements or words of a keyed signal.
Byte—A group of bits, usually eight.
Carrier detect (CD)—Formally, received line signal detector, a physical-level interface signal that
indicates that the receiver section of the modem is receiving tones from the distant modem.
CCIR Rec 476-4—The CCIR Recommendation used as the basis of AMTOR and incorporated by
reference into the FCC Rules.
CCIR—International Radio Consultative Committee, an International Telecommunication Union (ITU)
agency.
CCITT—International Telegraph and Telephone Consultative Committee, an ITU agency. CCIR and
CCITT recommendations are available from the UN Bookstore.
Chirp—Incidental frequency modulation of a carrier as a result of oscillator instability during keying.
Collision—A condition that occurs when two or more transmissions occur at the same time and cause
interference to the intended receivers.
Connection—A logical communication channel established between peer levels of two packet-radio
stations.
Contention—A condition on a communications channel that occurs when two or more stations try to
transmit at the same time.
Control field—An 8-bit pattern in an HDLC frame containing commands or responses, and sequence
numbers.
CRC—Cyclic redundancy check, a mathematical operation. The result of the CRC is sent with a transmission block. The receiving station uses the received CRC to check transmitted data integrity.
CSMA—Carrier sense multiple access, a channel access arbitration scheme in which packet-radio
stations listen on a channel for the presence of a carrier before transmitting a frame.
CTS—clear to send, a physical-level interface circuit generated by the DCE that, when on, indicates the
DCE is ready to receive transmitted data (abbreviated CTS).
Cut numbers—In Morse code, shortening of codes sent for numerals.
DARPA—Defense Advanced Research Projects Agency; formerly ARPA, sponsors of ARPANET.
Data set—Modem.
Datagram—A mode of packet networking in which each packet contains complete addressing and
control information. (Compare virtual circuit.)
DCE—Data circuit-terminating equipment, the equipment (for example, a modem) that provides communication between the DTE and the line radio equipment.
Destination—In packet radio, the station that is the intended receiver of the frame sent over a radio link
either directly or via a repeater.
Modulation Sources (What and How We Communicate)
12. 23
Digipeater—A link-level gateway station capable of repeating frames. The term “bridge” is used in
industry.
Domain—In packet radio, the combination of a frequency and a geographical service area.
DTE—Data terminal equipment, for example a VDU or teleprinter.
DXE—In AX.25, Data switching equipment, a peer (neither master nor slave) station in balanced mode
at the link layer.
EASTNET—A series of digipeaters along the US East Coast.
EIA—Electronic Industries Association.
EIA-232-C—An EIA standard physical-level interface between DTE (terminal) and DCE (modem),
using 25-pin connectors.
Envelope-delay distortion—In a complex waveform, unequal propagation delay for different frequency components.
Equalization—Correction for amplitude-frequency and/or phase-frequency distortion.
Eye pattern—An oscilloscope display in the shape of one or more eyes for observing the shape of a serial
digital stream and any impairments.
FADCA—Florida Amateur Digital Communications Association.
FCS—Frame check sequence. (See CRC.)
FEC—Forward error correction, an error-control technique in which the transmitted data is sufficiently
redundant to permit the receiving station to correct some errors.
Field—In packet radio, at the link layer, a subdivision of a frame, consisting of one or more octets.
Flag—In packet switching, a link-level octet (01111110) used to initiate and terminate a frame.
Frame—In packet radio, a transmission block consisting of opening flag, address, control, information,
frame-check-sequence and ending flag fields.
FSK—Frequency-shift keying.
Gateway—In packet radio, an interchange point.
HDLC—High-level data link control procedures as specified in ISO 3309.
Host—As used in packet radio, a computer with applications programs accessible by remote stations.
IA5—International Alphabet No. 5, a 7-bit coded character set, CCITT version of ASCII.
Information field—Any sequence of bits containing the intelligence to be conveyed.
ISI—Intersymbol interference; slurring of one symbol into the next as a result of multipath propagation.
ISO—International Organization for Standardization.
ITA2—International Telegraph Alphabet No. 2, a CCITT 5-bit coded character set commonly called the
Baudot or Murray code.
Jitter—Unwanted variations in amplitude or phase in a digital signal.
Key clicks—Unwanted transients beyond the necessary bandwidth of a keyed radio signal.
LAP—Link access procedure, CCITT X.25 unbalanced-mode communications.
LAPB—Link access procedure, balanced, CCITT X.25 balanced-mode communications.
Layer—In communications protocols, one of the strata or levels in a reference model.
Level 1—Physical layer of the OSI reference model.
Level 2—Link layer of the OSI reference model.
Level 3—Network layer of the OSI reference model.
Level 4—Transport layer of the OSI reference model.
Level 5—Session layer of the OSI reference model.
Level 6—Presentation layer of the OSI reference model.
Level 7—Application layer of the OSI reference model.
12.24
Chapter 12
Loopback—A test performed by connecting the output of a modulator to the input of a demodulator.
LSB—Least-significant bit.
Mode A—In AMTOR, an automatic repeat request (ARQ) transmission method.
Mode B—In AMTOR, a forward error correction (FEC) transmission method.
Modem—Modulator-demodulator, a device that connects between a data terminal and communication
line (or radio). Also called data set.
MSB—Most-significant bit.
MSK—Frequency-shift keying where the shift in Hz is equal to half the signaling rate in bits per second.
NAK—Negative acknowledge (opposite of ACK).
NAPLPS—ANSI X3.110-1983 Videotex/Teletext Presentation Level protocol syntax.
NBDP—Narrow-band direct-printing telegraphy.
NEPRA—New England Packet Radio Association.
Node—A point within a network, usually where two or more links come together, performing switching,
routine and concentrating functions.
NRZI—Nonreturn to zero. A binary baseband code in which output transitions result from data 0s but
not from 1s. Formal designation is NRZ-S (nonreturn-to-zero—space).
Null modem—A device to interconnect two devices both wired as DCEs or DTEs; in EIA RS-232-C
interfacing, back-to-back DB25 connectors with pin-for-pin connections except that Received Data
(pin 3) on one connector is wired to Transmitted Data (pin 3) on the other.
Octet—A group of eight bits.
OOK—On-off keying.
Originate—The station initiating a call. In modem usage, the calling station or modem tones associated
therewith.
OSI-RM—Open Systems Interconnection Reference Model specified in ISO 7498 and CCITT Rec
X.200.
Packet radio—A digital communications technique involving radio transmission of short bursts (frames)
of data containing addressing, control and error-checking information in each transmission.
PACSAT—AMSAT packet-radio satellite with store-and-forward capability.
PAD—Packet assembler/disassembler, a device that assembles and disassembles packets (frames). It is
connected between a data terminal (or computer) and a modem in a packet-radio station (see also
TNC).
Parity check—Addition of noninformation bits to data, making the number of ones in a group of bits
always either even or odd.
PID—Protocol identifier. Used in AX.25 to specify the network-layer protocol used.
PPRS—Pacific Packet Radio Society.
Primary—The master station in a master-slave relationship; the master maintains control and is able to
perform actions that the slave cannot. (Compare secondary.)
Protocol—A formal set of rules and procedures for the exchange of information within a network.
PSK—Phase-shift keying.
RAM—Random access memory.
Router—A network packet switch. In packet radio, a network-level relay station capable of routing
packets.
RS-232-C—See EIA-232-C.
RTS—Request to send, physical-level signal used to control the direction of data transmission of the
local DCE.
RTTY—Radioteletype.
Modulation Sources (What and How We Communicate)
12. 25
RxD—Received data, physical-level signals generated by the DCE are sent to the DTE on this circuit.
Secondary—The slave in a master-slave relationship. Compare primary.
SOFTNET—An experimental packet-radio network at the University of Linkoping, Sweden.
Source—In packet radio, the station transmitting the frame over a direct radio link or via a repeater.
SOUTHNET—A series of digipeaters along the US Southeast Coast.
SSID—Secondary station identifier. In AX.25 link-layer protocol, a multipurpose octet to identify
several packet-radio stations operating under the same call sign.
TAPR—Tucson Amateur Packet Radio Corporation, a nonprofit organization involved in packet-radio
development.
Teleport—A radio station that acts as a relay between terrestrial radio stations and a communications
satellite.
TNC—Terminal node controller, a device that assembles and disassembles packets (frames); sometimes
called a PAD.
TR switch—Transmit-receive switch to allow automatic selection between receive and transmitter for
one antenna.
TTY—Teletypewriter.
TU—Terminal unit, a radioteletype modem or demodulator.
Turnaround time—The time required to reverse the direction of a half-duplex circuit, required by
propagation, modem reversal and transmit-receive switching time of transceiver.
TxD—Transmitted data, physical-level data signals transferred on a circuit from the DTE to the DCE.
UI—Unnumbered information frame.
V.24—A CCITT standard defining physical-level interface circuits between a DTE (terminal) and DCE
(modem), equivalent to EIA RS-232-C.
V.28—A CCITT standard defining electrical characteristics for V.24 interface.
VADCG—Vancouver Amateur Digital Communications Group.
VDT—Video-display terminal.
VDU—Video display unit, a device used to display data, usually provided with a keyboard for data entry.
Videotex—A presentation-layer protocol for two-way transmission of graphics.
Virtual circuit—A mode of packet networking in which a logical connection that emulates a point-topoint circuit is established. (Compare Datagram.)
WESTNET—A series of digipeaters along the US West Coast.
Window—In packet radio at the link layer, the range of frame numbers within the control field used to
set the maximum number of frames that the sender may transmit before it receives an acknowledgment
from the receiver.
X.25—CCITT packet-switching protocol.
12.26
Chapter 12
ASCII
The American National Standard Code for Information Interchange (ASCII) is a coded character set
used for information-processing systems, communications systems and related equipment. Current FCC
regulations provide that amateur use of ASCII shall conform to ASCII as defined in ANSI Standard
X3.4-1977. Its international counterparts are ISO 646-1983 and International Alphabet No. 5 (IA5) as
specified in CCITT Rec V.3.
ASCII uses 7 bits to represent letters, figures, symbols and control characters. Unlike ITA2 (Baudot),
ASCII has both upper- and lower-case letters. A table of ASCII characters is presented as “ASCII
Character Set” in the References chapter.
In the international counterpart code, £ replaces #, and the international currency sign ¤ may replace
$ by agreement of the sender and recipient. Without such agreement, neither £, ¤ nor $ represent the
currency of any particular country.
Parity
While not strictly a part of the ASCII standard, an eighth bit (P) may be added for parity checking.
FCC rules permit optional use of the parity bit. The applicable US and international standards (ANSI
X3.16-1976; CCITT Rec V.4) recommend an even parity sense for asynchronous and odd parity sense
for synchronous data communications. The standards, however, generally are not observed by hams.
Code Extensions
By sacrificing parity, the eighth bit can be used to extend the ASCII 128-character code to 256
characters. Work is underway to produce an international standard that includes characters for all written
languages.
ASCII Serial Transmission
Serial transmission standards for ASCII (ANSI X3.15 and X3.16; CCITT Rec V.4 and X.4) specify
that the bit sequence shall be least-significant bit (LSB) first to most-significant bit (MSB), that is b0
through b6 (plus the parity bit, P, if used).
Serial transmission may be either synchronous or asynchronous. In synchronous transmissions, only
the information bits (and optional parity bit) are sent, as shown in Fig 12.24A.
Asynchronous serial transmission adds a start pulse and a stop pulse to each character. The start pulse
length equals that of an information pulse. The stop pulse may be one or two bits long. There is some
variation, but one stop bit is the convention, except for 110-baud transmissions with mechanical teletypewriters.
Fig 12.24—Typical serial synchronous and asynchronous timing for the ASCII character S.
Modulation Sources (What and How We Communicate)
12. 27
ASCII-over-AMTOR
The superior weak signal performance of
AMTOR, compared to RTTY and HF packet
radio, has made it a popular mode for HF data
networks. AMTOR BBS systems are popular
for passing long-haul traffic. Traffic from VHF
and UHF packet networks is converted into
AMTOR (and more recently PACTOR and
CLOVER) by specially equipped HF BBS
stations. This system combines the best
attributes of several different data transfer
modes: The convenience and short-range high
data rate of VHF/UHF packet is combined with
the high reliability of AMTOR/PACTOR/CLOVER for long-range HF data transfer.
There was a problem with AMTOR relays,
however. The CCIR-476 and CCIR-625 AMTOR
symbol set has no lower-case letters and lacks
many punctuation symbols common in VHF/UHF
packet radio. Therefore, messages routed via
AMTOR can differ from the original in format and
appearance. Differences in the header text of
AMTOR vs packet messages can be particularly
troublesome to automated data-transfer systems.
In late 1991, G3PLX (Peter Martinez) and
W5SMM (Vic Poor) devised an extended
AMTOR character set that contains all of the
printable ASCII symbols (ASCII control characters are not supported). Using this scheme,
AMTOR-delivered messages are indistinguishable from those delivered via ASCII-based
modes (such as packet radio). This “ASCIIover-AMTOR” system uses the generally
unused “blank” character code (“00000” in
Baudot, “1101010” in AMTOR) to toggle between the standard AMTOR character set and
the new “Blank Code Extension” character set,
which includes lower-case letters and ASCII
punctuation symbols.
When two ASCII-over-AMTOR equipped
stations first link, both controllers are set to the
standard CCIR-476/625 character set; uppercase letters are sent and the FIGS code
(AMTOR “0110110”) switches between letters
and numbers. When the first “blank” character
is sent, both stations switch to the new character set. Any following AMTOR letter codes are
assumed to be lower-case letters and FIGS
codes are translated into the new punctuation
symbol set. A second instance of the “blank”
code switches both stations back to the standard AMTOR character set. The expanded
ASCII-over-AMTOR character set is shown in
the Table.
12.28
Chapter 12
ASCII-over-AMTOR
Blank-Code Extension Symbol Set
Bit Code
1000111
1110010
0011101
1010011
1010110
0011011
0110101
1101001
1001101
0010111
0011110
1100101
0111001
1011001
1110001
0101101
0101110
1010101
1001011
1110100
1001110
0111100
0100111
0111010
0101011
1100011
1111000
1101100
1011010
0110110
1011100
1101010
Standard
CCIR-476
Ltrs
Figs
A
B
?
C
:
D
WRU
E
3
F
%
G
@
H
#
I
8
J
*
K
(
L
)
M
.
N
,
O
9
P
0
Q
1
R
4
S
‘
T
5
U
7
V
=
W
2
X
/
Y
6
Z
+
Blank Code
Extension
Ltrs
Figs
a
_
b
c
;
d
WRU
e
f
‘
g
}
h
{
i
j
k
[
l
]
m
>
n
<
o
~
p
q
!
r
$
s
“
t
u
&
v
|
w
x
\
y
^
z
CR
LF
LTRS
FIGS
SP
BLNK
CR
LF
LTRS
FIGS
SP
BLNK
CR
LF
LTRS
FIGS
SP
BLNK
CR = carriage return
LF = line feed
LTRS = shift to letter characters
FIGS = shift to figure characters
SP = space
BLNK = toggle between CCIR-476
CR
LF
LTRS
FIGS
SP
BLNK
and Blank Code
Extension sets.
Notes:
1. The logic state “1” represents the Mark or “Z”
condition, the higher radiated radio frequency.
2. Certain FIGS-case symbols follow CCIR-476 and
common European usage, differing from the “US
TTY” symbols shown in the ITA2 Codes table in
the References chapter. These differences are
necessary to assure international compatibility.
3. The signal “BELL” is not supported because it is
generally a nuisance to operation of otherwise
silent automated message relay stations. If BELL
is required, use FIGS -J in the Blank Extension set.
The ASCII-over-AMTOR extended symbol set is supported by most commercially available AMTOR
controllers and popular BBS software, such as APLINK and AMTOR MBO. The symbol set is backward compatible with stations that do not have the extended capability. A station that is not equipped
with ASCII-over-AMTOR will notice very few differences when receiving these signals except that all
letters will appear to be upper-case and the standard punctuation symbols will be printed.
The ASCII-over-AMTOR extension is remarkably efficient. If no nonBaudot characters are sent,
there is no additional overhead to the transmission. Even if the extended set is sent, far fewer bits are
transmitted than if ASCII were transmitted.
This technique, however, requires an error-correcting code such as AMTOR. The concept would not
work with standard Baudot RTTY because a noise “hit” on a Blank character would result in printing
from the wrong symbol set. The AMTOR error-correcting code is not infallible, but on-the-air use of
ASCII-over-AMTOR has demonstrated that case-errors are very rare. The system works well and is
in daily use by AMTOR BBS stations throughout the world.
ASCII Data Rates
Data-communication signaling rates depend largely on
the medium and the state of
the art when the equipment
was selected. Numerous national and international standards that recommend different data rates, are listed in
Table 12.4. The most-used
rates tend to progress in 2:1
steps from 300 to 9600 bits/s
and in 8 kbits/s increments
from 16 kbits/s upward (see
Table 12.5). For Amateur
Radio, serial ASCII transmissions data rates of 75, 110,
150, 300, 600, 1200, 2400,
4800, 9600, 16000, 19200 and
56000 bits/s are suggested.
Bauds vs Bits Per Second
Table 12.4
Data Transmission Signaling-Rate Standards
Standard
CCIT
V.5
V.6
V.21
V.23
V.34
V.35
V.36
X.3
Signaling Rates (bit/s)
Tolerance
600, 1200, 2400, 4800
±0.01%
Preferred: 600, 1200, 2400, 3600, 4800, 7200, 9600 ±0.01%
Supplementary: 1800, 3000, 4200, 5400, 6000, 6600
7800, 8400, 9000, 10200, 10800
110, 150,
≤200 bit/s
300 (where possible)
≤300 bit/s
600
≤600 bit/s
1200
≤1200 bit/s
75 (backward channel)
≤75 bits
28800, 26400, 24000, 21600, 19200, 16800 or 14400
Preferred: 48000
Recommended for international use: 48000
Certain applications: 56000, 64000, 72000
Packet assembly/disassembly speeds:
50, 75, 100, 134.5, 150, 200, 300, 600, 1200, 1200/75,
1800, 2400, 4800, 9600, 19200, 48000, 56000, 64000
ANSI
X3.1
X3.36
Serial: 75, 150, 300, 600, 1200, 2400, 4800, 7200, 9600
Parallel: 75, 150, 300, 600, 900, 1200
Above 9600 bit/s, signaling rates shall be in integral multiples of
8000 bit/s.
Selected standard rates: 16000, 56000, 1344000 and 1544000
Recognized for international use: 48000
The “baud” is a unit of signaling speed equal to one discrete condition or event per
EIA
second. In single-channel
transmission, such as the FCC RS-269-B (Same as ANSI X3.1)
prescribes for Baudot trans- FED STD
(Same as ANSI X3.36) For foreign communications: 64000
missions, the signaling rate in -1001
-1041
2400,
4800, 9600
bauds equals the data rate in
bits per second. However, the
FCC does not limit ASCII to single-channel transmission. Some digital modulation systems have more
than two (mark and space) states. In dibit (pronounced die-bit) modulation, two ASCII bits are sampled
Modulation Sources (What and How We Communicate)
12. 29
Table 12.5
ASCII Asynchronous Signaling Rates
Bits per
Second
110
150
300
600
1200
2400
4800
9600
19200
Data
Pulse (ms)
9.091
6.667
3.333
1.667
0.8333
0.4167
0.2083
0.1041
0.0520
Stop
Pulse (ms)
18.182
6.667
3.333
1.667
0.8333
0.4167
0.2083
0.1041
0.0520
CPS = characters per second
1
=
START + 7(DATA)+ PARITY + STOP
CPS
10.0
15.0
30.0
60.0
120
240
480
960
1920
WPM
100
150
300
600
1200
2400
4800
9600
19200
at a time. The four possible states for a dibit are 00,
01, 10 and 11. In four-phase modulation, each state
is assigned an individual phase of 0º, 90º, 180º and
270º respectively. For dibit phase modulation, the
signaling speed in bauds is half the informationtransfer rate in bits/s. As the FCC specifies the
digital sending speed in bauds, amateurs may
transmit ASCII at higher information rates by using digital modulation systems that encode more
bits per signaling element. This technology is open
for exploration by Amateur Radio experimenter.
One such example is Clover II.
Amateur ASCII RTTY Operations
On April 17, 1980 the FCC first permitted ASCII
in the Amateur Radio Service. US amateurs have
CPS
× 60
WPM = words per minute =
been slow to abandon Baudot in favor of asynchro6
nous serial ASCII.
= number of 5 - letter - plus - space groups per minute
One cause for resistance is the reasoning that
asynchronous ASCII has two (or three with a parity bit added) more bits than asynchronous Baudot and is usually sent at higher speeds. Thus, it is felt
that the greater data rates and increased bandwidth needed for ASCII would make its reliability less than
that of Baudot. This is true as far as it goes, but does not exhaust the theoretical possibilities, which will
be discussed below.
On the practical side, some amateurs tried ASCII on the air and experienced poor results. In some
cases, this can be traced to the use of modems that were optimized for 45-baud operation. At 110 or 300
bauds, the 45-baud mark and space filters are too narrow.
On the HF bands, speeds above 50 or 75 bauds are subject to intersymbol interference (ISI, slurring
one pulse into the next) from multipath propagation. Multiple paths can be avoided by operating at the
maximum usable frequency (MUF), where there is only one ray path. The amount of multipath delay
varies according to operating frequency with respect to the MUF and path distance. Paths in the 600- to
5000-mile range are generally less subject to multipath than shorter or longer ones. Paths of 250 miles
or less are difficult from a multipath standpoint. As a result, successful operation at the higher ASCII
speeds depends on using the highest frequency possible as well as having suitable modems at both ends
of the circuit.
Returning to the theoretical comparison of Baudot and ASCII, recall that the FCC requires asynchronous (start-stop) transmission of Baudot. This means that the five information pulses must be sent with
a start pulse and a stop pulse, usually of 1.42 times the length of the information pulse. Thus, an
asynchronous Baudot transmitted character requires 7.42 units. In contrast, 7 bits of ASCII plus a parity
bit, a start and a two-unit stop pulse has 11 units.
However, it is possible to send only the 7 ASCII information bits synchronously (without start
and stop pulses), making the number of units that must be transmitted (7 vs 7.42) slightly smaller
for ASCII than for Baudot. Or, it is possible to synchronously transmit 8 bits (7 ASCII bits plus
a parity bit) and take advantage of the error-detection capability of parity. Also, there is nothing
to prevent ASCII from being sent at a lower speed such as 50 or 75 bauds, to make it as immune
to multipath as is 45- or 50-baud Baudot RTTY. So it is easy to see that ASCII can be as reliable
as Baudot RTTY, if care is used in system design.
While 45- or 50-baud RTTY circuits can provide reliable communications, this range of signaling
12.30
Chapter 12
speeds does not make full use of the HF medium. Speeds ranging from 75 to 1200 bauds can be achieved
on HF with error-detection and error-correction techniques similar to those used in AMTOR. Reliable
transmission at higher speeds can be accomplished by means of more sophisticated modes, which are
described later in this chapter.
ASCII Bibliography
ANSI X3.4-1977, “Code for Information Interchange,” American National Standards Institute.
ANSI X3.15-1976, “Bit sequencing of the American National Standard Code for Information Interchange in Serial-by-Bit Data Transmission.”
ANSI X3.16-1976, “Character Structure and Character Parity Sense for Serial-by-Bit Data Communication Information Interchange.”
ANSI X3.25-1976, “Character Structure and Character Parity Sense for Parallel-by-Bit Communication
in American National Standard Code for Information Interchange.”
Bemer, “Inside ASCII,” Interface Age, May, June and July 1978.
CCITT V.3, “International Alphabet No. 5,” International Telegraph and Telephone Consultative Committee, CCITT volumes with recommendations prefixed with the letters V and X are available from
United Nations Bookstore.
CCITT V.4, “General Structure of Signals of International Alphabet No. 5 Code for Data Transmission
over the Public Telephone Network.”
ISO 646-1973 (E), “7-bit Coded Character Set for Information Processing Interchange,” International
Organization for Standardization, available from ANSI.
Mackenzie, Coded Character Sets, History and Development, Addison-Wesley Publishing Co, 1980.
Modulation Sources (What and How We Communicate)
12. 31
AMTOR
RTTY circuits are plagued with problems of fading and noise unless something is done to mitigate
these effects. Frequency, polarization and space diversity are methods of providing two or more simultaneous versions of the transmission to compare at the receiving station. Another method of getting more
than one opportunity to see a given transmission is time diversity. The same signal sent at different times
will experience different fading and noise conditions. Time diversity is the basis of AMTOR or Amateur
Teleprinting Over Radio.
AMTOR always uses two forms of time diversity in either Mode A (ARQ, automatic repeat request)
or Mode B (FEC, forward error correction). In Mode A, a repeat is sent only when requested by the
receiving station. In Mode B, each character is sent twice. In both Mode A or Mode B, the second type
of time diversity is supplied by the redundancy of the code itself.
Since 1983, AMTOR has been part of the US Amateur Radio rules. The rules recognize several
documents that define AMTOR, from 476-2 (1978) to CCIR Rec 476-4 and Rec 625 (1986). Anyone
interested in the design aspects of AMTOR should refer to these recommendations. You may obtain a
complete reprint of Rec 476-3 as part of the Proceedings of the Third ARRL Amateur Radio Computer
Networking Conference, available from ARRL Hq.
Overview
AMTOR is based on SITOR, a system devised in the Maritime Mobile Service as a means of improving
communications between RTTYs using the ITA2 (Baudot) code. The system converts the 5-bit code to
a 7-bit code for transmission such that there are 4 mark and 3 space bits in every character.
The constant mark/space ratio limits the number of usable combinations to 35. ITA2 takes up 32
of the combinations; the 3 remaining are service information signals—α, β and RQ in Table 12.6. The
table also shows several other service signals that are borrowed from the 32 combinations that equate
to ITA2. They are not confused with the message characters because they are sent only by the receiving
station.
Mode B (FEC)
When transmitting to no particular station (for example calling CQ, net operation or bulletin transmissions) there is no (one) receiving station to request repeats. Even if one station were selected, its
ability to receive properly may
not be representative of others
Table 12.6
desiring to copy the signal.
CCIR Rec 625 Service Information Signals1
Mode B uses a simple
Bit No.
forward-error-control (FEC)
Mode
A
(ARQ)
6543210
Mode B (FEC)
technique: it sends each charsignal 1 (CS1) 1100101
acter twice. Burst errors are Control
Control signal 2 (CS1) 1101010
virtually eliminated by delay- Control signal 3 (CS3) 1011001
Control signal 4 (CS4) 0110101
ing the repetition for a period
thought to exceed the duration Control signal 5 (CS5) 1101001
Idle signal β
0110011 Idle signal β
of most noise bursts. In
Idle signal α
0001111 Phasing signal 1, idle signal α
AMTOR, groups of five char- Signal repetition (RQ) 1100110 Phasing signal 2
acters are sent (DX) and then
1 1 represents the mark condition (shown as B in CCIR recommendarepeated (RX). At 70 ms per
tions), which is the higher emitted radio frequency for FSK, the lower
audio frequency for AFSK. 0 represents the space condition (shown as
character, there is 280 ms beY in CCIR recommendations). Bits are numbered 0 (LSB) through 6
tween the first and second
(MSB). The order of bit transmission is LSB first, MSB last.
transmissions of a character.
12.32
Chapter 12
The receiving station tests for the constant 4/3 mark/space ratio and prints only unmutilated DX or RX
characters. If both are mutilated, an error symbol or space prints.
The Information Sending Station (ISS) transmitter must be capable of 100% duty-cycle operation for
Mode B. Thus, it may be necessary to reduce power level to 25% to 50% of full rating.
The Sounds of
Amateur Radio
Listen to calling CQ on AMTOR.
Mode A (ARQ)
This synchronous system,
transmits blocks of three
characters from the Information Sending Station (ISS) to
the Information Receiving
Station (IRS). After each
block, the IRS either acknowledges correct receipt
(based on the 4/3 mark/space
ratio), or requests a repeat.
This cycle repeats as shown
in Fig 12.25.
The station that initiates the
ARQ protocol is known as the
Master Station (MS). The MS
first sends the selective call of
the called station in blocks of Fig 12.25—Typical AMTOR timing. Dark arrows indicate the signal
path from the ISS to the IRS and vice versa. Note the propagation
three characters, listening delays; they determine the minimum and maximum communcations
between blocks. Four-letter distances.
AMTOR calls are normally derived from the first character
and the last three letters of the station call sign. For example, W1AW’s AMTOR call would be WWAW.
The Slave Station (SS) recognizes its selective call and answers that it is ready. The MS now becomes
the ISS and will send traffic as soon as the IRS says it is ready.
When an ISS is done sending, it can enable the other station to become the ISS by sending the threecharacter sequence FIGS Z B. A station ends the contact by sending an “end of communication signal,’’
three Idle Signal Alphas.
On the air, AMTOR Mode A signals have a characteristic “chirp-chirp” sound. Because of the 210/
240-ms on/off timing, Mode A can be used with some transmitters at full power levels.
The W1AW AMTOR Mode B transmission follows the Baudot and ASCII bulletins. A W1AW
schedule appears in the References chapter.
AMTOR Bibliography
S. Ford, ARRL’s HF Digital Handbook (Newington, CT: ARRL, 1999).
CCIR, Recommendation 476-3, “Direct-Printing Telegraph Equipment in the Maritime Mobile Service.” Reprint available from ARRL Hq as part of the Proceedings of the Third ARRL Amateur Radio
Computer Networking Conference.
DATACOM, British Amateur Radio Teleprinter Group (BARTG).
Henry, “Getting Started in Digital Communications,” Part 4, QST, June 1992.
Modulation Sources (What and How We Communicate)
12. 33
Martinez, “AMTOR, An Improved RTTY System Using a Microprocessor,” Radio Communication,
RSGB, Aug 1979.
Martinez, “AMTOR, The Easy Way,” Radio Communication, RSGB, June/July 1980.
Martinez, “AMTOR—a Progress Report,” Radio Communication, RSGB, Sep 1981, p 813.
Meyn, “Operating with AMTOR,” Technical Correspondence, QST, July 1983, pp 40-41.
Newland, “An Introduction to AMTOR,” QST, July 1983.
Newland, “A User’s Guide to AMTOR Operation,” QST, Oct 1985.
12.34
Chapter 12
PACKET RADIO
Data communications is telecommunications between computers. Packet switching is a form of data
communications that transfers data by subdividing it into “packets,” and packet radio is packet switching
using the medium of radio. This description was written by Steve Ford, WB8IMY.
Packet radio has its roots in the Hawaiian Islands, where the University of Hawaii began using the
mode in 1970 to transfer data to its remote sites dispersed throughout the islands. Amateur packet radio
began in Canada after the Canadian Department of Communications permitted amateurs to use the mode
in 1978. (The FCC permitted amateur packet radio in the US in 1980.)
In the first half of the 1980s, packet radio was the habitat of experimenters and those few communicators who did not mind communicating with a limited number of potential fellow packet communicators. In the second half of the decade, packet radio “took off” as the experimenters built a network that
increased the potential number of packet stations that could intercommunicate and thus attracted tens of
thousands of communicators who wanted to take advantage of this potential. Today, packet radio is one
of the most popular modes of Amateur Radio communications, because it is very effective.
It provides error-free data transfer. The receiving station receives information exactly as the transmitting station sends it, so you do not waste time deciphering communication errors caused by interference
or changes in propagation.
It uses time efficiently, since packet bulletin-board systems (PBBSs) permit packet operators to store
information for later retrieval by other amateurs.
It uses the radio spectrum
efficiently, since one radio
channel may be used for multiple communications simultaneously or one radio channel
may be used to interconnect a
number of packet stations to
form a “cluster” that provides
for the distribution of information to all of the clustered
stations. The popular DX
PacketClusters are typical examples (see Fig 12.26).
Each local channel may be
connected to other local channels
to form a network that affords
interstate and international data
communications. This network
can be used by interlinked packet
bulletin-board systems to trans- Fig 12.26—DX PacketClusters are networks comprised of individual
nodes and stations with an interest in DXing and contesting. In this
fer information, messages and
N1BKE is connected to the KC8PE node. If he finds a DX
third-party traffic via HF, VHF, example,
station on the air, he’ll post a notice—otherwise known as a spot—
UHF and satellite links.
which the KC8PE node distributes to all its local stations. In
It uses other stations effi- addition, KC8PE passes the information along to the W1RM node.
W1RM distributes the information and then passes it to the KR1S
ciently, since any packet-radio
node, which does the same. Eventually, WS1O—who is connected
station can use one or more other to the KR1S node—sees the spot on his screen. Depending on the
packet-radio stations to relay size of the network, WS1O will receive the information within
minutes after it was posted by N1BKE.
data to its intended destination.
Modulation Sources (What and How We Communicate)
12. 35
It uses current station transmitting and receiving equipment efficiently, since the same equipment used
for voice communications may be used for packet communications. The outlay for the additional equipment necessary to make your voice station a packet-radio station may be as little as $100. It also allows
you to use that same equipment as an alternative to costly landline data communications links for
transferring data between computers.
The TNC
The terminal node controller—or TNC—is at the heart of every packet station. A TNC is actually a
computer unto itself. It contains the AX.25 packet protocol firmware along with other enhancements
depending on the manufacturer. The TNC communicates with you through your computer or data
terminal. It also allows you to communicate with other hams by feeding packet data to your transceiver.
The TNCs accepts data from
a computer or data terminal and
assembles it into packets (see
Fig 12.27). In addition, it translates the digital packet data into
audio tones that can be fed to a
transceiver. The TNC also
functions as a receiving device,
translating the audio tones into
digital data a computer or terminal can understand. The part
of the TNC that performs Fig 12.27—The functional block diagram of a typical TNC.
this tone-translating function
is known as a modem (see
Fig 12.28).
If you’re saying to yourself,
“These TNCs sound a lot like
telephone modems,” you’re
pretty close to the truth! The
first TNCs were based on telephone modem designs. If Fig 12.28—A block diagram of a typical modem.
you’re familiar with so-called
smart modems, you’d find that
TNCs are very similar.
You have plenty of TNCs to
choose from. The amount of
money you’ll spend depends
directly on what you want to
accomplish. Most TNCs are designed to operate at 300 and
1200 bit/s, or 1200 bit/s exclusively (see Fig 12.29). There
are also TNCs dedicated to
1200 and 9600 bit/s operation,
or 9600 bit/s exclusively. Many Fig 12.29—Four popular 1200 bit/s packet TNCs: (clockwise, from
of these TNCs include conve- bottom left) the MFJ-1270C, AEA PK-88, Kantronics KPC-3 and the
nient features such as personal DRSI DPK-2.
12.36
Chapter 12
packet mailboxes where friends can leave messages when you’re not at home. Some TNCs also include
the ability to easily disconnect the existing modem and substitute another. This feature is very important
if you wish to experiment at different data rates. For example, a 1200 bit/s TNC with a modem disconnect
header can be converted to a 9600 bit/s TNC by disconnecting the 1200 bit/s modem and adding a 9600
bit/s modem.
If you’re willing to spend more money, you can buy a complete multimode communications processor,
or MCP. These devices not only offer packet, they also provide the capability to operate RTTY, CW,
AMTOR, PACTOR, FAX and other modes. In other words, an MCP gives you just about every digital
mode in one box.
TNC Emulation and Internal TNCs
TNC-emulation systems exist for IBM PCs and compatibles. One is known as BayCom, which uses
the PC to emulate the functions of a TNC/terminal while a small external modem handles the interfacing.
BayCom packages are available in kit form for roughly half the price of a basic TNC.
PC owners also have the option of buying full-featured TNCs that mount inside their computers. TNC
cards are available on the market. They are complete TNCs that plug into card slots inside the computer
cabinet. No TNC-to-computer cables are necessary. Connectors are provided for cables that attach to
your transceiver. In many cases, specialized software is also provided for efficient operation.
Transceiver Requirements
Packet activity on the HF bands typically takes place at 300 bit/s using common SSB transceivers. The
transmit audio is fed from the TNC to the microphone jack or auxiliary audio input. Receive audio is
obtained from the external speaker jack or auxiliary audio output. Tuning is critical for proper reception;
a visual tuning indicator—available on some TNCs and all MCPs—is recommended.
These simple connections also work for 1200 bit/s packet, which is common on the VHF bands (2 m
in particular). Almost any FM transceiver can be made to work with 1200 bit/s packet by connecting the
transmit audio to the microphone jack and taking the receive audio from the external speaker (or
earphone) jack.
At data rates beyond 1200 bit/s, transceiver requirements become more rigid. At 9600 bit/s (the
most popular data rate above 1200 bit/s), the transmit audio must be injected at the modulator stage
of the FM transceiver. Receive audio must be tapped at the discriminator. Most 9600 bit/s operators
use modified Amateur Radio transceivers or commercial radios. The Motorola Mitrek transceiver
is a popular choice.
In the mid ’90s amateur transceiver manufacturers began incorporating data ports on some FM voice
rigs. The new “data-ready” radios are not without problems, however. Their IF filter and discriminator
characteristics leave little room for error. If you’re off frequency by a small amount, you may not be able
to pass data. In addition, the ceramic discriminator coils used in some transceivers have poor group
delay, making it impossible to tune them for wider bandwidths. With this in mind, some amateurs prefer
to make the leap to 9600 bit/s and beyond using dedicated amateur data radios such as those manufactured by Tekk and Kantronics (see Address List in References chapter), among others.
Regardless of the transceiver used, setting the proper deviation level is extremely critical. At
9600 bit/s, for example, optimum performance occurs when the maximum deviation is maintained at
3 kHz. Deviation adjustments involve monitoring the transmitted signal with a deviation meter or service
monitor. The output level of the TNC is adjusted until the proper deviation is achieved.
The Sounds of
Amateur Radio
Listen to a 9600 baud packet transmission.
Modulation Sources (What and How We Communicate)
12. 37
Packet Networking
Digipeaters
A digipeater is a packet-radio station capable of recognizing and selectively repeating packet frames.
An equivalent term used in industry is bridge. Virtually any TNC can be used as a single-port digipeater,
because the digipeater function is included in the AX.25 Level 2 protocol firmware. Although the use
of digipeaters is waning today as network nodes take their place, the digipeater function is handy when
you need a relay and no node is available, or for on-the-air testing.
NET/ROM
Ron Raikes, WA8DED, and Mike Busch, W6IXU, developed new firmware for the TNC 2 (and
TNC-2 clones) that supports Levels 3 and 4, the Network and Transport layers of the packet-radio
network. NET/ROM replaces the TNC-2 EPROM (that contains the TAPR TNC-2 firmware) and converts the TNC into a network node controller (NNC) for use at wide- and medium-coverage digipeater
sites. Since it is so easy to convert an off-the-shelf TNC into an NNC via the NET/ROM route, NET/
ROM has become the most popular network implementation in the packet-radio world and has been
installed at most dedicated digipeater stations, thus propelling the standard AX.25 digipeater into packetradio history.
The NET/ROM network user no longer has to be concerned with the digipeater path required to get
from one point to another. All you need to know is the local node of the station you wish to contact. NET/
ROM knows what path is required, and if one path is not working or breaks down for some reason, NET/
ROM will switch to an alternative path, if one exists. You can be assured that NET/ROM is on top of
things, because each NET/ROM node automatically updates its node list periodically, and whenever a
new node comes on the air, the other NET/ROM nodes become aware of the new node’s existence. In
addition to automatic route updating, routing information may also be updated manually by means of
a terminal keyboard or remotely using a packet-radio connection.
Once you are connected to another station via the NET/ROM network, most of your packets get
through because node-to-node packet acknowledgment is used rather than end-to-end acknowledgment.
Besides offering node-to-node acknowledgment, NET/ROM also allows you to build cross-frequency
or cross-band multiport nodes. This is done by installing NET/ROM in two TNCs and connecting their
serial ports together. In addition to providing these sophisticated NNC functions, NET/ROM also provides the standard AX.25 digipeater function.
ROSE
Several years ago, the Radio Amateur Telecommunications Society (RATS) developed a networking
protocol known as RATS Open System Environment, or ROSE. Like networks based on NET/ROM
nodes, the objective of ROSE is to let the network do the work when you’re trying to connect to another
station.
Using a ROSE network is similar to using the telephone. ROSE nodes are frequently referred to as
switches, and each switch has its own address based on the telephone area code and the first 3 digits of
the local exchange. A ROSE switch in one area of Connecticut, for example, may have an address of
203555. 203 is the area code and 555 is the local telephone exchange. The ROSE network uses this
addressing system to create reliable routes for packets (see Fig 12.30).
Unless you wish to set up a ROSE switch of your own, you won’t need special equipment or software
to use the network. You can access a ROSE network today if a switch is available in your area. All you
need to know is the call sign of your local switch and the ROSE address of the switch nearest to any
stations to want to contact.
12.38
Chapter 12
ROSE networks are appearing in many areas of the country. They are especially popular in the southeast and
midAtlantic states. ROSE addresses and system maps are
available from RATS (see References chapter Address List).
Send a business-sized SASE
with your request.
TexNet
TexNet is a high speed, centralized packet networking system developed by the Texas
Fig 12.30—In this hypothetical example, W4FXO, near Charlotte,
Packet Radio Society (TPRS).
North Carolina, uses the ROSE network to establish a connection
Designed for local and regional
to KC4ZC northwest of Richmond, Virginia. All that W4FXO has to
use, TexNet provides AX.25do is issue a connect request that includes his local ROSE switch
(N4APT-3) and the ROSE address of the switch nearest KC4ZC
compatible access on the 2-m
(804949). When the request is sent, the network takes over. In this
band at 1200 bit/s. This allows
example, the connection to KC4ZC is established by using a ROSE
packeteers to use TexNet withswitch in Raleigh.
out investing in additional
equipment or software. The
node-to-node backbones operate in the 70-cm band with data moving through the network at 9600
bit/s. Telephone links are also used to bridge some gaps in the system.
The network offers a number of services to its users. Two conference levels are available by simply
connecting to the proper node according to its SSID. By connecting to W5YR-2, for example, you’ll join
the first conference level. Connecting to W5YR-3 places you in the second level. When you connect to
a conference, you can chat with anyone else on the network in roundtable fashion.
Every TexNet network is served by a single PBBS. By using only one PBBS, the network isn’t bogged
down with constant mail forwarding. Even if you’re some distance from the PBBS, with the speed and
efficiency of TexNet you’ll hardly notice the delay.
TCP/IP
If you’re an active packeteer, sooner or later someone will bring up the subject of TCP/IP—Transmission Control Protocol/Internet Protocol. Of all the packet networking alternatives discussed so far,
TCP/IP is the most popular. In fact, many packeteers believe that TCP/IP may someday become the
standard for amateur packet radio.
Despite its name, TCP/IP is more than two protocols; it’s actually a set of several protocols. Together
they provide a high level of flexible, “intelligent” packet networking. At the time of this writing, TCP/
IP networks are local and regional in nature. For long-distance mail handling, TCP/IP still relies on
traditional AX.25 NET/ROM networks. Even so, TCP/IP enthusiasts see a future when the entire nation,
and perhaps the world, will be linked by high-speed TCP/IP systems using terrestrial microwave and
satellites.
Maintaining a packet connection on a NET/ROM network can be a difficult proposition—especially
if the station is distant. You can only hope that all the nodes in the path are able to relay the packets back
and forth. If the one of the nodes becomes unusually busy, your link to the other station could collapse.
Even when the path is maintained, your packets are in direct competition with all the other packets on
Modulation Sources (What and How We Communicate)
12. 39
the network. With randomly calculated transmission delays, collisions are inevitable. As a result, the
network bogs down, slowing data throughput for everyone.
TCP/IP has a unique solution for busy networks. Rather than transmitting packets at randomly determined intervals, TCP/IP stations automatically adapt to network delays as they occur. As network
throughput slows down, active TCP/IP stations sense the change and lengthen their transmission delays
accordingly. As the network speeds up, the TCP/IP stations shorten their delays to match the pace. This
kind of intelligent network sharing virtually guarantees that all packets will reach their destinations with
the greatest efficiency the network can provide.
With TCP/IP’s adaptive networking scheme, you can chat using the telnet protocol with a ham in a
distant city and rest assured that you’re not overburdening the system. Your packets simply join the
constantly moving “freeway” of data. They might slow down in heavy traffic, but they will reach their
destination eventually. (This adaptive system is used for all TCP/IP packets, no matter what they
contain.)
TCP/IP excels when it comes to transferring files from one station to another. By using the TCP/IP
file transfer protocol (ftp), you can connect to another station and transfer computer files—including
software. As you can probably guess, transferring large files can take time. With TCP/IP, however, you
can still send and receive mail (using the SMTP protocol) or talk to another ham while the transfer is
taking place.
When you attempt to contact another station using TCP/IP, all network routing is performed automatically according to the TCP/IP address of the station you’re trying to reach. In fact, TCP/IP networks are
transparent to the average user.
On conventional NET/ROM networks, access to backbone links is restricted. This isn’t true on TCP/
IP. Not only are you allowed to use the backbones, you’re actually encouraged to do so. If you have the
necessary equipment to communicate at the proper frequencies and data rates, you can tap into the highspeed TCP/IP backbones directly. By doing so, you’ll be able to handle data at much higher rates. This
benefits you and everyone else on the network.
To operate TCP/IP, all you need is a computer (it must be a computer, not a terminal), a 2-m FM
transceiver and a TNC with KISS capability. As you might guess, the heart of your TCP/IP setup is
software. The TCP/IP software set was written by Phil Karn, KA9Q, and is called NOSNET or just NOS.
There are dozens of NOS derivatives available today. All are based on the original NOSNET. The
programs are available primarily for IBM-PCs and compatibles and Macintoshes. You can obtain NOS
software from on-line sources such as the CompuServe HAMNET forum libraries, Internet ftp sites,
Amateur Radio-oriented BBSs and elsewhere. NOS takes care of all TCP/IP functions, using your
“KISSable” TNC to communicate with the outside world. The only other item you need is your own IP
address. Individual IP Address Coordinators assign addresses to new TCP/IP users.
12.40
Chapter 12
PACTOR
PACTOR (PT) is an HF radio transmission system developed by German amateurs Hans-Peter Helfert,
DL6MAA, and Ulrich Strate, DF4KV. It combines the best of AMTOR and packet to make a system that is
superior to both. This description was adapted from PACTOR specifications by the Handbook Editor.
PACTOR is much faster than AMTOR, yet improves on AMTOR’s error-correction scheme. It performs well
under both weak-signal and high-noise conditions. PACTOR/AMTOR BBS stations operating in the US and
other countries are used by amateurs all over the world. The BBSs respond automatically to both PACTOR
and AMTOR calls. PACTOR carries binary data, so it can transfer binary files, ASCII and other symbol sets.
Packet-radio style CRCs (two per packet, 16 bits each) and “ARQ Memory” enable the PT system to reconstruct defective packets by overlaying good and damaged data from different transmissions, which reduces
repeats and transmission time. PT’s overhead is much less than that of AMTOR. PACTOR uses complete call
signs for addressing. The mark/space convention is unnecessary and frequency-shift independent.
Transmission Formats
Information Blocks
All packets have the basic structure shown in Fig 12.31, and their timing is as shown in Table 12.7:
Header: contains a fixed bit pattern to simplify repeat requests, synchronization and monitoring. The
header is also important for the Memory ARQ function. In each packet carrying new information the bit
pattern is inverted.
Data: any binary information. The format is specified in the status word. Current choices are 8-bit
ASCII or 7-bit ASCII (with Huffman encoding). Characters are not broken across packets. ASCII RS
(hex 1E) is used as an IDLE character in both formats.
Status word: see Table 12.8
CRC: The CRC is calculated according to the CCITT standard, for the data, status and CRC.
Table 12.8
PACTOR Status Word
Fig 12.31—PACTOR data packet format.
Bit
0
1
2
3
4
5
6
7
Meaning
Packet count (LSB)
Packet count (MSB)
Data format (LSB)
Data format (MSB)
Not defined
Not defined
Break-in request
QRT request
Data Format Bits
Table 12.7
PACTOR Timing
Object
Packet
CS receive time
Control signals
Propagation delay
Cycle
Length (seconds)
0.96 (200 bd: 192 bits;
100 bd: 96 bits)
0.29
0.12 (12 bits at 10 ms each)
0.17
1.25
Format
ASCII 8 bit
Huffman code
Not defined
Not defined
bit 3
0
0
1
1
bit 2
0
1
0
1
Bits 0 and 1 are used as a packet count; successive
packets with the same value are identified by the
receiver as repeat packets. A modulus-4 count helps
with unrecognized control signals, which are unlikely
in practice.
Modulation Sources (What and How We Communicate)
12. 41
Acknowledgment Signals
The PACTOR acknowledgment signals are similar to those used in AMTOR, except for CS4 (see
Table 12.9). Each of the signals is 12 bits long. The characters differ in pairs in 8 bits (Hamming offset)
so that the chance of confusion is reduced. (One of the most common causes of errors in AMTOR is the
small CS Hamming offset of 4 bits.)
If the CS is not correctly received, the TX reacts by repeating the last packet. The request status can
be uniquely recognized by the 2-bit packet number so that wasteful transmissions of pure RQ blocks are
unnecessary.
Timing
The receiver pause between two blocks is 0.29 s. After deducting the CS lengths, 0.17 s remain (just
as in AMTOR) for switching and propagation delays so that there is adequate reserve for DX operation.
Contact Flow
Listening
In the listen mode, the receiver scans any received packets for a CRC match. This method uses a lot
of computer processing resources, but it’s flexible.
CQ
A station seeking contacts transmits CQ packets in a FEC mode, without pauses for acknowledgment
between packets. The transmit time length number of repetitions and speed are the transmit operator’s
choice. (This mode is also suitable for bulletins and other group traffic.) Once a listening station has
copied the call, the listener assumes the TX station role and initiates a contact. Thus, the station sending
CQ initially takes the RX station role. The contact begins as shown in Table 12.10
Speed Changes
With good conditions, PT’s normal signaling
rate is 200 baud (for a 600-Hz bandwidth), but the
system automatically changes from 200 to 100
baud and back, as conditions demand. In addition,
Huffman coding can further increase the throughput by a factor of 1.7. There is no loss of synchronization speed changes; only one packet is repeated.
When the RX receives a bad 200-baud packet, it
Table 12.9
PACTOR Control Signals
Code
CS1
CS2
CS3
Chars (hex)
4D5
AB2
34B
CS4
D2C
Function
Normal acknowledge
Normal acknowledge
Break-in (forms header of first
packet from RX to TX)
Speed change request
All control signals are sent only from RX to TX.
12.42
Chapter 12
Table 12.10
PACTOR Initial Contact
Master Initiating Contact
Size (bytes)
1
8
6
Content
/Header/SLAVECAL /SLAVECAL/
Speed (bauds)
100
100
200
Slave Response
The receiving station detects a call, determines
mark/space polarity, decodes 100-bd and 200-bd
call signs. It uses the two call signs to determine if it
is being called and the quality of the communication
path. The possible responses are:
First call sign does not match slave’s (Master not
calling this slave)
none
Only first call sign matches slave’s (Master calling
this slave, poor communications)
CS1
First and second call signs both match
the slaves (good circuit, request speed change to
200 bd)
CS4
can acknowledge with CS4. TX immediately assembles the previous packet in 100-baud format and
sends it. Thus, one packet is repeated in a change from 200 to 100 baud.
The RX can acknowledge a good 100-baud packet with CS4. TX immediately switches to 200 baud
and sends the next packet. There is no packet repeat in an upward speed change.
Change of Direction
The RX station can become the TX station by sending a special change-over packet in response to a
valid packet. RX sends CS3 as the first section of the changeover packet. This immediately changes the
TX station to RX mode to read the data in that packet and responds with CS1 and CS3 (acknowledge)
or CS2 (reject).
End of Contact
PACTOR provides a sure end-of-contact procedure. TX initiates the end of contact by sending a
special packet with the QRT bit set in the status word and the call of the RX station in byte-reverse order
at 100 baud. The RX station responds with a final CS.
Modulation Sources (What and How We Communicate)
12. 43
PACTOR II
This new protocol is a significant improvement over PACTOR; yet it is fully compatible with the older
mode. Invented in Germany, PACTOR uses 16PSK to transfer up to 800 bits/s at a 100-baud rate. This
keeps the bandwidth less than 500 Hz. Users believe that PACTOR II is faster and more robust than
CLOVER.
PACTOR II uses a DSP with Nyquist waveforms, Huffman and Markov compression, and powerful
Viterbi decoding to increase transfer rate and sensitivity into the noise level. The effective transfer rate
of text is over 1200 bits/s. Features of PACTOR II include:
•
•
•
•
•
•
•
•
Frequency agility—It can automatically adjust or lock two signals together over a ±100-Hz window.
Powerful data reconstruction based upon computer power—with over 2 MB of available memory.
Cross correlation—applies analog Memory ARQ to acknowledgment frames and headers.
Soft decision making—Uses artificial intelligence (AI) as well as digital information received to
determine frame validity.
Extended data block length—When transferring large files under good conditions, the data length is
doubled to increase the transfer rate.
Automatic recognition of PACTOR I, PACTOR II and so on, with automatic mode switching.
Intermodulation products are canceled by the coding system.
Two long-path modes extend frame timing for long-path terrestrial and satellite propagation paths.
This is a fast, robust mode—possibly the most powerful in the ham bands. It has excellent coding gain
as well. It can also communicate with all earlier PACTOR I systems. Like packet and AMTOR stations,
PACTOR II stations acknowledge each received data block. Unlike those modes, PACTOR II employs
computer logic as well as received data to reassemble defective data blocks into good frames. This
reduces the number of transmissions and increases the throughput of the data.
The Sounds of
Amateur Radio
12.44
Chapter 12
Listen to a PACTOR II QSO in progress.
G-TOR
This brief description has been adapted from “A Hybrid ARQ Protocol for Narrow Bandwidth HF
Data Communication” by Glenn Prescott, WB0SKX, Phil Anderson, W0XI, Mike Huslig, KB0NYK,
and Karl Medcalf, WK5M (May 1994 QEX, pp 12-19).
G-TOR is short for Golay-TOR, an innovation of Kantronics, Inc. It’s a new HF digital-communication mode for the Amateur Service. G-TOR was inspired by HF Automatic Link Establishment (ALE)
concepts and is structured to be compatible with ALE systems when they become available.
The purpose of the G-TOR protocol is to provide an improved digital radio communication capability
for the HF bands. The key features of G-TOR are:
•
•
•
•
•
•
•
•
•
•
Standard FSK tone pairs (mark and space)
Link-quality-based signaling rate: 300, 200 or 100 baud
2.4-s transmission cycle
Low overhead within data frames
Huffman data compression—two types, on demand
Embedded run-length data compression
Golay forward-error-correction coding
Full-frame data interleaving
CRC error detection with hybrid ARQ
Error-tolerant “Fuzzy” acknowledgments
The primary benefit of these innovations is increased throughput—that is, more bits communicated
in less time. This is achieved because the advanced processing features of G-TOR provide increased
resistance to interference and noise and greatly reduce multipath-induced data errors.
The G-TOR protocol is straightforward and relatively easy to implement on existing multimode
TNCs.
Propagation Problems
The miserable propagation conditions characteristic of the HF bands make effective data communication a nightmare. Received signals are often weak and subject to multipath fading; ever-present
interference can impair reception. With digital communication, the human brain cannot help interpret
the signal. Therefore, we need to incorporate great ingenuity into the receiving system. G-TOR uses
modern communication signal processing to help us transmit error-free data via the inherently poor HF
communication medium.
Worldwide HF communication may experience interference, multipath fading, random and burst
noise. For data communication over the HF bands, three factors dominate: available bandwidth, signaling rate and the dynamic time behavior of the channel.
... and Answers
Transmission bandwidths of 500 Hz or less minimize the effects of multipath propagation and manmade interference. G-TOR transmits at 300 baud or less, with maximum separation of 200 Hz, for a bandwidth just slightly greater than 500 Hz.
The FCC does not currently permit symbol rates greater than 300 symbols per second (baud) on most
HF bands. This is a reasonable limit because multipath propagation can become a serious problem with
faster rates.
The HF channel has a characteristic dynamic time behavior: Conditions can change significantly in
a few seconds. This indicates an optimum data-transmission length (usually 1 s or less). G-TOR transModulation Sources (What and How We Communicate)
12. 45
missions are nearly 2 s long because the signal-processing techniques can overcome some propagation
change.
The G-TOR Protocol
Since one of the objectives of this protocol is ease of implementation in existing TNCs, the modulation
format consists of standard tone pairs (FSK), operating at 300, 200 or 100 baud, depending upon channel
conditions. (G-TOR initiates contacts and sends ACKs only at 100 baud.) FSK was chosen for economy
and simplicity, but primarily because many hams already have FSK equipment.
The G-TOR waveform consists of two phase-continuous tones (BFSK) spaced 200 Hz apart (mark =
1600 Hz, space = 1800 Hz); however, the system can still operate at the familiar 170-Hz shift (mark =
2125 Hz, space = 2295 Hz), or with any other convenient tone pairs. The optimum spacing for 300-baud
transmission is 300 Hz, but we trade some performance for a narrower bandwidth.
Each transmission consists of a synchronous ARQ 1.92-s frame and a 0.48-s interval for propagation
and ACK transmissions (2.4 s cycle). All advanced protocol features are implemented in the signalprocessing software.
Synchronous operation increases the system throughput during multipath fading and keeps overhead
to a minimum. Synchronization is performed using the received data and precise timing.
Frame Structures
Data Frames—The basic G-TOR frame structure (see Fig 12.32) uses multiple 24-bit (triple-byte)
words for compatibility with the Golay encoder. Data frames are composed of 72 (300 baud), 48 (200
baud) or 24 (100 baud) data bytes, depending upon channel conditions.
A single byte before the CRC carries command and status information:
status bits 7 and 6: Command
00 - data
01 - turnaround request
10 - disconnect
11 - connect
status bits 5 and 4: Unused
00 - reserved
status bits 3 and 2: Compression
00 - none
01 - Huffman (A)
10 - Huffman (B)
11 - reserved
status bits 1 and 0: Frame no. ID
The error-detection code transmitted with each frame is a 2-byte
cyclic redundancy check (CRC)
code—the same used in AX.25. A
CRC calculation determines if error correction is needed, and another tests the result.
The connect and disconnect
frames are essentially identical in
structure to the data frame and contain the call signs of both stations.
12.46
Chapter 12
Fig 12.32—G-TOR ARQ system timing and frame structure
before interleaving. The data portion may be 69 (300 baud), 45
(200 baud) or 21 (100 baud) bytes depending on the channel
quality.
ACK Frames—G-TOR ACK frames are not interleaved and do not contain error-correction (parity)
bits. There are five different ACK frames:
•
•
•
•
•
Frame received correctly (send next data frame)
Frame error detected (please repeat)
Speed-up
Speed-down
Changeover
The ACK codes are composed of multiple cyclic shifts of a single 15-bit pseudorandom noise (PN)
sequence (plus an extra 0 bit to fill 16 bits). PN sequences have powerful properties that facilitate
identification of the appropriate ACK code, even in the presence of noise and interference. We refer to
this concept as a “fuzzy” ACK, in that it tolerates 3 bit errors within a received ACK frame.
Change-over frames are essentially data frames in which the first 16 bits of data is the ACK changeover
PN code.
Data Compression
Data compression is used to remove redundancy from source data. Therefore, fewer bits are needed to
convey any given message. This increases data throughput and decreases transmission time—valuable features for HF. G-TOR uses run-length coding and two types of Huffman coding during normal text transmissions. Run-length coding is used when more than two repetitions of an 8-bit character are sent. It provides
an especially large savings in total transmission time when repeated characters are being transferred.
The Huffman code works best when the statistics of the data are known. G-TOR applies Huffman A
coding with the upper- and lower-case character set, and Huffman B coding with upper-case-only text.
Either type of Huffman code reduces the average number of bits sent per character. In some situations,
however, there is no benefit from Huffman coding. The encoding process is then disabled. This decision
is made on a frame-by-frame basis by the information-sending station.
Golay Coding
The real power of G-TOR resides in the properties of the (24,12) extended Golay error-correcting
code, which permits correction of up to three random errors in three received bytes. The (24,12) extended
Golay code is a half-rate error-correcting code: Each 12 data bits are translated into an additional 12
parity bits (24 bits total). Further, the code can be implemented to produce separate input-data and paritybit frames.
The extended Golay code is used for G-TOR because the encoder and decoder are simple to implement
in software. Also, Golay code has mathematical properties that make it an ideal choice for short-cycle
synchronous communication:
• The rare property of self-duality makes the code “invertible”; that is, the original data can be recovered
by simply recoding the parity bits.
• Because of the linear block code structure of the Golay code, the encoder and decoder can be implemented using a simple table look-up procedure. An alternative decoder implementation uses the wellknown Kasami decoding algorithm, which requires far less memory than the look-up table.
Error-correction coding inserts some redundancy into each (triple-byte) word so that errors occurring
in the receiving process can be corrected. However, most error-correcting codes are effective at correcting only random errors. Burst errors from lightning or interference exceed the capabilities of most errorcorrecting codes.
Modulation Sources (What and How We Communicate)
12. 47
Interleaving
The conventional solution is called “interleaving.” Interleaving
(the very last operation performed before transmission and first
performed upon reception) rearranges the bit order to randomize
the effects of long error bursts.
The interleaving process reads 12-bit words into registers by
columns and reads 48-bit words out by rows; see Fig 12.33. The
deinterleaver simply performs the inverse, reading the received
data bits into the registers by row and extracting the original data
sequence by reading the columns. If a long burst of errors occurs—say, 12 bits in length—the errors will be distributed into 48
separate 12-bit words before error correction is applied, thus effectively nullifying the long burst. Both data and parity frames are
completely interleaved.
Fig 12.33—Interleaving the bits to
be transmitted.
Hybrid ARQ
G-TOR combines error detection and forward error correction with ARQ. Hybrid-ARQ uses a CRC
to check for errors in every frame. Only when errors are found; does G-TOR use forward error correction
(a relatively slow process) to recover the data.
The half-rate invertible Golay code provides an interesting dimension to the hybrid-ARQ procedure.
With separate data and parity frames, both of which can supply the complete data, G-TOR frames
alternate between data and parity frames.
When the receiver detects an error and requests a retransmission, the sending station sends the complementary portion of the frame (data or parity).
When the complementary frame arrives, it is processed and checked for errors. If it checks, the data
is accepted and a new frame is requested. If it fails the CRC check, the two frames are combined,
corrected and checked.
Using this scheme, two transmissions provide three independent chances to correct any errors. If this
process still fails, a retransmission is requested.
G-TOR Performance
Initial testing with G-TOR was conducted during January 1994, between Lawrence, Kansas, and
Laguna Niguel, California. During these tests, TRACE was set ON at each station, enabling the raw data
display of frames received with and without the aid of forward error correction and interleaving. The
results were somewhat surprising. While PACTOR often dropped in transmission speed from 200 to 100
bauds, G-TOR nearly always operated at 300 bauds. Enough frames were corrected to keep the system
running at maximum speed, regardless of man-made interference and mild multipath conditions. Transfer duration for the entire test files varied from 12 to 27 minutes for PACTOR, but only 5.5 to 7.5 minutes
for all but one G-TOR transfer. G-TOR simply maintained its highest pace better than PACTOR,
resulting in a substantial increase in average throughput.
On-air tests have shown G-TOR to have the ability to “hang in there” when channel conditions get
tough. The time required to send a given binary file tends to be much less for G-TOR than for
PACTOR.
This protocol should continue to be valuable when DSP-based TNCs become widely available.
G-TOR has the essential characteristics to be a useful protocol for years to come.
See “A Comparison of HF Digital Protocols” in Jul 1996 QST for an overview of performance
tradeoffs between the numerous competing protocols available.
12.48
Chapter 12
CLOVER-II
The desire to send data via HF radio at high data rates and the problems encountered when using AX.25
packet radio on HF radio led Ray Petit, W7GHM, to develop a unique modulation waveform and data
transfer protocol that is now called “CLOVER-II.” Bill Henry, K9GWT, supplied this description of the
Clover-II system. CLOVER modulation is characterized by the following key parameters:
• Very low base symbol rate: 31.25 symbols/second (all modes).
• Time-sequence of amplitude-shaped pulses to provide a very narrow frequency spectra. Occupied
bandwidth = 500 Hz at 50 dB below peak output level.
• Differential modulation between pulses.
• Multilevel modulation.
The low base symbol rate is very resistant to multipath distortion because the time between modulation
transitions is much longer than even the worst-case time-smearing caused by summing of multipath
signals. By using a time-sequence of tone pulses, Dolph-Chebychev “windowing” of the modulating
signal and differential modulation, the total occupied bandwidth of a CLOVER-II signal is held to
500 Hz.
The CLOVER Waveform
Multilevel tone, phase and amplitude modulation give CLOVER a large selection of data modes that
may be used (see Table 12.11). The adaptive ARQ mode of CLOVER senses current ionosphere
conditions and automatically adjusts the modulation mode to produce maximum data throughput. When
using the “Fast” bias setting, ARQ throughput automatically varies from 11.6 bytes/s (1.7 times AMTOR)
to 70 bytes/s (10.5 times AMTOR).
The CLOVER-II waveform uses four tone pulses that are spaced in frequency by 125 Hz. The time and
frequency domain characteristics of CLOVER modulation are shown in Figs 12.34, 12.35 and 12.36. The
time-domain shape of each tone pulse is intentionally shaped to produce a very compact frequency spectra.
The four tone pulses are spaced in time and then combined to produce the composite output shown. Unlike
other modulation schemes, the CLOVER modulation spectra is the same for all modulation modes.
Modulation
Data is modulated on a CLOVER-II signal by varying the phase and/or amplitude of the tone pulses.
Further, all data modulation is differential on the same tone pulse; data is represented by the phase (or
amplitude) difference from one
pulse to the next. For example,
Table 12.11
when binary phase modulation
CLOVER-II Modulation Modes
is used, a data change from “0”
As presently implemented, CLOVER-II supports a total of 7 different
to “1” may be represented by a
modulation formats: 5 using PSM and 2 using a combination of PSM
change in the phase of tone
and ASM (Amplitude Shift Modulation).
pulse 1 by 180º between the
Description
In-Block Data Rate
first and second occurrence of Name
16P4A
16 PSM, 4-ASM
750 bps
that pulse. Further, the phase
16PSM 16 PSM
500 bps
state is changed only while the
8P2A
8 PSM, 2-ASM
500 bps
pulse amplitude is zero. There8PSM
8 PSM
375 bps
250 bps
fore, the wide frequency spec- QPSM 4 PSM
BPSM
Binary PSM
125 bps
tra normally associated with 2DPSM 2-Channel Diversity BPSM 62.5 bps
PSK of a continuous carrier is
Modulation Sources (What and How We Communicate)
12. 49
Fig 12.35—A frequency-domain
plot of a CLOVER-II waveform.
Fig 12.34—Ampitude vs time plots for CLOVER-II’s four-tone
waveform.
avoided. This is true for all CLOVER-II modulation formats. The
term “phase-shift modulation”
(PSM) is used when describing
CLOVER modes to emphasize
this distinction.
Coder Efficiency Choices
CLOVER-II has four “coder
efficiency” options: 60%, 75%,
90% and 100% (“efficiency” being the approximate ratio of real
data bytes to total bytes sent).
“60% efficiency” corrects the
most errors but has the lowest net
data throughput. “100% efficiency” turns the encoder off and
has the highest throughput but
fixes no errors. There is therefore
Fig 12.36—Spectra plots of AMTOR, HF packet-radio and
CLOVER-II signals.
a tradeoff between raw data
throughput vs the number of errors that can be corrected without resorting to retransmission of the entire data block.
Note that while the “In Block Data Rate” numbers listed in the table go as high as 750 bps, overhead
reduces the net throughput or overall efficiency of a CLOVER transmission. The FEC coder efficiency
setting and protocol requirements of FEC and ARQ modes add overhead and reduce the net efficiency.
Table 12.12 and Table 12.13 detail the relationships between block size, coder efficiency, data bytes
per block and correctable byte errors per block.
12.50
Chapter 12
Multilevel Digital Modulation Waveforms
Digital waveforms discussed so far have all used either on/off keying (OOK, that is Morse code, or
CW) or frequency-shift keying (FSK, RTTY, AMTOR, PACTOR and packet radio). Both OOK and FSK
are “simple” digital modulation waveforms; they have only two binary states that are represented by
two radio-frequency states. In Morse code, the states are key-down = logical “1” and key-up = logical
“0.” In RTTY, AMTOR, PACTOR and packet radio, one frequency is “1” state, another is the “0” state.
More efficient use may be made of the spectrum by using multilevel modulation, in which one
change in the transmitted signal may represent two or more bits of data. A simple example of multilevel modulation is quadrature phase-shift keying, known as QPSK. The simplest QPSK signal transmits a continuous carrier at a single frequency. Digital information is modulated on this carrier by
changing the phase shift in 90° increments. Since there are four possible 90°-increment states (0°,
90°, 180° and 270°), four different modulation states may be signaled. Put another way, each phase
state may be used to represent two bits of binary data. Examples of four common PSK modes are
shown in Fig A.
The Sounds of
Amateur Radio
Listen to 1200-baud PSK packet transmissions from OSCAR 16.
Note that the phase of the transmitter carrier may be changed from any given state to any other
state. Thus when using QPSK, if two bits of data change from “00” to “11,” only one change to the
transmitter carrier phase is required—from 0° to 270°. This observation illustrates the very important
difference between modulation symbol rate (bauds) and data throughput rate (in bits-per-second,
bits/s). In QPSK, bauds = 0.5 × bits/s (100 baud = 200 bits/s). This concept can be extended to 8PSK
which has 8 phase states that represent 3 bits of data (bits/s = 3 × bauds). Carried further, each
phase state in 16PSK modulation
represents 4 bits of binary data and the
throughput is 4 times the base symbol
rate (bit/s = 4 × bauds).
Higher-level phase shift modulation
schemes have been used (32PSK and
64PSK for example), but these systems
require much more complex demodulator design. In particular, demodulator
sensitivity to noise and distortion
increases greatly as the number of
possible phase states is increased.
Consider the relatively simple QPSK
example. The design-center phase
states of 0°, 90°, 180°, and 270° represent the four possible modulation
conditions. Ionosphere propagation,
multipath signal reflections, and transmission distortion all conspire to insert
phase “jitter” or uncertainty in the
received signal. In QPSK, signals with
a phase shift between 45° and 135°
can be assumed to represent the 90°
state, 135° to 225° for the 180° state
and so on. The margin for error or
“phase margin” for QPSK is ±45°. A
similar calculation for 16PSK shows
that its phase margin is just ±12.25°. If
we consider use of a 10.000 MHz
Fig A
carrier with 16PSK, the period of the
Modulation Sources (What and How We Communicate)
12. 51
carrier sine wave is 0.100 microsecond and the allowable phase jitter corresponds to a time uncertainty of only ±0.003403 ms, or ±3.403 ns. Obviously, very stable phase references must be used in a
16PSK system and it does not take very much distortion or noise to make correct data detection
impossible. However, such systems are commonly used in telephone-line modems.
Telephone modems carry the multilevel concept one step further and use amplitude-level modulation (amplitude-shift keying, ASK) in addition to PSK modulation. If two-level ASK is used with 16PSK,
a total of 32 states may be sent. Similarly, use of 4ASK and 16PSK gives 64 unique states for each
modulation change. This is commonly called “QAM” for Quadrature Amplitude Modulation and is the
modulation used by most 9600-baud telephone modems. Each modulation change can represent the
state of 6 bits of binary data; the data throughput is
6 times the base modulation symbol rate (bits/s = 6 × bauds). As noted above, complex multilevel
modulation schemes require very complex and expensive demodulators that are very susceptible to
noise and distortion. Fortunately, modern telephone lines are relatively noise-free and stable. By use
of error correction and line distortion equalization, high “speed” data transmission via telephone line is
now in common use.
Unfortunately, these same techniques cannot be directly applied to radio data transmission, particularly to HF signals. Long-range HF signals are propagated via the ionosphere, which is not stable or
well-defined from instant to instant. Ionosphere reflection height and signal attenuation varies widely
with time of day, geographic location, and solar activity. Moreover, noise levels on HF vary considerably with location as well as time of day.
With multipath propagation, multiple copies of an original signal are summed at the receiving antenna. Since each signal travels via a different path, the propagation delays are different. Multiple
signals therefore arrive at the receiver at slightly different times and the “mark-to-space” transition
time is different for each signal. This causes “smearing” of the exact transition times. Multipath
distortion occurs commonly on HF when both single-hop and multiple-hop signals arrive at the receiving antenna with similar strengths. Multipath distortion is also common on VHF and UHF signals in
highly populated areas where large buildings provide reflecting surfaces.
The HF environment is therefore complicated and hostile to data transmission. Modulation techniques that work well on stable and predictable telephone lines may also be usable for VHF and UHF
radio systems, but they may seldom be directly applied to HF data radio systems. Further, data
format protocols that were devised for the stable phone-line environment are generally not optimum
for use on HF data radio. For example, both the FSK modulation and the protocol used for AX.25
packet radio lead to serious problems when used on HF signals.
Table 12.12
Data Bytes Transmitted Per Block
Block Size
17
51
85
255
12.52
Reed-Solomon Encoder Efficiency
60% 75%
90%
100%
8
10
12
14
28
36
42
48
48
60
74
82
150
188
226
252
Chapter 12
Table 12.13
Correctable Byte Errors Per Block
Block Size
17
51
85
255
Reed-Solomon Encoder Efficiency
60%
75%
90%
100%
1
1
0
0
9
5
2
0
16
10
3
0
50
31
12
0
CLOVER FEC
All modes of CLOVER-II use Reed-Solomon forward error correction (FEC) data encoding which
allows the receiving station to correct errors without requiring a repeat transmission. This is a very
powerful error correction technique that is not available in other common HF data modes such as AX.25
packet radio or AMTOR ARQ mode.
CLOVER ARQ
Reed-Solomon data coding is the primary means by which errors are corrected in CLOVER “FEC”
mode (also called “broadcast mode”). In ARQ mode, CLOVER-II employs a three-step strategy to
combat errors. First, channel parameters are measured and the modulation format is adjusted to minimize
errors and maximize data throughput. This is called the “Adaptive ARQ Mode” of CLOVER-II. Second,
Reed-Solomon encoding is used to correct a limited number of byte errors per transmitted block. Finally,
only those data blocks in which errors exceed the capacity of the Reed-Solomon decoder are repeated
(selective block repeat). Unlike AX.25 packet radio, CLOVER-II does not repeat blocks which have
been received correctly.
With seven different modulation formats, four data block lengths (17, 51, 85 or 255 bytes) and four
Reed-Solomon coder efficiencies (60%, 75%, 90% and 100%), there are 112 (7 × 4 × 4) different
waveform modes that could be used to send data via CLOVER. Once all of the determining factors are
considered, however, there are 8 different waveform combinations which are actually used for FEC and/
or ARQ modes.
CLOVER vs AMTOR vs Packet
Fig 12.36 shows the modulator output spectra of CLOVER-II, AMTOR and HF packet radio. Nearly
all of the CLOVER-II signal energy is concentrated within ±250 Hz of the center frequency. Therefore,
CLOVER-II signals can be spaced as closely as 500 Hz from any data-mode signal with very little
cochannel interference. Tests show that “cross-talk” between two 500-Hz spaced CLOVER-II signals
is less than 50 dB. This is much better than the common spacing of AMTOR (1000 Hz) or HF packet
signals (2000 Hz).
Fig 12.37 shows throughput
vs S/N for AMTOR and various
modes of CLOVER-II. For all
values of S/N and all modes of
CLOVER, the data throughput
obtainable using CLOVER-II is
higher than that achievable
when using AMTOR. In addition, CLOVER may be used to
send full 8-bit computer data
whereas AMTOR is restricted
to either the Baudot RTTY characters set (CCIR-476/625) or
the printable subset of ASCII
(ASCII-over-AMTOR).
RTTY has better automatic
receive decoding performance
than Morse code and is rela- Fig 12.37—ARQ-mode data throughput vs receiver S/N ratio for
tively inexpensive, but offers AMTOR and three different CLOVER-II configurations.
Modulation Sources (What and How We Communicate)
12. 53
no automatic error correction. AMTOR includes error correction, has good performance under weak
signal conditions and is relatively inexpensive. However, its maximum data throughput rate is low and
it cannot support transmission of 8-bit data files.
AX.25 packet radio is inexpensive but its performance on HF is typically very poor. This is due both
to the popular choice of modulation (200 Hz shift, 300 baud FSK) and the AX.25 protocol which was
not designed to handle the burst-type errors that are common to HF propagation. The MIL-188/110A
(now proposed Federal Standard pFS-1052) “Serial, Single-Tone” waveform works well on HF and can
pass error-corrected 8-bit data with a throughput of up to 2400 baud. However, modems for this mode
are presently very expensive, the occupied bandwidth of 3000 Hz is very wide, and ARQ or adaptive
ARQ modes are still under development.
In comparison, CLOVER-II modems are moderately expensive but will adaptively match existing
signal conditions and provide high data throughput rates when conditions permit. CLOVER-II will pass
full 8-bit data and a CLOVER signal is the most bandwidth efficient of all modes considered.
How do They Compare?
An extensive comparison of digital modes was written by Tim Riley; Dennis Bodson, W4PWF;
Stephen Rieman and Teresa Sparkman. See “A Comparison of HF Digital Protocols,” QST, July 1996,
page 35.
12.54
Chapter 12
CLOVER-2000
CLOVER-2000 is a faster version of CLOVER (about four times faster) that uses eight tone pulses,
each of which is 250-Hz wide, spaced at 250-Hz centers, contained within the 2-kHz bandwidth between
500 and 2500 Hz. The eight tone pulses are sequential, with only one tone being present at any instant
and each tone lasting 2 ms. Each frame consists of eight tone pulses lasting a total of 16 ms, so the base
modulation rate of a CLOVER-2000 signal is always 62.5 symbols per second (regardless of the type
of modulation being used). CLOVER-2000’s maximum raw data rate is 3000 bits per second. Allowing
for overhead, CLOVER-2000 can deliver error-corrected data over a standard HF SSB radio channel at
up to 1994 bits per second, or 249 charcaters (8-bit bytes) per second. These are the uncompressed data
rates; the maximum throughput is typically doubled for plain text if compression is used. The effective
data throughput rate of CLOVER-2000 can be even higher when binary file transfer mode is used with
data compression.
The binary file transfer protocol used by HAL Communications operates with a terminal program
explained in the HAL E2004 engineering document listed under references. Data compression algorithms tend to be context sensitive—compression that works well for one mode (e.g. text), may not work
well for other data forms (graphics, etc.). The HAL terminal program uses the PK-WARE compression
algorithm which has proved to be a good general-purpose compressor for most computer files and
programs. Other algorithms may be much more efficient for some data formats, particularly for
compression of graphic image files and digitized voice data. The HAL Communications CLOVER-2000
modems can be operated with other data compression algorithms in the users’ computers.
CLOVER-2000 is similar to the previous version of CLOVER, including the transmission protocols
and Reed-Solomon error detection and correction algorithm. The original descriptions of the CLOVER
Control Block (CCB) and Error Correction Block (ECB) still apply for CLOVER-2000, except for the
higher data rates inherent to CLOVER-2000. Just like CLOVER, all data sent via CLOVER-2000 is
encoded as 8-bit data bytes and the error-correction coding and modulation formatting processes are
transparent to the data stream—every bit of source data is delivered to the receiving terminal without
modification. Control characters and special “escape sequences” are not required or used by CLOVER2000. Compressed or encrypted data may therefore be sent without the need to insert (and filter) additional control characters and without concern for data integrity. Five different types of modulation may
be used in the ARQ mode—BPSM (Binary Phase Shift Modulation), QPSM (Quadrature PSM), 8PSM
(8-level PSM), 8P2A (8PSM + 2-level Amplitude-Shift Modulation), and 16P4A (16 PSM plus 4 ASM).
The same five types of modulation used in ARQ mode are also available in Broadcast (FEC) mode,
with the addition of 2-Channel Diversity BPSM (2DPSM). Each CCB is sent using 2DPSM modulation,
17-byte block size, and 60% bias. The maximum ARQ data throughput varies from 336 bits per second
for BPSM to 1992 bits per second for 16P4A modulation. BPSM is most useful for weak and badly
distorted data signals while the highest format (16P4A) needs extremely good channels, with high SNRs
and almost no multipath.
Most ARQ protocols designed for use with HF radio systems can send data in only one direction at
a time. For example, when using CCIR-476/625 (SITOR) or PACTOR, one station sends all of its data,
ending the transmission with an “OVER” command. The second station may then send its information.
Because CLOVER-2000 does not need an “OVER” command, data may flow in either direction at any
time. The CLOVER ARQ time frame automatically adjusts to match the data volume to be sent in either
or both directions. When first linked, both sides of the ARQ link exchange information using six bytes
of the CCB. When one station has a large volume of data buffered and ready to send, ARQ mode
automatically shifts to an expanded time frame during which one or more 255 byte data blocks are sent.
If the second station also has a large volume of data buffered and ready to send, its half of the ARQ frame
is also expanded. Either or both stations will shift back to CCB level when all buffered data has been sent.
Modulation Sources (What and How We Communicate)
12. 55
This feature provides the benefit of full-duplex data transfer but requires use of only simplex frequencies
and half-duplex radio equipment. This two-way feature of CLOVER can also provide a back-channel
order-wire capability. Communications may be maintained in this “chat” mode at 55 words per minute,
which is more than adequate for real-time keyboard-to-keyboard communications.
Two different CLOVER-2000 modems are available from HAL Communications, the PCI-4000/2K
and the DSP-4100/2K. The PCI-4000/2K is for use inside dedicated desk-top personal computers. The
PCI-4000/2K may be installed in any IBM-compatible personal computer that uses an 80386 or faster
microprocessor (386, 486, Pentium, etc.) and supports the ISA PC plug-in card bus. The DSP-4100/2K
is for connection to a laptop or non-IBM PC, since it is a stand-alone DSP modem that may be used with
any computer or data terminal having an RS-232 port.
12.56
Chapter 12
PSK31
Peter Martinez, G3PLX, who was instrumental in bringing us AMTOR, developed PSK31 for
real time keyboard-to-keyboard QSOs. This section was adapted from an article in RadCom, Jan
1999. The name derives from the modulation type (phase shift keying) and the data rate, which is
actually 31.25 bauds. PSK31 is a robust mode for HF communications that features the 128 ASCII
(Internet) characters and the full 256 ANSI character set. This mode works well for two-way QSOs
and for nets. Time will tell if PSK31 will replace Baudot RTTY on the amateur HF bands.
Morse code uses a single carrier frequency keyed on and off as dits and dahs to form characters. RTTY
code shifts between two frequencies one for mark (1) the other for space (0). Sequences of marks and
spaces comprise the various characters.
Martinez devised a new variable-length code for PSK31 that combines the best of Morse and RTTY.
He calls it Varicode because a varying number of bits are used for each character (see Fig A). Much like
the Morse code, the more
commonly used letters have
shorter codes.
As with RTTY, there is a
need to signal the gaps between
characters. The Varicode does
this by using “00” to represent
a gap. The Varicode is structured so that two zeros never
appear together in any of the
combinations of 1s and 0s that
make up the characters. In onthe-air tests, Martinez has
verified that the unique “00”
sequence works significantly
better than RTTY’s stop code
for keeping the receiver synchronized.
With Varicode, a typing Fig A—Codes for the word “ten” in ASCII, Baudot, Morse and
speed of about 50 words per Varicode.
minute requires a 32 bit/s
transmission rate. Martinez
chose 31.25 bit/s because it can
be easily derived from the
8-kHz sample rate used in
many DSP systems.
The shifting carrier phase
generates sidebands 31.25 Hz
from the carrier. These are used
to synchronize the receiver
with the transmitter. The required bandwidth is less than
that for the FSK signal of 100
baud Baudot RTTY, as shown
Fig B—The spectrum of a PSK31 signal compared to that of a 100
baud, 200-Hz-shift FSK signal.
in Fig B.
Modulation Sources (What and How We Communicate)
12. 57
ERROR CORRECTION
Martinez has added error correction to PSK31 by using QPSK (quatenary phase shift keying) and a
convolutional encoder to generate one of four different phase shifts that corresond to patterns of five
successive data bits. At the receiving end, a Viterbi decoder is used to correct errors. There are 32
possible sequences for five bits. The Viterbi decoder tracks these possibilities while discarding the least
likely and retaining the most likely sequences. Retained sequences are given a score that is based on the
running total. The most accurate sequence is reported, and thus errors are corrected.
Operating PSK31 in the QPSK mode should result in 100% copy under most conditions, but at a price.
Tuning is twice as critical as it is with BPSK. An accuracy of less than 4 Hz is required for the Viterbi
decoder to function properly.
GETTING STARTED
In addition to a transceiver and antenna, you only need a computer with a Windows operating system
and a 16-bit sound card to receive and transmit PSK31. Additional information and software is available
for free download over the Web. Use a search engine to find PSK31 information and links to downloads.
12.58
Chapter 12
Image Modes
FACSIMILE
This section, by Dennis Bodson, W4PWF, and Steven Karty, N5SK, covers several facsimile systems
in most common Amateur Radio use today. For further information on the area of facsimile, its
history, and the development of related standards associated with this mode, refer to FAX: Facsimile
Technology and Systems.1 The subject of Weather fax, while of interest to many amateurs, is not a
primary activity of the Amateur Radio Service. Information on this subject is contained in the Weather
Satellite Handbook.2
FACSIMILE OVERVIEW
Facsimile (fax) is a method for transmitting very high resolution still pictures using voice bandwidth
radio circuits. The narrow bandwidth of the fax signal, equivalent to SSTV, provides the potential for
worldwide communications on the HF bands. Fax is the oldest of the image-transmitting technologies
and has been the primary method of transmitting newspaper photos and weather charts. Fax is also used
to transmit high-resolution cloud images from both polar-orbit and geostationary satellites. Many of
these images are retransmitted using fax on the HF bands.
The resolution of typical fax images greatly exceeds what can be obtained using SSTV or even
conventional television (typical images will be made up of 800 to 1600 scanning lines). This high
resolution is achieved by slowing down the rate at which the lines are transmitted, resulting in image
transmission times of 4 to 10 minutes. Prior to the advent of digital technology, the only practical way
to display such images was to print each line directly to paper as it arrived. The mechanical systems for
accomplishing this are known as facsimile recorders and are based on either photographic media (a
modulated light source exposing film or paper) or various types of direct printing technologies including
electrostatic and electrolytic papers.
Modern desktop computers have virtually eliminated bulky fax recorders from most amateur installations. Now the incoming image can be stored in computer memory and viewed on a standard TV
monitor or a high-resolution computer graphics display. The use of a color display system makes it
entirely practical to transmit color fax images when band conditions permit. The same computer-based
system that handles fax images is often capable of SSTV operation as well, blurring what was once a clear
distinction between the two modes. The advent of the personal computer has provided amateurs with a
wide range of options within a single imaging installation. SSTV images of low or moderate resolution
can be transmitted when crowded band conditions favor short frame transmission times. When band
conditions are stable and interference levels are low, the ability to transmit very high resolution fax
images is just a few keystrokes away!
HARDWARE AND SOFTWARE
Electromechanical fax equipment has been replaced by personal computer hardware and software. The computer allows reception and transmission of various line per minute rates and indices of cooperation by simply pressing a key or by pointing and
clicking a mouse. Many fax programs are available as either commercial software or shareware. Usually, the shareware packages
(and often trial versions of the commercial packages) are available by downloading from the Internet.
A good starting point is the ARRL software repositories. To get
to them, set your browser to the ARRL Web and go to the FTP
1
McConnell, Ken, Bodson,
Dennis, and Urban, Steve, FAX:
Facsimile Technology and
Systems, 3rd Ed., Artech House,
1999,
2
Taggart, R.E., Weather Satellite
Handbook, 5th Ed. (Newington:
ARRL, 1994).
Modulation Sources (What and How We Communicate)
12. 59
(files) link in the site index. You can use any commercial search site to look for “fax” AND “software.”
Examplesof several fax programs are as follows:
JVFAX is a very popular fax program. It is DOS-based program with a large number of options for
installation. It can receive and transmit several fax formats, black-and-white and color. Your computer’s
serial port, connected to a very simple interface, provides the connection to your transceiver.
The FAX 480 software program can also be used with fax as well as SSTV. For more information on
this program and others including website addresses, see the July 1998 QST article “FAX 480 and SSTV
Interfaces and Software” page 32. A copy for downloading of the free software program vester_n.zip for
FAX 480 can be found online at the Oakland University FTP site (see the References chapter). This
program also uses a simple interface almost identical to that for JVFAX.
Weatherman is a DOS-based program, using a SoundBlaster (or compatible) card as the interface.
The program is shareware and provides receive-only capability. A single, shielded wire from your
receiver audio output to the computer audio input is the only connection needed.
WXSat operates under Windows 3.X. While specifically set up to decode and store weather-satellite
APT pictures, it can also be used for HF-fax reception.
Both Weatherman and WXSat are samples of what you can find during a search on the Internet. Often,
programs are offered and then either withdrawn or improved over the versions previously distributed—
to get the latest and greatest you have to periodically search and see what comes up. If you use an online
service such as CompuServe or AOL, they are another source of fax software. Check their ham forums
or sections for listings.
Many commercial multimode controllers either contain software to receive and transmit fax, or are
compatible with PC-hosted software. Available controller suppliers include MFJ, Timewave, and
Kantronics; additional software may be required for the Kam Plus. Check the advertising pages of QST
for the latest units available.
One well-known fax page on the Internet, complete with downloadable software, is posted and maintained by Marius Rensen; it contains listings of commercial fax transmissions for you to test your
software or just SWL for interest. See the References chapter for the URL. Before using a program taken
from any Internet source, check other sources for newer versions. It is not uncommon to have older
versions posted on one place and newer versions in another. It is a good idea to virus check the software
before and after unzipping.
Image transmission using voice bandwidth is a trade-off between resolution and time. In the section
on slow-scan television, standards are described that permit 240-line black-and-white images to be
transmitted in about 36 seconds while color images of similar resolution require anywhere from 72 to
188 seconds, depending on the color format. In terms of resolution, 240-line SSTV images are roughly
equivalent to what you would obtain with a standard broadcast TV signal recorded on a home VCR. This
is more than adequate for routine video communication, but there are many situations that demand
images of higher resolution.
HAL Communications Corporation has developed an interesting system which enables a standard fax
machine (Group 3 or G3) to send commercial fax images over HF radio. HAL Communications accomplishes this with just two small ancillary devices, which connect between a standard fax machine and an
ordinary HF radio transceiver (see Fig 12.38). This method is frequently referred to as “G3 fax over
radio.” Any G3 fax machine can be connected to the HAL FAX-4100 controller with just a standard RJ11 modular connector. The FAX-4100 controller connects directly to the HAL CLOVER-2000 (DSP4100) radio data modem, which in turn connects to the HF transceiver. This entire setup is duplicated
at the opposite end of the link.
A “call” is initiated from the fax machine keypad just as if the fax machine were connected to a phone
line. The FAX-4100 controller includes a built-in 9600-baud G3 modem which emulates the telephone
system: The controller at the initiating end answers the ring from the originating fax machine, establishes
12.60
Chapter 12
Fig 12.38—Set up of a G3 fax machine connected to a HAL FAX-4100 controller and a HAL CLOVER2000 (DSP-4100) radio data modem, which in turn connects to an HF transceiver.
Modulation Sources (What and How We Communicate)
12. 61
the HF radio link (based on the “phone number”), and handshakes with the controller at the other end
to start the receiving faxmachine. Fax image data then passes from the fax machine into the controller’s
memory at the originating end. The controller also establishes a data link between the CLOVER-2000
modems at both ends, then passes the fax data through them and the controller at the receiving end, and
finally into the receiving G3 fax machine. HAL has automated the HF radio operating procedures. To
the user, sending a fax over HF radio is a simple three-step process:
1. Lay the page(s) on the fax machine.
2. Enter the ID number of the other station.
3. Push GO on the fax machine.
Housekeeping control functions and indications are also automated, feeding messages back to the fax
machine whenever possible (link failed, other station not available, etc.). A full page can be sent in 2
to 6 minutes, depending upon ionospheric conditions and density of the page to be transmitted. The entire
link set up and maintenance procedure is transparent to the fax operator, who need not know nor care
that an HF radio system is part of the fax link. It all works just like a standard fax telephone transmission.
An additional piece of equipment is available from HAL to enable the same fax machine to be shared
between HF radio and conventional telephone lines. The HAL LI-4100 Line Interface is a “smart switch”
that can be connected between the fax machine, the FAX-4100 controller, and up to two telephone lines.
12.62
Chapter 12
SLOW-SCAN TELEVISION (SSTV)
An ancient Chinese proverb states: “A picture is worth a thousand words.” It’s still true today. Sight
is our highest bandwidth sense and the primary source of information about the world around us. What
would you think about a TV news program without pictures about the stories? Would you enjoy reading
the comics if there were no drawings with the text? Do you close your eyes when talking to someone in
person? Many hams feel the same way about conversing with Amateur Radio: sending images is a
wonderful way to enhance communication. This material was written by John Langner, WB2OSZ.
For decades only a dedicated few kept SSTV alive. The little commercial equipment was very expensive and home brewing was much too complicated for most people. Early attempts at computer-based
systems were rather crude and frustrating to use.
The situation has changed dramatically in recent years. There is now a wide variety of commercial
products and home-brew projects to fit every budget, and SSTV activity is experiencing rapid growth.
There is even software that uses the popular Sound Blaster computer sound card for SSTV.
The early SSTV 8-second transmission standard is illustrated in Fig 12.49. Audio tones in the 1500
to 2300-Hz range represent black, white, and shades of gray. A short 1200-Hz burst separates the scan
lines, and a longer 1200-Hz tone signals the beginning of a new picture.
Color SSTV Evolution
The early experimenters weren’t content with only black and white (B&W) images and soon devised
a clever way to send color pictures with B&W equipment. The transmitting station sends the same image
three times, one each with red, green and blue filters in front of the TV camera lens. The receiving
operator took three long-exposure photographs of the screen, placing red, green and blue filters in front
of the film camera’s lens at the appropriate times. This was known as the “frame sequential” method.
In the 1970s, it became feasible to save these three images in solid-state memory and simultaneously
display them on an ordinary color TV. But, the frame-sequential method had some drawbacks. As the
first frame was received you’d see a red and black image. During
the second frame, green and yellow would appear. Blue, white,
and other colors wouldn’t show up until the final frame. Any noise
(QRM or QRN) could ruin the image registration (the overlay of
the frames) and spoil the picture.
The next step forward was the “line sequential” method. Each
line is scanned 3 times: once each for the red, green, and blue
picture components. Pictures could be seen in full color as they
were received and registration problems were reduced. The
Wraase SC-1 modes are examples of early line-sequential color
transmission. They have a horizontal sync pulse for each of the
color component scans. The major weakness here is that if the
receiving end gets out of step, it won’t know which scan repreFig 12.49—Early SSTV operators
sents which color.
Rather than sending color images with the usual RGB (red, developed a basic 8-second black
and white transmission format.
green, blue) components, Robot Research used luminance and The sync pulses are often called
chrominance signals for their 1200C modes. The first half or two “blacker than black.” A complete
thirds of each scan line contains the luminance information which picture would have 120 lines
is a weighted average of the R, G and B components. The remain- (8 seconds at 15 ms per line).
Horizontal sync pulses occur at
der of each line contains the chrominance signals with the color the beginning of every line; a
information. Existing B&W equipment could display the B&W- 30 ms vertical sync pulse precompatible image on the first part of each scan line and the rest cedes each frame.
Modulation Sources (What and How We Communicate)
12. 63
would go off the edge of the screen. This compatibility was very beneficial when most people still had
only B&W equipment.
The luminance-chrominance encoding made more efficient use of the transmission time. A 120-line
color image could be sent in 12 s, rather than the usual 24 s. Our eyes are more sensitive to details in
changes of brightness than color, so the time could be used more efficiently by devoting more time to
luminance than chrominance. The NTSC and PAL broadcast standards also take advantage of this vision
characteristic and use less bandwidth for the color part of the signal.
The 1200C introduced another innovation: it encodes the transmission mode in the vertical sync
signal. By using narrow FSK encoding around the sync frequency, compatibility was maintained. This
new signal just looked like an extra-long vertical sync to older equipment. (See the sidebar “Examining
Robot’s Vertical-Interval-Signaling (VIS) Code” for more details.)
The luminance-chrominance encoding offers some benefits but image quality suffers. It is acceptable
for most natural images but looks bad for sharp, high-contrast edges, which are more and more common
as images are altered via computer graphics. As a result, all newer modes have returned to RGB encoding.
The Martin and Scottie modes are essentially the same except for the timings. They have a single horizontal
sync pulse for each set of RGB scans. Therefore, the receiving end can easily get back in step if synchronization is temporarily lost. Although they have horizontal sync, some implementations ignore them on receive.
Instead, they rely on very accurate time bases at the transmitting and receiving stations to keep in step. The
advantage of this “synchronous” strategy is that missing or corrupted sync pulses won’t disturb the received
image. The disadvantage is that even slight timing inaccuracies produce slanted pictures.
In the late 1980s, yet another incompatible mode was introduced. The AVT mode is different from
all the rest in that it has no horizontal sync. It relies on very accurate oscillators at the sending and
receiving stations to maintain synchronization. If the beginning-of-frame sync is missed, it’s all over.
There is no way to determine where a scan line begins. However, it’s much harder to miss the 5-s header
than the 300-ms VIS code. Redundant information is encoded 32 times and a more powerful errordetection scheme is used. It’s only necessary to receive a small part of the AVT header in order to achieve
synchronization. After this, noise can wipe out parts of the image, but image alignment and colors remain
correct. Table 12.15 lists characteristics of common modes.
Scan Converters
A scan converter is a device that converts signals from one TV standard to another. In this particular
case we are interested in converting between SSTV, which can be sent through audio channels, and fast
Examining Robot’s Vertical-Interval-Signaling (VIS) Code
The original 8-second black-and-white SSTV-image standard
used a 30-millisecond, 1200-Hz pulse to signal the beginning of
a new frame. In the Robot 1200C, Robot Research increased
the vertical sync period by a factor of 10, encoded 8 bits of
digital data into it and called it vertical-interval signaling (VIS).
VIS is composed of a start bit, 7 data bits, an even parity bit,
and a stop bit, each 30 milliseconds long. (See Fig A).
Since then, inventors of new SSTV modes (Martin, Scottie,
AVT, etc) have adopted Robot’s scheme and assigned codes to
their particular mode that are unused by the Robot modes. So,
each of the SSTV transmission modes has a unique VIS code.
This allows new equipment to automatically select any of the
new SSTV modes while maintaining compatibility with the older
equipment.—WB2OSZ
12.64
Chapter 12
Fig A—Composition of the
vertical interval signaling (VIS)
code.
Table 12.15
SSTV Transmission Characteristics
Mode
AVT
24
90
94
188
125
Color
Type
RGB
RGB
RGB
RGB
BW
Martin
M1
M2
M3
M4
RGB
RGB
RGB
RGB
114
58
57
29
240
240
120
120
B
B
C
C
YC
YC
90
112
240
240
G
G
P3
P5
P7
RGB
RGB
RGB
203
305
406
16+480
16+480
16+480
Robot
8
12
24
36
12
24
36
72
BW
BW
BW
BW
YC
YC
YC
YC
8
12
24
36
12
24
36
72
120
120
240
240
120
120
240
240
A,E
E
E
E
Scottie
S1
S2
S3
S4
DX
RGB
RGB
RGB
RGB
RGB
110
71
55
36
269
240
240
120
120
240
B
B
C
C
B
Wraase SC-1
24
48
96
RGB
RGB
RGB
24
48
96
120
240
240
C
B
B
Wraase SC-2
30
60
120
180
RGB
RGB
RGB
RGB
30
60
120
180
128
256
256
256
Pro-Skan
J120
RGB
120
240
WinPixPro
GVA 125
GVA 125
GVA 250
BW
RGB
RGB
125
125
250
480
240
480
JV Fax
JV Fax Color
RGB
variable
variable
F
FAX480
Fax 480
Truscan
Colorfax 480
BW
BW
RGB
138
128
384
480
480
480
H
I
HQ
Pasokon TV
Designator
HQ1
HQ2
Scan Time
(sec)
24
90
94
188
125
Scan Lines
Notes
120
240
200
400
400
D
D
D
D
D
Notes
RGB—Red, green and blue
components sent separately.
YC—Sent as Luminance (Y) and
Chrominance (R-Y and B-Y).
BW—Black and white.
A—Similar to original 8-second
black & white standard.
B—Top 16 lines are gray scale.
240 usable lines.
C—Top 8 lines are gray scale.
120 usable lines.
D—AVT modes have a 5-second
digital header and no horizontal
sync.
E—Robot 1200C doesn’t really
have B&W mode but it can
send red, green or blue
memory separately. Traditionally, just the green component
is sent for a rough approximation of a b&w image.
F—JV Fax Color mode allows the
user to set the number of lines
sent, the maximum horizontal
resolution is slightly less than
640 pixels. This produces a
slow but very high resolution
picture. SVGA graphics are
required.
G—Available only on Martin 4.6
chipset in Robot 1200C.
H—Vester version of FAX480
(with VIS instead of start signal
and phasing lines).
I—Trucolor version of Vester
Truscan.
Modulation Sources (What and How We Communicate)
12. 65
Courteous SSTV
Operating
• Recommended frequencies:
3.845, 7.171, 14.230,
14.233, 21.340, 28.680,
145.5 MHz.
• 14.230 is the most active
• Make contact by voice
before sending SSTV.
• Not all systems recognize
the VIS code, so it is good
manners to announce the
mode before transmitting.
Fig 12.50—Diagram of an SSTV station based on a scan converter.
scan (broadcast or ATV), so we can use ordinary camcorders and color televisions to generate and
display pictures. From about 1985 to 1992, the Robot 1200C was king.
Fig 12.50 shows a typical SSTV station built around a scan converter such as the Robot 1200C or a
SUPERSCAN 2001. The scan converter has circuitry to accept a TV signal from a camera and store it
in memory. It also generates a display signal for an ordinary television set. The interface to the radio is
simply audio in, audio out and a push-to-talk (PTT) line. In the early days, pictures were stored on audio
tape, but now computers store them on disks. Once a picture is in a computer, it can be enhanced with
paint programs.
This is the easiest approach. Just plug in the cables, turn on the power and it works. Many people prefer
special dedicated hardware, but most of the recent growth of SSTV has been from these lower cost PCbased systems.
SSTV with a Computer
There were many attempts to use early home computers for SSTV. Those efforts were hampered by
very small computer memories, poor graphics capabilities and poor software development tools.
Surprisingly, little was available for the ubiquitous IBM PC until around 1992, when several systems
appeared in quick succession. By this time, all new computers had a VGA display, which is required for
this application. Most new SSTV stations look like Fig 12.51. Some sort of interface is used to get audio
in and out of the computer. These can be external interfaces connected to a serial or printer port, an
internal card specifically for SSTV or even a peripheral audio card. IBM-type PC compatible computers
with VGA video display monitors can also be used with their existing SoundBlaster-compatible sound
boards for the interfaces, if software such as WinSkan and WinPix Pro are used. Most of the work is done
in software. System updates are performed by reading a floppy disk instead of changing EPROMs or
other components. Most of these software programs are based on the work of Ben Vester, K3BC. These
computer programs include Vester Truscan, Pasokon TV Lite, ProScan, JVFAX, and HamComm; they
all use a simple “clipper” hardware interface, which can easily be built with less than $15 worth of
RadioShack parts, because the computer program does all of the processing work previously done by
more expensive hardware. See the July 1998 issue of QST for “FAX 480 and SSTV Interfaces and
Software” on page 32. The URL for downloading Vester’s software is ftp://oak.oakland.edu/pub/
hamradio/arrl/bbs/programs.
12.66
Chapter 12
How It Works
Transmitting SSTV images
with a computer is quite
simple. All you need to do is
generate fairly accurate tones
and change them at the proper
pixel rate. Tones in the range
of 1500 to 2300 Hz correspond
to the pixel intensities, and
most modes use 1200-Hz sync
pulses. A very low-cost system
Fig 12.51—A modern, PC-based SSTV station.
could even use the computer’s
built-in tone generator for
transmitting, but the tones must be pure with little distortion in order to produce an acceptable RF signal
via AFSK (see “AFSK” under Baudot section of this chapter).
SSTV reception is a little more difficult. First you must somehow measure the frequency of the
incoming tone. You can’t simply count the number of cycles in a second, or even 0.01 second, because
the frequency is changing thousands of times each second. Fig 12.52 illustrates one way of rapidly
measuring the incoming tone’s frequency. Two filters are designed to have maximum outputs a little
beyond the ends of the frequency range of interest. The output of one filter is rectified to become a
positive voltage; the output of the other is rectified to become a negative voltage; then the voltages are
summed. A low-pass filter, with a 1-kHz cutoff, removes the audio carrier ripple while passing the
slower video signal. With careful design, the result is a voltage that is fairly proportional to the input
frequency. Finally, an analog to digital (A/D) converter processes the signal for the computer.
Another frequency-measuring approach uses digital circuitry to measure the period of each audio
cycle (see Fig 12.53). When the signal amplitude crosses zero, a counter is reset. It then proceeds to count
Fig 12.52—Block diagram of an analog SSTV demodulator.
Fig 12.53—Block diagram of a
digital SSTV demodulator.
Modulation Sources (What and How We Communicate)
12. 67
SSTV Glossary
ATV—Amateur Television. Sending pictures by Amateur Radio. You’d expect this abbreviation to apply
equally to fast-scan television (FSTV), slow-scan television (SSTV) and facsimile (fax), but it’s generally
applied only to FSTV.
AVT—Amiga Video Transceiver. 1) Interface and software for use with an Amiga computer, developed by
Ben Blish-Williams, AA7AS, and manufactured by Advanced Electronic Applications (AEA); 2) a family
of transmission modes first introduced with the AVT product.
Back porch—The blank part of a scan line immediately following the horizontal sync pulse.
Chrominance—The color component of a video signal. NTSC and PAL transmit color images as a blackand-white compatible luminance signal along with a color subcarrier. The subcarrier phase represents
the hue and the subcarrier’s amplitude is the saturation. Robot color modes transmit pixel values as
luminance (Y) and chrominance (R-Y [red minus luminance] and B-Y [blue minus luminance]) rather
than RGB (red, green, blue).
Demodulator—For SSTV, a device that extracts image and sync information from an audio signal.
Field—Collection of top to bottom scan lines. When interlaced, a field does not contain adjacent scan
lines and there is more than one field per frame.
Frame—One complete scanned image. The Robot 36-second color mode has 240 lines per frame. NTSC
has 525 lines per frame with about 483 usable after subtracting vertical sync and a few lines at the top
containing various information.
Frame Sequential—A method of color SSTV transmission which sent complete, sequential frames of red,
then green and blue. Now obsolete.
Front porch—The blank part of a scan line just before the horizontal sync.
FSTV—Fast-Scan TV. Same as common, full-color, motion commercial broadcast TV.
Interlace—Scan line ordering other than the usual sequential top to bottom. For example, NTSC sends a
field with just the even lines in 1/ 60 second, then a field with just the odd lines in 1/ 60 second. This
results in a complete frame 30 times a second. AVT “QRM” mode is the only SSTV mode that uses
interlacing.
Line Sequential—A method of color SSTV transmission that sends red, green, and blue information for
each sequential scan line. This approach allows full-color images to be viewed during reception.
Luminance—The brightness component of a video signal. Usually computed as Y (the luminance signal)
= 0.59 G (green) + 0.30 R (red) + 0.11 B (blue).
Martin—A family of amateur SSTV transmission modes developed by Martin Emmerson, G3OQD, in
England.
NTSC—National Television System Committee. Television standard used in North America and Japan.
PAL—Phase alteration line. Television standard used in Germany and many other parts of Europe.
Pixel—Picture element. The dots that make up images on a computer’s monitor.
P7 monitor—SSTV display using a CRT having a very-long-persistence phosphor.
RGB—Red, Green, Blue. One of the models used to represent colors. Due to the characteristics of the
human eye, most colors can be simulated by various blends of red, green, and blue light.
Robot—(1) Abbreviation for Robot 1200C scan converter; (2) a family of SSTV transmission modes
introduced with the 1200C.
Scan converter—A device that converts one TV standard to another. For example, the Robot 1200C
converts SSTV to and from FSTV.
Scottie—A family of amateur SSTV transmission modes developed by Eddie Murphy, GM3SBC, in Scotland.
SECAM—Sequential color and memory. Television standard used in France and the Commonwealth of
Independent States.
SSTV—Slow Scan Television. Sending still images by means of audio tones on the MF/HF bands using
transmission times of a few seconds to a few minutes.
Sync—That part of a TV signal that indicates the beginning of a frame (vertical sync) or the beginning of
a scan line (horizontal sync).
VIS—Vertical Interval Signaling. Digital encoding of the transmission mode in the vertical sync portion of
an SSTV image. This allows the receiver of a picture to automatically select the proper mode. This was
introduced as part of the Robot modes and is now used by all SSTV software designers.
Wraase—A family of amateur SSTV transmission modes first introduced with the Wraase SC-1 scan
converter developed by Volker Wraase, DL2RZ, of Wraase Electronik, Germany.
12.68
Chapter 12
pulses from a crystal controlled oscillator. At the end of the audio cycle, the counter content is snatched,
the counter is reset and the process starts all over again.
The digital approach offers a few advantages over the analog approach. A single chip can contain the
counter and handle several other functions as well. The analog approach requires a handful of op amps,
resistors, capacitors, diodes and an analog to digital (A/D) converter. The digital approach has crystal
controlled accuracy and no adjustments are required. The frequency-to-voltage transfer function of the
analog version isn’t exactly linear and can change with temperature, power-supply variations and component aging.
Digital Signal Processing (DSP) is an exciting possibility for SSTV demodulators. With DSP, a high
speed A/D converter is used to sample the audio input. After that, it’s all software. DSP can be used to
construct filters that are more flexible, accurate, stable and reproducible than their analog counterparts.
Once you have the tone-frequency information, the real work begins. The next step is to separate the
composite signal into the sync and video components. To reduce the effects of noise, the sync pulses are
cleaned up with a low pass filter and Schmitt trigger. Then, sync is used to control the timing of pixel
sampling. Fig 12.54 contains a high level outline of a program used to receive an 8-s B&W picture.
Receiving colors isn’t much more difficult. For nonRobot modes, gather the R, G, and B scans for each
line, combine them and display a line in color. Robot modes require considerably more calculation to
undo their encoding.
AN INEXPENSIVE SSTV SYSTEM
Here is a color SSTV/FAX480/weatherfax (Fig 12.55) system for IBM PCs and compatibles that is
essentially 99% software! (It most recently appeared in July 1998 QST, pp 23-26.) And this system
transmits, too! The software is available from ARRLWeb. See page viii.
Ben Vester’s, K3BC, work is aimed at the experimentally inclined, so if you’re not familiar with
BASIC programming, be prepared to learn a little about it if you want to maximize the utility of this
system.
Hardware
Fig 12.56 shows a simple circuit used for receiving and transmitting. Connect the output of T2 to the
phone patch input (often labeled LINE INPUT) of your transceiver. If you already have a phone patch, you
can eliminate T2, and connect the line directly to the patch’s phone-line terminals. Nearly all patches
employ transformer isolation, but a simple ohmmeter check will verify that is true of your patch. (Avoid
using the transceiver’s mike input because of possible RF feedback problems.) R3 is set to the proper
level for the audio going to the transmitter. SSTV has a 100% duty cycle signal, so you must set the audio
signal to the transceiver at a
level it can handle without
Set line number, L, to 1
Repeat:
overheating.
Wait for sync
There is no low-pass filterWait for end of sync
ing in the audio line between
If it was vertical sync, set L = 1
the computer output and transmitter audio input. On-the-air
Gather 128 pixels
checks with many stations reDisplay pixels on line L
Increment L
veal that no additional external
If
L > 120, set L = 1
filtering is required when using
SSB transmitters equipped with
Fig 12.55—An example SSTV
Fig 12.54—An outline of typical
mechanical or crystal filters. If
image.
software written to display an
you intend to use this circuit
SSTV frame from received
with an AM or phasing-type digital picture information.
Modulation Sources (What and How We Communicate)
12. 69
SSB rig (or with VHF/UHF FM
transmitters), add audio filtering to provide the required
spectral purity. An elliptical
low-pass filter such as described by Campbell1 should be
adequate for most cases.
Circuit component values
aren’t critical nor is the
circuit’s physical construction.
Do use a socket for the IC. A
PC board is available from
FAR Circuits,2 but perf-board
construction employing short
leads works fine.
The Computer
Fig 12.56—Schematic of the simple SSTV receive and transmit
circuit. This circuit appears on page 34 of July 1998 QST. T1 and T2
are RadioShack 273-1380 audio-output transformers; the 20-µF, 50V capacitor is a parallel combination of two RadioShack 272-999
10-µF, 50-V nonpolarized capacitors; equivalent parts can be
substituted. Unless otherwise specified, resistors are 1/4-W,
5%-tolerance carbon composition or film units. An optional lowpass filter can be used between the output of the computer and the
transmitter's audio-input line (see text). At J1, numbers in parentheses are for 25-pin connectors; other numbers are for 9-pin
connectors.
The most important piece of
hardware is the computer,
which should have an 80286
(or better) microprocessor; a
’386 machine running at 16 or
33 MHz definitely gives better
results. You need a VGA color
monitor that can provide a
640×480, 256-color noninterlaced display and a VGA (usually identified as SVGA) video
adapter card that offers a 640×480×256-color mode.3 The software directly addresses six of the most
common SVGA chip types and also includes a VESA standard choice. If your video adapter card doesn’t
match one of the six, you’ll need a VESA driver for your specific card. If you have trouble finding a
driver, try checking on the Internet.
Software
GWBASIC is the programming tool. Although the guts of the program are contained in assembly
language code (.ASM files), this code is available to the program (and you) through BASIC. All of the modifications to the
core programs (.ASM files) that adapt them to the multitude of 1 R. Campbell, “High-Performance, Single-Signal DirectSSTV/FAX modes are accomplished using BASIC POKEs.
Conversion Receivers,” QST,
This allows experimenters with even a limited knowledge of
Jan 1993, pp 32-40. See also
BASIC programming to make modifications that add other
Feedback, QST, Apr 1993, p 75.
modes, and so on. In deference to a few friends who complained about learning any BASIC, the programs include a 2 FAR Circuits (see Address List
in References chapter). The PC
system configuration list.The program uses this list to deterboard is $4.50, plus $1.50
mine which POKEs to make. This system is strictly keyboard
shipping.
controlled. The software uses a unique technique to get wider
color definition than is normally available with a 256-color 3 Picture quality is degraded with
video card.
an interlaced display.
12.70
Chapter 12
Commercial SSTV Products
All software and computer interfaces are for IBM PC with VGA display unless otherwise noted.
Contact information for each of these sources appears in the Address List in the References chapter.
Scan Converters
DFM 1200 USA—PC Boards and instructions to build a Robot 1200C clone. The builder must
collect EPROM and other parts. Muneki also supplies some of the hard-to-find parts.
Donald P. Lucarell, K8SQL
Felipe Rojas
Muneki Yamafuzi, JF3GOH
SUPERSCAN 2001—Similar to 1200C but with many new features such as: four image memories,
built-in mouse interface, on-screen help messages, and battery back up of CMOS memory to save
system parameters when power is turned off. EPROMs developed by Martin Emmerson. Available
assembled and in various semi-kit options.
Jad Bashour
Tasco (TSC-70U)—A stand-alone color slow-scan TV converter. Receives and transmits color
slow-scan without a PC. For picture storage, a PC interface is an optional module.
Replacement EPROMs—A brand new 1200C was capable of only the “Robot” modes. Martin
supplies replacement EPROMs which add the Martin, Scottie, AVT, Wraase, and fax modes and
other interesting features such as an “oscilloscope” tuning indicator. Product Reviews: Jul 1991, 73
Amateur Radio Today, p 46 (version 4.0); IVCA Newsletter, Fall 1991 (version 4.1); IVCA Newsletter
Spring 1993 (version 4.2)
Martin H. Emmerson MSc, G3OQD
Computer-based SSTV Systems
BMK-MULTY—Software for transmitting and receiving AMTOR, RTTY, CW, PACTOR, Audio
Spectrum Analyzer, HF WEFAX, and SSTV.
Schnedler Systems, AC4IW
MFJ-1278B—MCP for packet radio, RTTY, AMTOR, CW and so on. It is also capable of sending
and receiving most popular SSTV modes with the MultiCom software.
MFJ Enterprises Inc
Pasokon TV— Interface to send and receive SSTV fits inside expansion slot of computer. Software
supports all popular modes, automatic receive mode selection from VIS code, up to 32k simultaneous
colors on screen, graphical user interface with mouse support. Article: Jan 1993, QST, p 20. A free
demo version, called EZSSTV, is available in many of the ham radio software depositories.
Absolute Value Systems
PC SSTV 5—Compact separate send and receive interfaces plug into a serial port. Software supports the most popular modes, reads/writes popular image file formats, built-in text generating capability.
Software Systems Consulting
Slow Scan II— Software to send and receive SSTV using the popular Sound Blaster (or compatible)
sound card instead of interface dedicated to SSTV. Details: May 1993, QEX . A free demo version of
the software is available on CompuServe: Go HAMNET, Library 6, search for “SSTV”,
“SLOWSC.ZIP”.
Harlan Technologies
SSTV Explorer—Low cost, receive-only system for most popular modes. Compact interface plugs
into serial port. Has graphical user interface with mouse support, automatic receive mode selection,
super VGA support with up to 32768 colors. Product Review: April 1994, QST , p 80.
Radioware
Viewport VGA— External interface to send and receive plugs into printer port. Software (shareware
by KA2PYJ) supports most popular modes. Construction article: 73, Aug 1992.
A&A Engineering
Modulation Sources (What and How We Communicate)
12. 71
Accessories and Related Software
ART (Amiga Robot Terminal)—Hardware interface and software to control Robot 1200C from
Amiga computer. Contains paint program, multifont text, and many image processing functions.
Supports Martin and Scottie EPROMs.
Thomas M. Hibben, KB9MC
Audio Analyzer—Software for use with the Sound Blaster. Produces frequency vs time plots of
audio signals. Useful for studying SSTVsignals.
Harlan Technologies
DFM SSTV Bandpass Filter—A bandpass filter especially designed for SSTV.
Donald Lucarell
GEST—”all-in-one” SSTV utility package for the Robot 1200C. Includes paint program, text generation, special effects and image processing tools. Graphical user interface supports CGA, EGA, VGA
and mouse. Controls the 1200C through parallel port.
Torontel
Royal Electronics (Canada)
HiRes—Paint program for use with the Robot 1200C. Has many impressive special effects and
character fonts.
Tom Jenkins, N9AMR
HiRes 32—New version of HiRes designed specifically for use with PC-based SSTV systems.
Requires VGA display adapter capable of 32768 simultaneous colors.
Tom Jenkins, N9AMR
Robot Helper—Robot 1200C control program for Microsoft Windows and OS/2 environments.
Some features include: thumbnail previews of images on disk, dual image preview windows, fast
image load and save to Robot, support for Robot or Martin EPROMs.
William Montgomery, VE3EC
SCAN—Software for use with Robot 1200C.
Bert Beyt, W5ZR
Some Program Details
One of the common SSTV practices is to retransmit a picture you just received so other SSTVers not
copying the originating station can see the image. This capability is included.
RT.BAS is the receive and retransmit program. On receive, you simply choose the mode from a menu,
and wait for the picture transmission to complete. As of this writing, Robot 36 and 72 modes are available
in either a synchronous or a line-synced mode. Other modes (all synchronous) are Scottie 1 and 2, Martin
1 and 2, AVT90, AVT94, Wraase 96, FAX480 and weatherfax.
When receiving, if you fail to get the mode selection made in time to catch the frame sync, you can
go directly to copying by pressing the keyboard’s spacebar. On all but the AVT modes, the next line sync
is picked up and starts the picture. The AVT modes copy out of sync. Because the program allows you
to scroll horizontally across the RGB color frames, you can resync after the picture has been received.
A few images have nonstandard color registration, so the program can adjust color registration after the
picture is received. You also can save the picture—usually after you have scrolled the picture so the CRT
screen frames just the part you want to keep.
TX.BAS is used for transmitting any picture file. When queried, you provide the mode and the file
name, and after a brief pause while the picture loads, press G(o) to transmit. To avoid additional
switching complexity, VOX transmitter switching is used.
VU.BAS allows you to view a picture. It has the same adjustments available as RT.BAS. One feature
(applicable only to the Robot modes) is the ability to “retune” the picture (in 10-Hz increments) as you
view its color balance.
12.72
Chapter 12
SLIDESHO.BAS gives you the vehicle to display a bunch of pictures as a slide show. Place
SLIDESHO.BAS in a directory contained in your PATH statement so it can be called up from
anywhere.
TIFCONV.BAS converts 640×480, 24-bit color, TIFF pictures into a format that can be transmitted
by any of the supported SSTV modes except Robot. TIFF is a common format used to transfer higherresolution pictures between programs. This program works with the Computer Eyes/RT4 and Software
Systems Consulting5 frame grabbers. The picture output from this program can be viewed with VU.BAS
and, of course, is bound by 320×240 with 18-bit color.
LABEL.BAS allows you to add call signs and other text to the SSTV pictures. It takes any black-andwhite TIFF (that is, 1-bit) file and creates a mask cutout where the black is. You can superimpose the
cutout over an SSTV picture either in any color you want, or transfer a cutout of any background file
you find interesting. The letters will then look like they were cut out of the background picture. Obviously, you can use squares or circles in addition to fonts to transfer a piece of one file onto another one.
Use a cheap hand scanner to capture interesting fonts you find. You can get a three-dimensional effect
by painting a color through the mask, then moving the mask a few pixels and rerunning the data through
LABEL with a background file or another color. Or, run several different masks through LABEL in
sequence to obtain different colors or patterns on different letters.
Work with Ben Vester’s system continues. Look at articles by Vester in the SSTV Bibliography and
watch QST for more discussion.
SUMMARY
For decades there was a convenient excuse for not trying SSTV: it cost kilobucks to buy a specialized
piece of equipment. But you can’t use that excuse anymore. There are several free programs that only
require trivial interfaces to receive pictures. Once you get hooked, there are plenty of other home-brew
projects and commercial products available at affordable prices. You need not be a computer wizard to
install and use these systems.
SSTV is a rapidly changing area of Amateur Radio. Although
4 ComputerEyes R/T by Digital
it is still supported, the once-popular Robot 1200C has been
Vision (see Address List in
discontinued. Many new products have been introduced.
References chapter).
SSTV Bibliography
5
Abrams, C., and R. Taggart, “Color Computer SSTV,” 73, Nov
and Dec 1984.
Software Systems Consulting
(see Address List in References
chapter).
For More Information
Contact information for each of these sources
appears in the Address List in the References
chapter.
Weekly nets:
Saturdays, 1500 UTC 14.230 MHz.
Saturdays, 1800 UTC 14.230 MHz.
SSTV Newsletter:
VISION from International Visual Communications Association (IVCA)
Magazines specializing in ATV:
Amateur Television Quarterly
ATV Today!
CQ-TV from British Amateur Television Club
The SPEC-COM Journal
Old A5 magazine reprints:
ESF copy services
Handbook:
Slow Scan Television Explained, by Mike Wooding, G6IQM (available from British Amateur Television Club and Amateur Television Quarterly).
Modulation Sources (What and How We Communicate)
12. 73
Battles, B. and S. Ford, “Smile—You’re on Ham Radio!” QST, Oct 1992, p 42.
Bodson, D., W4PWF, and Karty, S., N5SK, “FAX480 and SSTV Interfaces and Software,” QST, Jul
1998, pp 32-36.
Cameroni, G., I2CAB, and G. Morellato, I2AED (translated by Jim Grubbs, K9EI), “Get on SSTV—
with the C-64,” Ham Radio, Oct 1986, p 43.
Churchfield, T., K3HKR, “Amiga AVT System,” 73 Amateur Radio, Jul 1989, p 29.
Goodman, D., WA3USG, “SSTV with the Robot 1200C Scan Converter and the Martin Emmerson
EPROM Version 4.0,” 73 Amateur Radio Today, Jul 1991, p 46.
Langner, J., WB2OSZ, “Color SSTV for the Atari ST,” 73 Amateur Radio, Dec 1989, p 38; Jan 1990,
p 41.
Langner, J., WB2OSZ, “SSTV—The AVT System Secrets Revealed,” CQ-TV 149 (Feb 1990), p 79.
Langner, J. WB2OSZ, “Slow Scan Television—It isn’t expensive anymore,” QST, Jan 1993, p 20.
Montalbano, J., KA2PYJ, “The ViewPort VGA Color SSTV System,” 73, Aug 1992, p 8.
Schick, M., KA4IWG, “Color SSTV and the Atari Computer,” QST, Aug 1985, p 13.
Taggart, R., WB8DQT, “The Romscanner,” QST, Mar 1986, p 21.
Taggart, R., WB8DQT, “A New Standard for Amateur Radio Facsimile,” QST, Feb 1993, p 31.
Vester, B., K3BC "Vester SSTV/FAX80/Fax System Upgrades," Technical Correspondence, QST,
Jun 1994, pp 77-78.
Vester, B., K3BC, "SSTV: An Inexpensive System Continues to Grow," Dec 1994 QST, pp 22-24.
Vester, B., K3BC, “K3BC’s SSTV Becomes TRUSCAN,” Technical Correspondence, QST, Jul 1996,
pp66-67.
12.74
Chapter 12
FAST-SCAN TELEVISION
Fast-scan amateur television (FSTV or just ATV) is a wide-band mode that uses standard broadcast,
or NTSC, television scan rates. It is called “fast scan” only to differentiate it from slow-scan TV. In fact,
no scan conversions or encoder/decoders are necessary with FSTV. Any standard TV set can display the
amateur video and audio. Standard (1 V P-P into 75 Ω) composite video from home camcorders,
cameras, VCRs or computers is fed directly into an AM ATV transmitter. The audio has a separate
connector and goes through a 4.5 MHz FM subcarrier generator which is mixed with the video. This
section was written by Tom O’Hara, W6ORG.
Amateurs regularly show themselves in the shack, zoom in on projects, show home video tapes,
computer programs and just about anything that can be shown live or by tape (see Figs 12.57 and 12.58).
Whatever the camera “sees” and “hears” is faithfully transmitted, including color and sound information.
Picture quality is about equivalent to that of a VCR, depending on video signal level and any interfering
carriers. All of the sync and signal-composition information is present in the composite-video output of
modern cameras and camcorders. Most camcorders have an accessory cable or jacks that provide separate video and audio outputs. Audio output may vary from one camera to the next, but usually it has been
amplified from the built-in microphone to between 0.1 to 1 V P-P (into a 10-kΩ load).
ATV transmitters have been carried by helium balloons to above 100,000 ft, to the edge of space. The
result is fantastic video transmissions, showing the curvature of the Earth, that have been received as far
as 500 miles from the balloon. Small cameras have been put into the cockpits of R/C model airplanes
to transmit a pilot’s-eye view. Many ATV repeaters retransmit Space Shuttle video and audio from
NASA during missions. This is especially exciting for schools involved with SAREX. ATV is used for
public service events such as parades, races, Civil Air Patrol searches and remote damage assessment.
Emergency service coordinators have found that live video from a site gives a better understanding
of a situation than is possible from voice descriptions alone. Weather-radar video, WEFAX, or other
computer generated video has also been carried by ATV transmitters for RACES groups during significant storms. This use enables better allocation of resources by presenting real-time information about
the storm track. Computer graphics and video special effects are often transmitted to dazzle the viewers.
How Far Does ATV Go?
The theoretical snow-free line-of-sight distance for 10 W, given 15.8-dBd antennas and 2-dB feedline loss at both ends, is 91 miles. (See Table 12.16.) However, except for temperature-inversion skip
conditions, reflections, or through high hilltop repeaters, direct line-of-sight ATV contacts seldom
exceed 25 miles. The RF horizon over flat terrain with a 50ft tower is 10 miles. For best
DX use low loss feed line and a
broadband high-gain antenna,
up as high as possible. The antenna system is the most important part of an ATV system
because it affects both receive
and transmit signal strength.
A snow-free, or “P5,” picture rating (see Fig 12.59) reFig 12.58—The ATV view shows
quires at least 200 µV (–61
Fig 12.57—Students enjoy using the aft end of the Space Shuttle
dBm) of signal at the input of
ATV to communicate between
cargo bay during mission
science and computer classes.
the ATV receiver, depending
STS-9.
Modulation Sources (What and How We Communicate)
12. 75
Table 12.16
Line-of-Sight Snow-Free 70-cm ATV Communication
Distances
This table relates transmit and receive station antenna gains to communication distances in miles for 1/10/100 W PEP at 440 MHz. To find the
possible snow-free distance under line-of-sight conditions, select the
column that corresponds to transmit antenna gain and the row for the
receive antenna gain. Read the distance where the row and column
intersect. Multiply the result by 0.5 for 902 MHz and 0.33 for 1240 MHz.
The table assumes 2 dB of feed-line loss, a 3 dB system noise figure at
both ends and snow-free is greater than 40 dB picture:noise ratio (most
home cameras give 40 to 45 dB picture:noise; this is used as the
limiting factor to define snow-free ATV pictures). The P unit picture
rating system goes down about 6 dB per unit. For instance, P4 pictures
would be possible at double the distances in the table.
RX Antenna
0 dBd
4 dBd
9 dBd
15.8 dBd
0 dBd
TX Antenna
4 dBd
9 dBd
15.8 dBd
0.8/2.5/8
1/3.5/11
2/7/22
5/15/47
1/3.5/11
2/6/19
3.5/11/34
7.5/23/75
5/15/47
7.5/23/75
13/42/130
29/91/290
2/7/22
3.5/11/34
6/19/60
13/42/130
on the system noise figure and bandwidth. The noise floor increases
with bandwidth. Once the receiver system gain and noise figure
reaches this floor, no additional gain will increase sensitivity. At 3MHz bandwidth the noise floor is 0.8 µV (–109 dBm) at standard
temperature. If you compare this to an FM voice receiver with 15
kHz bandwidth; there is a 23 dB difference in the noise floor. However the eye, much like the ear of experienced CW operators, can
pick out sync bars in the noise below the noise floor. Sync lock and
large well contrasted objects or lettering can be seen between 1 and
2 µV. Color and subcarrier sound come out of the noise between 2
and 8 µV depending on their injection level at the transmitter and
TV-set differences.
Two-meter FM is used to coordinate ATV contacts. Operators
must take turns transmitting on the few available channels and the
2-m link allows full-duplex audio from many receiving stations to
the ATV transmitting station, who is speaking on the sound
subcarrier. This is great for interactive show and tell. Also it is much
easier to monitor a squelched 2-m channel using an omni antenna
rather than searching out each station with a beam. Depending on the
third-harmonic relationship to the video on 70 cm, 144.34 MHz and
146.43 MHz (simplex) are the most popular frequencies; they are
often mixed with the subcarrier sound on ATV repeater outputs.
P5 —Excellent
P4—Good
P3—Fair
P2—Poor
Getting the Picture
P1—Barely perceptible
Since the 70-cm band corresponds to cable channels 57 through 61,
seeing your first ATV picture may be as simple as connecting a good
Fig 12.59—An ATV quality
reporting system.
12.76
Chapter 12
outside 70-cm antenna (aligned for the customary local polarization) to a cable-ready TV set’s antenna input
jack. Cable channel 57 is 421.25 MHz, and each channel is progressively 6 MHz higher. (Note that cable and
broadcast UHF channel frequencies are different.) Check the ARRL Repeater Directory for a local ATV
repeater output that falls on one of these cable channels. Cable-ready TVs may not be as sensitive as a lownoise downconverter designed just for ATV, but this technique is well worth a try.
Most stations use a variable tuned downconverter specifically designed to convert the whole amateur
band down to a VHF TV channel. Generally the 400 and 900 MHz bands are converted to TV channel
3 or 4, whichever is not used in the area. For 1200 MHz converters, channels 7 through 10 are used to
get more image rejection. The downconverter consists of a low-noise preamp, mixer and tunable or
crystal controlled local oscillator. Any RF at the input comes out at the lower frequencies. All signal
processing is done in the TV set. A complete receiver with video and audio output would require all the
TV sets circuitry, less the sweep and CRT components. There is no picture-quality gain by going direct
from a receiver to a video monitor (as compared with a TV set) because IF and detector bandwidth are
still the limiting factors.
A good low-noise amateur downconverter with 15 dB gain ahead of a TV set will give sensitivity close
to the noise floor. A preamp located in the shack will not significantly increase sensitivity, but rather will
reduce dynamic range and increase the probability of intermod interference. Sensitivity can be increased
by increasing antenna-system gain: reducing feed-line loss, increasing antenna gain or adding an antenna
mounted preamp (which will eliminate the coax loss plus any loss through transmit linear amplifier TR
relays). Remember that each 6 dB increase in combination of transmitted power, reduced coax loss,
antenna gain or receiver sensitivity can double the line-of-sight distance.
Foliage greatly attenuates the signal at UHF, so place antennas above the tree tops for the best results.
Beams made for 432-MHz weak-signal work or 440-MHz FM may not have enough SWR bandwidth
to cover all the ATV frequencies for transmiting, but they are okay for reception. A number of manufacturers now make ATV beam antennas to cover the whole band from 420 to 450 MHz. Use low-loss
coax (such as Belden 9913: 2.5 dB/100 ft at 400 MHz) or Hardline for runs over 100 ft. All outside
connectors must be weatherproofed with tape or coax sealer; any water that gets inside the coax will
greatly increase the attenuation. Almost all ATV antennas use N connectors, which are more resistant
to moisture contamination than other types.
Antenna polarization varies from area to area. Technically, the polarization should be chosen to give
additional isolation (up to 20 dB) from other users near the channel. It is more common to find that the
polarity was determined by the first local ATV operators (which antennas they had in place for other
modes). Generally, those on 432 MHz SSB and weak-signal DX
have horizontally polarized antennas, and those into FM, public
service or repeaters will have vertical antennas. Check with local
ATV operators before permanently locking down the antennamast clamps. Circularly polarized antennas let you work all modes,
including satellites, with only 3 dB sacrificed when working a
fixed polarity.
ATV Frequencies
Standard broadcast TV channels are 6 MHz wide to accommodate the composite video, 3.58 MHz color and 4.5 MHz sound
subcarriers. (See Fig 12.60.) Given the NTSC 525 horizontal line
and 30 frames per second scan rates, the resulting horizontal resolution bandwidth is 80 lines per MHz. Therefore, with the typical
TV set’s 3-dB rolloff at 3 MHz (primarily in the IF filter), up to
240 vertical black lines can be seen. Color bandwidth in a TV set
Fig 12.60—A 6-MHz video channel with the video carrier
1.25 MHz up from the lower edge.
The color subcarrier is at
3.58 MHz and the sound
subcarrier at 4.5 MHz above the
video carrier.
Modulation Sources (What and How We Communicate)
12. 77
is less than this, resulting in up to 100 color lines. Lines of resolution are often confused with the number
of horizontal scan lines per frame. The video quality should be every bit as good as on a home video
recorder.
The lowest frequency amateur band wide enough to support a TV channel is 70 cm (420 - 450 MHz),
and it is the most popular. With transmit power, antenna gains and coax losses equal, decreasing frequency increases communication range. The 33-cm band goes half the distance that 70 cm does, but this
can be made up to some extent with high-gain antennas, which are physically smaller at the higher
frequency. A Technician class or higher license is required to transmit ATV on this band, and Novices
can transmit ATV only in the 1270 to 1295 MHz segment of the 23-cm band.
Depending on local bandplan options, there is room for no more than two simultaneous ATV
channels in the 33- and 70-cm bands without interference. Unlike cable channels, broadcast TV
signals must skip a channel to keep a strong adjacent channel signal from interfering with a weaker
on-channel signal. Cable companies greatly filter and equalize the signal amplitudes in order to use
every channel.
Generally, because only two channels are available in the 70-cm band, an ATV repeater input
on 439.25 or 434.0 MHz is shared with simplex. 421.25 MHz is the most popular in-band repeater
output frequency. At least 12 MHz of separation is necessary for in-band repeaters because of
filter-slope attenuation characteristics and TV-set adjacent-channel rejection. Some repeaters have
their output on the 33-cm or 23-cm (the 923.25 and 1253.25 MHz output frequencies are most
popular) bands which frees up a channel on 70 cm for simplex. Such cross-band repeaters also
make it easier for the transmitting operator to monitor the repeated video with only proper antenna
separation to prevent receiver desensitization. 426.25 MHz is used for simplex, public service and
R/C models in areas with cross-band repeaters, or as a alternative to the main ATV activities on
434.0 or 439.25 MHz. Before transmitting, check with local ATV operators, repeater owners and
frequency coordinators listed in the ARRL Repeater Directory for the coordinated frequencies used
in your area.
Since a TV set receives a 6-MHz bandwidth, ATV is more susceptible to interference from many other
sources than are narrower modes. Interference 40 dB below the desired signal can be seen in video. Many
of our UHF (and above) amateur bands are shared with radar and other government radio positioning
services. These show up as horizontal bars in the picture. Interference from amateurs who are unaware
of the presence of the ATV signal (or in the absence of a technically sound and publicized local band
plan) can wipe out the sound or color or put diagonal lines in the picture.
DSB and VSB Transmission
While most ATV is double sideband (DSB) with the widest
component being the sound subcarrier out plus and minus
4.5 MHz, over 90% of the spectrum power is in the first 1 MHz on
both sides of the carrier for DSB or VSB (vestigial sideband). As
can be seen in Fig 12.61, the video power density is down more
than 30 dB at frequencies greater than 1 MHz from the carrier.
DSB and VSB are both compatible with standard TV receivers,
but the lower sound and color subcarriers are rejected in the TV
IF filter as unnecessary. In the case of VSB, less than 5% of the
lower sideband energy is attenuated. The other significant energy
frequencies are the sound (set in the ATV transmitter at 15 dB
below the peak sync) and the color at 3.58 MHz (greater than
22 dB down).
Narrow-band modes operating greater than 1 MHz above or
12.78
Chapter 12
Fig 12.61—A spectrum-analyzer
photo of a color ATV signal. Each
vertical division represents
10 dB; horizontal divisions are
1 MHz. Spectrum power density
varies with picture content, but
typically 90% of the sideband
power is within the first 1 MHz.
below the video carrier are rarely interfered with or know that the ATV transmitter is on unless the
narrow-band signal is on one of the subcarrier frequencies or the stations are too near one another.
If the band is full and the lower sideband color and sound subcarrier frequencies need to be used
by a dedicated link or repeater, a VSB filter in the antenna line can attenuate them another 20 to
30 dB, or the opposite antenna polarization can be used for more efficient packing of the spectrum.
Since all amateur linear amplifiers re-insert the lower sideband to within 10 dB of DSB, a VSB
filter in the antenna line is the only cost-effective way to reduce the unnecessary lower sideband
subcarrier energy if more than 1 W is used. In the more populated areas, 2-m calling or coordination frequencies are often used to work out operating time shifts, and so on, between all users
sharing or overlapping the same segment of the band.
ATV Identification
ATV identification can be on video or the sound subcarrier. A large high-contrast call-letter sign on
the wall behind the operating table in view of the camera is the easiest way to fulfill the requirement.
Transmitting stations fishing for DX during band openings often make up call-ID signs using fat black
letters on a white background to show up best in the snow. Their city and 2-m monitoring frequency are
included at the bottom of the sign to make beam alignment and contact confirmation easier.
Quite often the transmission time exceeds 10 minutes, especially when transmitting demonstrations,
public-service events, space-shuttle video, balloon flights or a video tape. A company by the name of
Intuitive Circuits makes a variety of boards that will overlay text on any video looped through them. Call
letters and other information can be programmed into the board’s non-volatile memory by on-board push
buttons or an RS-232 line from a computer (depending on the version and model of the OSD board).
There is even a model that will accept NMEA-0183 GPRMC data from a GPS receiver and overlay
latitude, longitude, altitude, direction and speed as well as call letters on the applied camera video. This
is ideal for ATV rockets, balloons and R/C vehicles. The overlaid ID can be selected to be on, off or
flashed on for a few seconds every 10 minutes to automatically satisfy the ID requirement of 97.119 (see
Fig 12.62). The PC Electronics VOR-2 board has an automatic nine minute timer, but it also has an endof-transmission hang timer that switches to another video source for ID.
A 20-W ATV Transceiver
Many newcomers to ATV start out by buying an inexpensive downconverter board just to check out
the local simplex or repeater activity. Once they see a picture it
isn’t long before they want to transmit. The downconverter board
can be kept separate or put in a larger chassis with transmitter
boards to make one convenient package, as shown in Fig 12.63.
All the modules shown here are available wired and tested from
PC Electronics and are also functionally representative of what is
available from other suppliers. Fig 12.64 shows a block diagram
of this transceiver.
The complete 20-W ATV transceiver consists of the
• TVC-2G downconverter (420 - 450 MHz in, TV channel 2, 3 or
4 out)
• TXA5-70 80 mW exciter/modulator
• FMA5-F 4.5-MHz sound subcarrier generator
• PA5-70 20-W brick linear amplifier
• DMTR video detector, video monitor driver and TR relay modules.
Fig 12.62—A photo of an ATV
image of the Space Shuttle
interior with K6KMN’s repeater ID
overlaid. Automatic video overlay
in the picture easily solves the
10-minute ID requirement for
Space Shuttle retransmissions
and other long transmissions.
Modulation Sources (What and How We Communicate)
12. 79
The modules must be
mounted in an aluminum enclosure for RF shielding and heat
sinking. A 2.5×7×7-inch or
larger aluminum chassis and
bottom cover will make a nice
transceiver. The Hammond
1590F diecast aluminum box
(A)
makes a more rugged and RF
(B)
tight enclosure. Lay all the
modules in the selected chassis
to position for best fit before
drilling the mounting holes.
Board wiring and mounting layouts come with each module.
Mount the PA5-70 amplifier
and DMTR TR relay on the
back panel, with the Mitsubishi
M57716 RF power module as
low as possible for best air flow.
Unscrew the power module and
its board from the heatsink and
poke through the four mounting
holes and a piece of paper with
a pencil. Use this as a template
to center punch the drill locations on the chassis from the
outside. Make sure the heatsink
will mount at least 1/ 8 inch
above the bottom edge of the
chassis. Drill the 3/16-inch diameter holes and carefully
debur each side. The M57716
must be on a perfectly flat surface or the ceramic substrate
could crack when its mounting
bolts are tightened. Use a thin
layer of heatsink compound under both the M57716 and the
Fig 12.64—Block diagram of a complete ATV station using the 20-W
heatsink. Mount the M57716
transceiver.
and its board inside the chassis,
and the heatsink outside by running the four screws from the M57716 side through the chassis into the heatsink.
The DMTR TR relay board mounts directly on a flange N UG58 chassis connector. Use RG-174 (small
50-Ω coax) for the RF leads to the amplifier and downconverter modules. To minimize RF coupling
inside the chassis, carefully dress the coax braid back over its outer insulation (no more than 1/4 inch)
and solder the shield directly to the board ground planes. When soldering, make sure there are no bends
or stress on the coax. Do not twist the braid into a “pig tail” at UHF.
Fig 12.63—A is the front view
of a complete ATV transceiver
and B is the inside view. This
complete 20-W 70-cm ATV
transceiver is assembled from
readily available built and
tested modules and mounted
in a Hammond 1590F die-cast
aluminum enclosure. On the
box floor, left to right: TVC-2G
downconverter, FMA5-F
4.5-MHz sound subcarrier
generator and TXA5-70 80-mW
exciter/video modulator. On
the back (top left) is the
downconverter-to-TV F connector and a 4-pin mic jack
(which serves as the +13.8 V dc
input). To the right is the
DMTR TR relay board mounted
to a flanged N connector. On
the inside in front of the
heatsink is the PA5 20-W
power-amplifier module using
a Mitsubishi M57716.
12.80
Chapter 12
A four-pin mic jack is used for the +13.8 V dc power connector. It is wired through a 4 A fast-acting
fuse to the SPST POWER switch. The two unused pins can be used to control or power external devices
such as a camera. A 1N4745A 16-V, 1-W Zener diode is connected from the transceiver side of the fuse
to ground to help protect the circuits in case of accidental or reverse voltage. The downconverter, exciter
and subcarrier generator can be mounted inside the chassis with #4-40×1/2 screws with double nuts for
spacers (see module board mounting detail). Again, keep the exposed length of the interconnecting
RG-174 center conductor less than 1/4 inch. Solder the coax carefully and check with an ohmmeter for
shorts. Use #18 wire for the amplifier power leads and #22 solid wire for all of the other wiring. Dress
all dc leads away from the RF coaxes and the power module. The video and audio leads, and the panelpot connections, can be #22 twisted pair (up to 6 inches long). Use RG-174 for longer runs.
You may want to remove and change some of the board mounted trimpots to panel mounted
potentiometers to make adjustments easier. (For example, the video gain on the exciter, the mic and line
gain on the sound subcarrier board, and the down-converter frequency tuning may be changed.) Remove
the trimpots and run three wires from the mounting holes to their respective carbon (no wire wounds as
they are inductive at video frequencies) panel potentiometers. 100-Ω carbon panel controls for the video
gain are difficult to find, but they are available from PC Electronics.
For RF purposes, bypass each video input connector (100-pF ceramic disc capacitor) and each audio
connector (220-pF disc) directly at the connector with short leads.
Most camcorders use phono jacks for the composite-video and line-audio connections. A low-impedance mic with push-to-talk can be used in parallel with the camera or VCR audio, which is mixed in the
sound subcarrier board and the transmit receive toggle switch. An F connector on the back panel supplies
downconverter output to the TV set antenna input. Use 75-Ω coax for the line to the TV. (300-Ω twin
lead picks up too much interference from strong adjacent-channel broadcast TV stations.) Do not put any
other boards inside the chassis that might be RF susceptible.
Transceiver Checkout
Use an ohmmeter to verify that there are no short circuits in the coax or +13.8 V dc leads. (The antenna
input will show a short because of the stripline tuned circuit.) Connect a good resonant 70-cm antenna,
do not run a piece of wire or other band antenna just to try it out. With the transceiver off, connect the
downconverter output coax to the TV set antenna jack. Switch the TV set on and select a channel that
is not used in your area, usually 3 or 4. Adjust the fine tuning for minimum adjacent-channel interference.
Then turn on the transceiver and adjust the downconverter tuning for a known nearby ATV station that
you have contacted on 2 m. Peak the input trimmer cap on the TR relay board for minimum snow.
Next, with no video connected, switch the transmitter on for no more than 10 seconds at a time while
verifying that you have less than 1 W of reflected power (as shown by an RF power meter in the antenna
line). Continued transmission into an SWR of more than 2:1 can damage the SAU4 power module. If
the SWR is low, peak the trimmer cap on the DMTR board for maximum output, then proceed to set the
blanking pedestal pot on the TXA5-70 exciter.
ATV is a complex waveform that requires that the video to sync ratio remains constant throughout all
of the linear amplifiers and with camera contrast changes (see Fig 12.65). The modulator contains a
blanking clamp circuit that also acts as a sync stretcher to compensate for amplifier gain compression.
To set this level, the pedestal control is set to maximum power output and then backed off to 60% of that
value. The sync tip, which is the peak power, is constant at the maximum power read and the blanking
level is the 60% point. This procedure must be repeated anytime a different power amplifier is added or
applied voltage is changed by more than 0.5 V. Any other RF power measurements with an averaging
power meter under video modulation are meaningless.
The camera video can now be connected, and the video gain set for best picture as described by the
receiving station (or by observing a video monitor connected to the output jack on the DMTR board). Be
Modulation Sources (What and How We Communicate)
12. 81
careful not to overmodu-late.
Overmodulation is indicated by
white smearing in the picture
and sync buzz in the audio.
Connect a low-impedance
(150 Ω to 600 Ω) dynamic mic
(Radio Shack has some tape recorder replacements with a
push-to-talk switch) into the mic
jack and adjust the audio gain to
a comfortable level as described
by the receiving station. Electret
mics are not good for this application because they are more
susceptible to RF pickup (sympFig 12.65—An ATV waveform. Camera and corresponding transmittom: sync buzz in the audio). RF
ter RF output power levels during one horizontal line scan for
pickup may also be a problem
black-and-white TV. (A color camera would generate a “burst”of 8
with inadequately shielded mic
cycles at 3.58 MHz on the back porch of the blanking pedestal.)
cords. For example, it may be
Note that “black” corresponds to a higher transmitter output power
than does “white.” For the purposes of blanking pedestal setup
necessary to replace a cord havwith a RF power meter rather than an oscilloscope, the 75% PEV
ing a spiral wrapped shield with
corresponds to slightly less than 60% power.
one that has a braided shield, in
order to improve shielding at
UHF. The FMA5-F board has a soft limiter that comes in at the standard 25-kHz deviation.
The line-audio input has an independent volume control for the camcorder amplified mic or VCR
audio, which is mixed with the low impedance mic input. This feature is great for voice-over commenting during video tapes.
Driving Amplifiers with ATV
Wide-band AM video requires some special design considerations for linear amplifiers (as compared
to those for FM and SSB amplifiers). Many high-power amateur amplifiers would oscillate (and possibly
self destruct) from high gain at low frequencies if they were not
protected by feedback networks and power RF chokes. These same
stability techniques can affect some of the 5-MHz video bandwidth. Sync, color and sound can be very distorted unless the
amplifier has been carefully designed for both stability and AM
video modulation.
Mirage, Teletec and Down East Microwave either make special
ATV amplifiers or offer standard models that were designed for all
modes, including ATV. Basically the collector and base bias supplies have a range of capacitors to keep the voltage constant under
modulation while at the same time using the minimum-value lowresistance series inductors or chokes to prevent self oscillation.
Fig 12.66—An oscilloscope used
Almost all amateur linear power amplifiers have gain compression to observe a video waveform. The
from half to their full rated peak envelope power. To compensate for lower trace is the video signal
it comes out of the sync
this, the ATV exciter/modulator has a sync stretcher to maintain the as
stretcher. The upper trace is the
proper transmitted video to sync ratio (see Fig 12.66). With both
signal from the Mirage D1010-N
video and sound subcarrier disconnected, the pedestal control is set amplifier.
12.82
Chapter 12
for maximum power output. Peak sync should first be set to 90% of the rated peak envelope power. (This is
necessary to give some head room for the 4.5 MHz sound that is mixed and adds with the video waveform.)
The TXA5-70 exciter/modulator has a RF power control to set this. Once this is done, the blanking pedestal
control can be set to 60% of the peak sync value. For example, a 100-W amplifier would first be set for
90 W with the RF power control and then 54 W with the pedestal control. Then the sound subcarrier can be
turned back on and the video plugged in and adjusted for best picture. If you could read it on a peak-reading
power meter made for video, the power is between 90 and 100 W PEP. On a dc oscilloscope connected to a
RF diode detector in the antenna line, it can be seen that the sync and blanking pedestal power levels remain
constant at their set levels regardless of video gain setting or average picture contrast. On an averaging meter
like a Bird 43, however, it is normal to read something less than the pedestal set up power.
ATV Repeaters
Basically there are two kinds of ATV repeaters: in band and cross band. 70-cm in-band repeaters are
more difficult to build and use, yet they are more popular because equipment is more available and less
expensive. Indeed, cable-ready TV sets tune the 70-cm band with no modifications.
Why are 70-cm repeaters more difficult to build? The wide bandwidth of ATV makes for special filter
requirements. Response across the 6-MHz passband must be as flat as possible with minimum insertion
loss, but also must sharply roll off to reject other users as little as 12 MHz away. Special multipole
interdigital or combline VSB filters are used to meet the requirement. An ATV duplexer can be used to
feed one broadband omnidirectional antenna, but an additional VSB filter is needed in the transmitter
line for sufficient attenuation of noise and IMD products.
A cross-band repeater, because of the great frequency separation between the input and output, requires
less sophisticated filtering to isolate the transmitter and receiver. In addition, a cross-band repeater makes
it easier for users to see their own video (no duplexer is needed, only sufficient antenna spacing). Repeater
linking is easier too, if the repeater outputs alternate between the 23- and 33-cm bands.
Fig 12.67 shows a block diagram for a simple 70-cm in-band repeater. No duplexer is shown because
Fig 12.67—A block diagram of a 70-cm in-band ATV repeater. The antennas are Diamond omnidirectional verticals, which require 20 ft (minimum) of vertical separation to prevent receiver
desensitization. The VSB filters are made by DCI; they have the proper band-pass characteristics and
only 1 dB insertion loss. A low pass filter on the reciever is also necessary because cavity type filters
repeat a pass-band at odd harmonics and the third-harmonic energy from the transmitter may not be
attenuated enough. The receiver, 10-W transmitter and VOR are made by PC Electronics. The Communications Specialists DTD-1 DTMF decoder and ID8 Morse identifier (optional if a video ID is used)
are used to remotely turn the repeater transmitter on or off and to create a CW ID, respectively.
Alternatively, an Intuitive Circuits ATV4-4 ATV repeater controller board can do all the control box
functions as well as remotely select from up to four video sources.
Modulation Sources (What and How We Communicate)
12. 83
the antennas and VSB filters provide adequate isolation. The repeater transmitter power supply should be
separate from the receiver and exciter supply. ATV is amplitude modulated, therefore the current varies
greatly from maximum at the sync tip to minimum during white portions of the picture. Power supplies are
not generally made to hold tight regulation with such great current changes at rates up to several megahertz.
Even the power supply leads become significant inductors at video frequencies; they will develop a voltage
across them that can be transferred to other modules on the same power-supply line.
To prevent unwanted key up from other signal sources, ATV repeaters use a video operated relay
(VOR). The VOR senses the horizontal sync at 15,734 Hz in much the same manner that FM repeaters
use CTCSS tones. Just as in voice repeaters, an ID timer monitors VOR activity and starts the repeater
video ID generator every nine minutes or a few seconds after a user stops transmitting.
Frequency Modulated ATV (FMATV)
While AM is the most popular mode because of greater equipment availability, lower cost, less
occupied bandwidth and use of a standard TV set, FMATV is gaining interest among experimenters and
also repeater owners for links. FM on the 1200-MHz band is the standard in Europe because there is little
room for video in their allocated portion of the 70-cm band. FMATV occupies 17 to 21 MHz depending
on deviation and sound subcarrier frequency. The US 70-cm band is wide enough but has great interference potential in all but the less populated areas. Most available FMATV equipment is made for the
1.2, 2.4 and 10.25-GHz bands. Fig 12.68 is a block diagram of an FMATV receiver.
The US standard for FMATV is 4 MHz deviation with the 5.8-MHz sound subcarrier set to 10 dB
below the video level. 1252 or 1255 MHz are suggested frequencies in order to stay away from FM voice
repeaters and other users higher in the band while keeping sidebands above the 1240-MHz band edge.
Using the US standard with Carsons rule for FM occupied bandwidth, it comes out to just under 20 MHz.
So 1250 MHz would be the lowest possible frequency. Almost all modern FMATV equipment is synthesized, but if yours is not, use a frequency counter to monitor the frequency for warm up drift. Check
with local frequency coordinators before transmitting because the band plan permits other modes in that
segment.
Fig 12.68—Block diagram of an FMATV receiver.
12.84
Chapter 12
Experimentally, using the
US standard, FMATV gives increasingly better picture-tonoise ratios than AMATV at
receiver input signals greater
than 5 µV. Because of the wider
noise bandwidth and FM
threshold effect, AM video can
be seen in the noise well before
FM. For DX work, it has been
shown that AM signals are recognizable signals in the snow at
four times (12 dB) greater distance than FM signals with all
other factors equal. Above the
FM threshold, however, FM
rapidly overtakes AM; snowfree pictures occur above 50
µV, or 4 times farther away Fig 12.69—Two approaches to ATV receiving. This chart compares
than with AM signals. The AM (A) and FM (F) ATV as seen on a TV receiver and monitor.
Signal levels are into the same downconverter with sufficient gain
crossover point is near the sig- to be at the noise floor. The FM receiver bandwidth is 17 MHz,
nal level where sound and color using the US standard.
begin to appear for both systems. Fig 12.69 compares AM
and FMATV across a wide range of signal strengths.
There are a variety of methods to receive FMATV. Older satellite receivers have a 70 or 45-MHz input
and require a down converter with 40 to 50 dB gain ahead of them. Also satellite receivers are made for
wider deviation and need some video gain to give the standard 1 volt peak to peak video output when
receiving a signal with the standard 4-MHz deviation. Current satellite receivers directly tune anywhere
from 900 to 2150 MHz and they only need a preamp added at the antenna for use on the 33 and 23-cm
ham bands. The additional video gain can often be had by adjusting an internal pot or changing the gain
with a resistor.
Some of the inexpensive Part 15 license-free wireless video receivers in the 33-cm band are 4 MHz
deviation FM video, and most of the 2.4 GHz ones are FM, which can be used directly. However, they
may or may not have the standard de-emphasis video network which may have to be added. On 2.4 GHz,
some of the Part 15 frequencies are outside the band and care should be taken to use only those inside
the 2390 to 2450 MHz ham band if modified. Wavecom Jr has been the most popular 2.4 GHz licensefree video transmitter and receiver (available from ATV Research) and have been modified for higher
power and other features as well as having all 4 of the channels in the ham band using interface boards
from PC Electronics.
Gunnplexers on 10.4 GHz make inexpensive point to point ATV links for public-service applications
or between repeaters. A 10-mW Gunnplexer with 17-dB horn can cover over 2 miles line-of-sight when
received on a G8OZP low noise 3-cm LNB and satellite receiver. An application note for construction
of the 3-cm transmitter comes with the GVM-1 Gunnplexer video modulator board from PC Electronics.
For short distance ATV from R/C vehicles, low-power FM ATV modules with 50 to 100-mW output
in the 33, 23 or 13-cm bands are often used. These offer less desense possibility to the R/C receiver. An
example can be seen on the model Humvee in the photo.
For greater distance such as with R/C aircraft, use up to a 1-W ATV transmitter board operating in
Modulation Sources (What and How We Communicate)
12. 85
the 70-cm band. Since R/C receivers at 50 or 72 MHz were not designed to be placed right next to a
transmitter, it is necessary to shield the R/C receiver and put a simple 3-pole 100-MHz low-pass filter
at the antenna input. An application note is available from PC Electronics.
Further ATV Reading
Amateur Television Quarterly Magazine.
CQ-TV, British ATV Club, a quarterly publication available through Amateur Television Quarterly
Magazine.
Ruh, ATV Secrets for the Aspiring ATVers, Vol 1, 1991 and Vol 2, 1992. Available through Amateur
Television Quarterly Magazine.
Taggart, “An Introduction to Amateur Television,” April, May and June 1993 QST.
ATV Equipment Sources
Contact information for these sources appears in the Address List in the References chapter.
Advanced Receiver Research
ATV Research
Digital Communications, Inc (DCI)
Down East Microwave
Elktronics
Intuitive Circuits
Mini-Circuits Labs
PC Electronics
Phillips-Tech Electronics
Spectrum International
TX/RX Systems
Teletec
Wyman Research Inc
12.86
Chapter 12
Radio Control
Amateur Radio gave birth to the radio control
(R/C) hobby as we know it today. Part 97 of the
FCC regulations (§97.215) specifically permits
“remote control of model craft” as a licensed amateur station activity. Station identification is not
required for R/C, and the transmitter power is limited to 1 W. Before 1950, development of telecommand radio systems small enough to be used
for remote radio control of model aircraft, cars and
boats, was primarily an Amateur Radio activity. In
the early 1950s, the FCC licensed R/C transmitter
operation on nonham frequencies, without an operator license examination. The invention of the
transistor and the subsequent increase in R/C development activity lead to the sophisticated electronic control systems in use today. This section
N8QPJ mounted an ATV setup aboard this model
was contributed by H. Warren Plohr, W8IAH.
Humvee.
The simplest electronic control systems are currently used in low-cost toy R/C models. These toys
often use simple on/off switching control that can be transmitted by on/off RF carrier or tone modulation.
More expensive toys and R/C hobby models use more sophisticated control techniques. Several simultaneous proportional and switching controls are available, using either analog or digital coding on a
single RF carrier.
R/C hobby sales records show that control of model cars is the most popular segment of the hobby.
Battery powered cars like that shown in Fig 12.70 are the most popular. Other popular types include
models powered by small internal combustion “gas” engines.
R/C model aircraft are next in the line of popularity and include a wide range of styles and sizes. Fixedwing models like those shown in Fig 12.71 are the most popular. They can be unpowered (gliders) or
powered by either electric or “gas” motors. The basic challenge for a new model pilot is to operate the
model in flight without crashing. Once this is achieved, the challenge extends to operating detailed
scaled models in realistic flight, performing precision aerobatics, racing other models or engaging in
model-to-model combat. The challenge for the R/C glider pilot is to keep the model aloft in rising air
currents. The most popular rotary-wing aircraft models are helicopters. The sophistication of model
helicopters and their control systems can only be appreciated when one sees a skilled pilot perform a
Fig 12.71—Photo of two R/C
aircraft models.
Fig 12.70—Photo of three R/C model electric cars.
Modulation Sources (What and How We Communicate)
12. 87
schedule of precision flight maneuvers. The most exotic maneuver is sustained inverted flight, a maneuver not attainable by a
full-scale helicopter.
R/C boats are another facet of the hobby. R/C water craft models
can imitate full-scale ships and boats. From electric motor powered
scale warships that engage in scale battles, to “gas” powered racing
hydroplanes, model racing yachts and even submarines.
Most R/C operation is no longer on Amateur Radio frequencies.
The FCC currently authorizes 91 R/C frequencies between 27
MHz and 76 MHz. Some frequencies are for all odels, some are for
aircraft only and others for surface (cars, boats) models only.
Some frequencies are used primarily for toys and others for
hobbyist models. Amateur Radio R/C operators use the 6-m band
almost exclusively. Spot frequencies in the upper part of the band
are used in geographical areas where R/C operation is compatible
with 6-m repeater operation and TV Channel-2 signals that can
interfere with control. Eight spot frequencies, 53.1 to 53.8 MHz,
spaced 100 kHz apart, are used. There is also a newer 200 kHz
R/C band from 50.8 to 51.0 MHz providing ten channels spaced
20 kHz apart. The close channel spacing in this band requires
more selective receivers than do the 53-MHz channels. The AMA
Membership Manual provides a detailed list of all R/C frequencies in current use.7 The ARRL Repeater Directory lists current
Amateur Radio R/C frequencies.
Fig 12.72 shows a typical commercial R/C system, consisting of
a hand-held aircraft transmitter (A), a multiple-control receiver, four
control servos and a battery (B). This particular equipment is available for any of the ten R/C frequencies in the 50.80 to 51.00 MHz
band. Other commercially available control devices include relays
(solid-state and mechanical) and electric motor speed controllers.
Some transmitters are tailored to specific kinds of models. A
helicopter, for example, requires simultaneous control of both
collective pitch and engine throttle. A model helicopter pilot commands this response with a linear motion of a single transmitter
control stick. The linear control stick signal is conditioned within
the transmitter to provide the encoder with a desired combination
of nonlinear signals. These signals then command the two servos
that control the vertical motion of the helicopter.
Transmitter control-signal conditioning is provided by either
analog or digital circuitry. The signal conditioning circuitry is often
designed to suit a specific type of model, and it is user adjustable to
meet an individual model’s control need. (Low-cost transmitters
use analog circuitry.) They are available for helicopters, sailplanes
and pattern (aerobatic) aircraft.
More expensive transmitters 7
Academy of Model Aeronauuse digital microprocessor cirtics Membership Manual is
cuitry for signal conditioning.
available from AMA, Muncie,
Fig 12.73 shows a transmitter
IN 47302.
12.88
Chapter 12
(A)
(B)
Fig 12.72—A, photo of Futaba’s
Conquest R/C aircraft transmitter.
B shows the matching airborne
system.
Fig 12.73—Photo of Airtronics
Infinity 660 R/C aircraft transmitter.
that uses a programmable microprocessor. It is available on any 6-m Amateur Radio R/C frequency with
switch-selectable PPM or PCM coding. It can be programmed to suit the needs of a helicopter, sailplane
or pattern aircraft. Nonvolatile memory retains up to four user-programmed model configurations.
Many R/C operators use the Amateur Radio channels to avoid crowding on the nonham channels.
Others do so because they can operate home-built or modified R/C transmitters without obtaining FCC
type acceptance. Still others use commercial R/C hardware for remote control purposes around the
shack. Low-cost R/C servos are particularly useful for remote actuation of tuners, switches and other
devices. Control can be implemented via RF or hard wire, with or without control multiplexing.
R/C RF MODULATION
The coded PPM or PCM information for R/C can modulate an RF carrier via either amplitude- or
frequency-modulation techniques. Commercial R/C systems use both AM and FM modulation for PPM,
but use FM exclusively for PCM.
The AM technique used by R/C is 100% “down modulation.” This technique switches the RF carrier
off for the duration of the PPM pulse, usually 250 to 350 µs. A typical transmitter design consists of a
third-overtone transistor oscillator, a buffer amplifier and a power amplifier of about 1/2 W output. AM
is achieved by keying the 9.6-V supply to the buffer and final amplifier.
The FM technique used by R/C is frequency shift keying (FSK). The modulation is applied to the
crystal-oscillator stage, shifting the frequency about 2.5 or 3.0 kHz. The direction of frequency shift, up
or down with a PPM pulse or PCM code, can be in either direction, as long as the receiver detector is
matched to the transmitter. R/C manufacturers do not standardize, so FM receivers from different
manufacturers may not be compatible.
SIGNALING TECHNIQUES
Background
Radio control (R/C) of models has used many different control techniques in the past. Experimental
techniques have included both frequency- and time-division multiplexing, using both electronic and
mechanical devices. Most current systems use time-division multiplexing of pulse-width information.
This signaling technique, used by hobbyist R/C systems, sends pulse-width information to a remotely
located pulse-feedback servomechanism. Servos were initially developed for R/C in the 1950s and are
still used today in all but low-cost R/C toys.
Fig 12.74 is a block diagram of a pulse-feedback servo. The leading edge of the input pulse triggers
a linear one-shot multivibrator. The width of the one-shot output pulse is compared to the input pulse.
Any pulse width difference is an error signal that is amplified to drive the motor. The motor drives a
feedback potentiometer that controls the one-shot
timing. When this feedback loop reduces the error
signal to a few microseconds, the drive motor
stops. The servo position is a linear function of the
input pulse width. The motor-drive electronics are
usually timed for pulse repetition rates of 50 Hz
or greater and a pulse width range of 1 to 2 ms.
A significantly slower repetition rate reduces the
servomechanism slew rate but not the position
accuracy.
In addition to motor driven servos, the concept
of pulse-width comparison can be used to operate
solid-state or mechanical relay switches. The same Fig 12.74—Diagram of a pulse-feedback servo.
Modulation Sources (What and How We Communicate)
12. 89
concept is used in solid-state proportional electric motor speed controllers. These speed controllers are
used to operate the motors powering model cars, boats and aircraft. Currently available model speed
controllers can handle tens of amperes of direct current at voltages up to 40 V dc using MOSFET
semiconductor switches.
Requirements
The signaling technique required by R/C is the transmission of 1- to 2-ms-wide pulses with an
accuracy of ±1 µs at repetition rates of about 50 Hz. A single positive-going dc pulse of 3 to 5 V amplitude
can be hard wire transmitted successfully to operate a single control servomechanism. If such a pulse
is sent as modulation of an RF carrier, however, distortion of the pulse width in the modulation/demodulation process is often unacceptable. Consequently, the pulse-width information is usually coded for RF
transmission. In addition, most R/C systems require pulse-width information for more than one control.
Time-division multiplexing of each control provides this multichannel capability. Two coding techniques are used to transfer the pulse-width information for multiple control channels, pulse-position
modulation (PPM) and pulse-code modulation (PCM).
Pulse-Position Modulation
PPM is analog in nature. The timing between transmitted pulses is an analog of the encoded pulse
width. A train of pulses encodes multiple channels of pulse-width information as the relative
position or timing between pulses. Therefore the name, pulse-position modulation. The transmitted pulse is about 300 µs in width and uses slow rise and fall times to minimize the transmitter RF
bandwidth. The shape of the received waveform is unimportant because the desired information
is in the timing between pulses. Fig 12.75 diagrams a frame of five pulses that transmits four
control channels of pulse-width information. The frame of modulation pulses is clocked at 50 Hz
for a frame duration of 20 ms. Four multiplexed pulse widths are encoded as the times between five
300-µs pulses. The long period between the first and the last pulse is used by the decoder for
control-channel synchronization.
PPM is often incorrectly called digital control because it can use digital logic circuits to encode
and decode the control pulses. A block diagram of a typical encoder is shown in Fig 12.76. The
50-Hz clock frame generator produces the first 300-µs modulation pulse and simultaneously triggers the first one-shot in a chain of multivibrators. The trailing edge of each one-shot generates
a 300-µs modulation pulse while simultaneously triggering the succeeding multivibrator one-shot.
In a four-channel system the fifth modulation pulse, which indicates control of the fourth channel,
is followed by a modulation pause that is dependent on the frame rate. The train of 300-µs pulses
are used to modulate the RF.
Fig 12.75—Diagram of a fourchannel PPM RF envelope.
Fig 12.76—Diagram of a PPM encoder.
12.90
Chapter 12
Received pulse decoding can
also use digital logic semiconductors. Fig 12.77 shows a
simple four-control-channel decoder circuit using a 74C95
CMOS logic IC. The IC is a 4-bit
shift register operated in the
right-shift mode. Five data
pulses spaced 1 to 2 ms apart,
followed by a synchronization
pause, contain the encoded Fig 12.77—Diagram of a 74C95 PPM decoder.
pulse-width information in one
frame. During the sync pause,
the RC circuit discharges and sends a logic-one signal to the 74C95 serial input terminal. Subsequent
negative going data pulses remove the logic-one signal from the serial input and sequentially clock the
logic one through the four D-flip-flops. The output of each flip-flop is a positive going pulse, with a
width corresponding to the time between the clocking pulses. The output of each flip-flop is a
demultiplexed signal that is used to control the corresponding servo.
Pulse Code Modulation
PCM uses true digital code to transfer R/C signals. The pulse width data of each control channel is
converted to a binary word. The digital word information of each control channel is coded and multiplexed to permit transmission of multiple channels of control on a single RF carrier. On the receiving
end, the process is reversed to yield the servo control signals.
There is no standard for how the digital word is coded for transmission. Therefore PCM R/C transmitters and receivers from different makers are not interchangeable. Some older PCM systems provide
only 256 discrete positions for 90° of servo motion, thereby limiting servo resolution. Newer systems
use more digital bits for each word and provide smooth servo motion with 512 and 1024 discrete
positions. All PCM and PPM systems use the same servo input-signal and supply voltages. Therefore
the servos of different manufacture are interchangeable once compatible wiring connectors have been
installed.
Modulation Sources (What and How We Communicate)
12. 91
Spread Spectrum
This introduction to spread spectrum communications was written by André Kesteloot, N4ICK. The
ARRL Spread Spectrum Sourcebook contains a more complete treatment of the subject.
A Little History
Spread spectrum has existed at least since the mid 1930s. Despite the fact that John Costas, W2CRR,
published a paper on nonmilitary applications of spread spectrum communications in 1959,8 spread
spectrum was used almost solely for military purposes until the late 1970s. In 1981, the FCC granted the
Amateur Radio Research and Development Corporation (AMRAD) a Special Temporary Authorization
to conduct Amateur Radio spread spectrum experiments. In June 1986, the FCC authorized all US
amateurs to use spread spectrum above 420 MHz.
Why Spread Spectrum
Faced with increasing noise and interference levels on most RF bands, traditional wisdom still holds
that the narrower the RF bandwidth, the better the chances that “the signal will get through.” This is not
so.
In 1948, Claude Shannon published his famous paper, “A Mathematical Theory of Communication”
in the Bell System Technical Journal, followed by “Communications in the Presence of Noise” in the
Proceedings of the IRE for January 1949. A theorem that follows Shannon’s, known as the ShannonHartley theorem, states that the channel capacity C of a band-limited gaussian channel is
C = W log2 (1 + S/N) bits/s
(6)
where
W is the bandwidth,
S is the signal power and
N is the noise within the channel bandwidth.
This theorem states that should the channel be perfectly noiseless, the capacity of the channel is
infinite. It should be noted, however, that making the bandwidth W of the channel infinitely large does
not make the capacity infinite, because the channel noise increases proportionately to the channel
bandwidth.
Within reason, however, one can trade power for bandwidth. In addition, the power density at any
point of the occupied bandwidth can be very small, to the point that it may be well below the noise floor
of the receiver. The US Navy Global Positioning System (GPS) is an excellent example of the use of what
is called direct-sequence spread spectrum. The average signal at the GPS receiver’s antenna terminals
is approximately −160 dBW (for the C/A code). Since most sources of interference are relatively narrowband, spread-spectrum users will also benefit, as narrow-band interfering signals are rejected automatically during the despreading process, as will be explained later in this section.
These benefits are obtained at the cost of fairly intricate circuitry: The transmitter must spread its
signal over a wide bandwidth in accordance with a certain prearranged code, while the receiver must
somehow synchronize on this code and recombine the received energy to produce a usable signal. To
generate the code, use is made of pseudo-noise (PN) generators. The PN generators are selected for their
correlation properties. This means that when two similar PN sequences are compared out of phase their
correlation is nil (that is, the output is 0), but when they are exactly
in phase their correlation produces a huge peak that can be used 8
“Poisson, Shannon and the
for synchronization purposes.
Radio Amateur,” Proceedings of
This synchronization process has been (and still is) the major
the IRE, Dec 1959.
12.92
Chapter 12
complicating factor in any spread spectrum link, for how can one synchronize on a signal that can be well
below the receiver’s noise floor? Because of the cost associated with the complicated synchronization
processes, spread spectrum applications were essentially military-related until the late 1970s. The development of ICs then allowed for the replacement of racks and racks of tube equipment by a few plugin PC boards, although the complexity level itself did not improve. Amateur Radio operators could not
afford such levels of complexity and had to find simpler solutions, at the cost of robustness in the
presence of interference.
Spread-Spectrum Transmissions
A transmission can be called “spread spectrum” if the RF bandwidth used is (1) much larger than that
needed for traditional modulation schemes and (2) independent of the modulation content. Although
numerous spread spectrum modulation schemes are in existence, only two, frequency-hopping (FH) and
direct-sequence spread spectrum (DSSS) are specifically authorized by the FCC for use by the Amateur
Radio community.
To understand FH, let us assume a transmitter is able to transmit on any one of 100 discrete frequencies
F1 through F100. We now force this equipment to transmit for 1 second on each of the frequencies, but
in an apparently random pattern (for example, F1, F62, F33, F47…; see Fig 12.78). Should some source
interfere with the receiver site on three of those discrete frequencies, the system will still have achieved
reliable transmission 97% of the time. Because of the built-in redundancy in human speech, as well as
the availability of error-correcting codes in data transmissions, this approach is particularly attractive
for systems that must operate in heavy interference.
In a DSSS transmitter, an RF carrier and a pseudo-random pulse
train are mixed in a doubly balanced mixer (DBM). In the process,
the RF carrier disappears and is replaced by a noise-like wideband transmission, as shown in Fig 12.79. At the receiver, a similar pseudo-random signal is reintroduced and the spread spectrum
signal is correlated, or despread, while narrow-band interference
is spread simultaneously by the same process.
The technical complexity mentioned above is offset by several
important advantages for military and space applications:
• Interference rejection. If the interference is not synchronized
with the original spread spectrum signal, it will not appear after
despreading at the receiver.
• Security. The length and sophistication of the pseudo-random
codes used can be such as to make unauthorized recovery difficult if not impossible.
• Power density. Low power density makes for easy hiding of the
RF signal and a resulting lower probability of detection.
As far as the Amateur Radio community is concerned, particular benefit will be derived from the interference rejection just
mentioned, as it offers both robustness and reliability of transmissions, as well as low probability of interference to other users.
Additionally, spread spectrum has the potential to allow better
utilization of the RF spectrum allocated to amateurs. There is a
limit as to how many conventional signals can be placed in a given
band before serious transmission degradation takes place. Addi-
Fig 12.78—Power vs frequency
for frequency-hopping spread
spectrum signals. Emissions
jump around to discrete frequencies in pseudo-random fashion.
Fig 12.79—Power vs frequency
for a direct-sequence-modulated
spread spectrum signal. The
envelope assumes the shape of a
(sin x/x)2 curve. With proper
modulating techniques, the
carrier is suppressed.
Modulation Sources (What and How We Communicate)
12. 93
tional spread spectrum signals will not cause severe interference, but may instead only raise the background noise level. This becomes particularly important in bands shared with other users and in our VHF
and UHF bands increasingly targeted by would-be commercial users. The utilization of a channel by
many transmitters is essentially the concept behind CDMA (Code Division Multiple Access), a system
in which several DSSS transmissions can share the same RF bandwidth, provided they utilize orthogonal
pseudo-random sequences.
Amateur Spread Spectrum
When radio amateurs (limited in both financial resources and time available for experimentation)
decided to try their hand at spread spectrum transmissions, they had to attack the problem by simplifying
several assumptions. Security and privacy, the primary goals of the military, were sacrificed in favor of
simplicity of design and implementation.
Experimentation sponsored by AMRAD began in 1981 and continues to this day. These experiments
have lead to the design and construction of a practical DSSS UHF link. This project was described in
May 1989 QST and was reprinted in The ARRL Spread Spectrum Sourcebook. In it, N4ICK offered a
simple solution to the problem of synchronization. (Because of its simplicity, this solution does not offer
all the anti-jamming properties of more sophisticated systems, but this should not be of concern to
Amateur Radio operators.) The block diagram is shown in Fig 12.80. Fig 12.81 shows the RF signals
at the transmitter output, at the receiver antenna terminals and the recovered signal after correlation.
James Vincent, G1PVZ, replaced the original FM scheme with a continuously variable delta modulation
system, or CVSD. A description of his work can be found in the September and October 1993 issues of
the British magazine Electronics World & Wireless World.
In addition to The ARRL Spread Spectrum Sourcebook, interested readers may want to pay particular
attention to Robert Dixon’s text, Spread Spectrum Systems. Additional information can be found in the
publications and magazines listed below.
SS References
Dixon, Spread Spectrum Systems, second edition, 1984, Wiley Interscience, New York.
Dixon, Spread Spectrum Techniques, IEEE.
Golomb, Shift Register Sequences, 1982, Aegean Park Press, Laguna Hills, California.
Fig 12.80—A block diagram of the practical spread spectrum link. The success of this arrangement
lies in the use of a synchronized oscillator (right) to recover the transmitter clock signal at the
receiving site.
12.94
Chapter 12
Fig 12.81—(A) The envelope of the unfiltered biphase-modulated spread spectrum signals as viewed
on a spectrum analyzer. In this practical system, band-pass filtering is used to confine the spread
spectrum signal to the amateur band. (B) At the receiver end of the line, the filtered spread spectrum
signal is apparent only as a 10-dB hump in the noise floor. (C) The despread signal at the output of
the receiver DBM. The original carrier—and any modulation components that accompany it—has
been recovered. The peak carrier is about 45 dB above the noise floor—more than 30 dB above the
hump shown at B. (These spectrograms were made at a sweep rate of 0.1 s/division and an analyzer
bandwidth of 30 kHz; the horizontal scale is 1 MHz/division.)
Hershey, Proposed Direct Sequence Spread Spectrum Voice Techniques for Amateur Radio Service,
1982, US Department of Commerce, NTIA Report 82-111.
Holmes, Coherent Spread Spectrum Systems, 1982, Wiley Interscience, New York.
Kesteloot, Ed., The ARRL Spread Spectrum Sourcebook (Newington, CT: ARRL, 1990). Includes
Hershey, QST and QEX material listed separately here.
The AMRAD Newsletter carries a monthly column on spread spectrum and reviews ongoing AMRAD
experiments. Contact information appears in the Address List in the References chapter.
The following articles have appeared in Amateur Radio publications. All of the articles from QST and
QEX are reproduced in The ARRL Spread Spectrum Sourcebook.
Feinstein, “Spread Spectrum—A report from AMRAD,” 73, November 1981.
Feinstein, “Amateur Spread Spectrum Experiments,” CQ, July 1982.
Kesteloot, “Practical Spread Spectrum: A Simple Clock Synchronization Scheme,” QEX, October 1986.
Kesteloot, “Experimenting with Direct Sequence Spread Spectrum,” QEX, December 1986.
Kesteloot, “Extracting Stable Clock Signals from AM Broadcast Carriers for Amateur Spread Spectrum
Applications,” QEX, October 1987.
Kesteloot, “Practical Spread Spectrum Achieving Synchronization with the Slip-Pulse Generator,”
QEX, May 1988.
Kesteloot, “A Practical Direct Sequence Spread-Spectrum UHF Link,” QST, May 1989.
Kesteloot, “Practical Spread Spectrum Clock Recovery With the Synchronous Oscillator,” QEX, June
1989.
Rohde, “Digital HF Radio A Sampling of Techniques,” Ham Radio, April 1985.
Rinaldo, “Spread Spectrum and the Radio Amateur,” QST, November 1980.
Sabin, “Spread Spectrum Applications in Amateur Radio,” QST, July 1983.
Williams, “A Digital Frequency Synthesizer,” QST, April 1984.
Williams, “A Microprocessor Controller for the Digital Frequency Synthesizer,” QST, February 1985.
Modulation Sources (What and How We Communicate)
12. 95
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