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MAX17550
60V, 25mA, Ultra-Small, High-Efficiency,
Synchronous Step-Down DC-DC Converter
with 22µA No-Load Supply Current
General Description
Benefits and Features
The MAX17550 uses peak-current-mode control. The
device can be operated in pulse-width modulation (PWM)
or pulse-frequency modulation (PFM) modes.
●● Reduces Number of DC-DC Regulators to Stock
• Wide 4V to 60V Input
• Adjustable 0.8V to 0.9 x VIN Output
• 100kHz to 2.2MHz Adjustable Switching Frequency
with External Synchronization
The MAX17550 high-efficiency, high-voltage, synchronous
step-down DC-DC converter with integrated MOSFETs
operates over a 4V to 60V input. The converter can deliver
up to 25mA and generates output voltages from 0.8V up
to 0.9 x VIN. The feedback (FB) voltage is accurate to
within ±1.75% over -40°C to +125°C.
●● Reduces External Components and Total Cost
• No Schottky–Synchronous
• Internal Compensation for Any Output Voltage
• Built-In Soft-Start
• All-Ceramic Capacitors, Compact Layout
The device is available in a 10-pin (3mm x 2mm) TDFN
and 10-pin (3mm x 3mm) μMAX® packages. Simulation
models are available.
●● Reduces Power Dissipation
• 22µA Quiescent Current
• Peak Efficiency > 90%
• PFM Enables Enhanced Light-Load Efficiency
• 1.2µA Shutdown Current
Applications
●●
●●
●●
●●
Industrial sensors and Process control
High-Voltage LDO Replacement
Battery-Powered Equipment
HVAC and Building Control
●● Operates Reliable in Adverse Environments
• Peak Current-Limit Protection
• Built-In Output-Voltage Monitoring RESET
• Programmable EN/UVLO Threshold
• Monotonic Startup Into Prebiased Load
• Overtemperature Protection
• -40°C to +125°C Operation
Ordering Information appears at end of data sheet.
µMAX is a registered trademark of Maxim Integrated Products, Inc.
Typical Application Circuits—High-Efficiency 5V, 25mA Regulator
VIN
6V TO 60V
CIN
1µF
IN
LX
L1
1mH
COUT
10µF
MAX17550
EN/UVLO
GND
SS
VOUT
MODE
FB
RT/SYNC
R3
191kΩ
19-7109; Rev 1; 3/15
VOUT
5V, 25mA
R4
22.1Ω
C1
0.22µF
R1
261kΩ
R2
49.9kΩ
RESET
SWITCHING FREQUENCY = 220kHz
L1 COILCRAFT LPS5030-105M
COUT MURATA 10µF/X7R/6.3V/0805 (GRM21BR70J106K)
CIN MURATA 1µF/X7R/100V/1206 (GRM31CR72A105K)
MAX17550
60V, 25mA, Ultra-Small, High-Efficiency
Synchronous Step-Down DC-DC Converter
with 22µA No-Load Supply Current
Absolute Maximum Ratings
IN, EN/UVLO, VOUT, RESET to GND.....................-0.3V to 70V
LX to GND....................................................... -0.3V to IN + 0.3V
RT/SYNC, SS, FB, MODE to GND............................-0.3V to 6V
LX Total RMS Current.........................................................±0.8A
Output Short-Circuit Duration.....................................Continuous
Continuous Power Dissipation (TA = +70°C)
TDFN (derate 14.9mW/°C above +70°C) ............... 1188.7mW
µMAX (derate 8.8mW/°C above +70°C)...................707.3mW
Operating Temperature Range.......................... -40°C to +125°C
Junction Temperature.......................................................+150°C
Storage Temperature Range............................. -65°C to +150°C
Lead Temperature (soldering, 10s).................................. +300°C
Soldering Temperature (reflow)........................................+260°C
Stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these
or any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to absolute maximum rating conditions for extended periods may affect
device reliability.
Package Thermal Characteristics (Note 1)
TDFN
Junction-to-Ambient Thermal Resistance (θJA)........67.3°C/W
Junction-to-Case Thermal Resistance (θJC).............18.2°C/W
μMAX
Junction-to-Ambient Thermal Resistance (θJA)......113.1°C/W
Junction-to-Case Thermal Resistance (θJC)................42°C/W
Note 1: Package thermal resistances were obtained using the method described in JEDEC specification JESD51-7, using a four-layer
board. For detailed information on package thermal considerations, refer to www.maximintegrated.com/thermal-tutorial.
Electrical Characteristics
(VIN = 24V, VGND = 0V, VOUT = 3.3V, VFB = 0.85V, VEN/UVLO = 1.5V, RT/SYNC = 191kΩ, LX = SS = MODE = RESET = unconnected;
TA = TJ = -40°C to +125°C, unless otherwise noted. Typical values are at TA = +25°C. All voltages are referenced to GND, unless
otherwise noted.) (Note 3)
PARAMETER
SYMBOL
CONDITIONS
MIN
TYP
MAX
UNITS
60
V
INPUT SUPPLY (IN)
Input Voltage Range
Input Shutdown Current
Input Supply Current
VIN
4
IIN-SH
VEN/UVLO = 0V, TA = +25°C
IQ-PFM
VMODE = unconnected (Note 2)
IQ-PWM
Normal switching mode, VIN = 24V
0.67
1.2
2.25
18
32
180
485
650
2.96
3.05
3.12
µA
EXTERNAL BIAS (VOUT)
VOUT Switchover Threshold
V
ENABLE/UVLO (EN/UVLO)
EN/UVLO Threshold
VENR
VEN/UVLO rising
1.2
1.25
1.3
VENF
VEN/UVLO falling
1.1
1.15
1.2
V
+100
nA
VEN-TRUESD
EN/UVLO Leakage Current
IEN
VEN/UVLO falling, true shutdown
VEN/UVLO = 1.3V, TA = +25°C
0.7
-100
POWER MOSFETs
High-Side pMOS On-Resistance
RDS-ONH
ILX = 0.1A (sourcing)
3.2
5.9
11.1
Ω
Low-Side nMOS On-Resistance
RDS-ONL
ILX = 0.1A (sinking)
1.6
3.0
6
Ω
VEN = 0V, TA = +25°C,
VLX = (VGND + 1V) to (VIN - 1V)
-1
+1
µA
LX Leakage Current
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ILX-LKG
Maxim Integrated │ 2
MAX17550
60V, 25mA, Ultra-Small, High-Efficiency
Synchronous Step-Down DC-DC Converter
with 22µA No-Load Supply Current
Electrical Characteristics (continued)
(VIN = 24V, VGND = 0V, VOUT = 3.3V, VFB = 0.85V, VEN/UVLO = 1.5V, RT/SYNC = 191kΩ, LX = SS = MODE = RESET = unconnected;
TA = TJ = -40°C to +125°C, unless otherwise noted. Typical values are at TA = +25°C. All voltages are referenced to GND, unless
otherwise noted.) (Note 3)
PARAMETER
SYMBOL
CONDITIONS
MIN
TYP
MAX
UNITS
SOFT-START (SS)
Soft-Start Time
tSS
SS = unconnected
4.4
5.1
5.8
ms
SS Charging Current
ISS
VSS = 0.4V
4.7
5
5.3
µA
MODE = GND
0.786
0.8
0.814
MODE = unconnected
0.786
0.812
0.826
VFB = 1V, TA = 25°C
-100
FEEDBACK (FB)
FB Regulation Voltage
FB Input Leakage Current
VFB-REG
IFB
V
+100
nA
mA
CURRENT LIMIT
Peak Current-Limit Threshold
IPEAK-LIMIT
Negative Current-Limit Threshold
ISINK-LIMIT
PFM Current Level
IPFM
VMODE = GND
66
72
78
24
32
40
VMODE = unconnected
0.01
mA
VMODE = unconnected
17
23
29
mA
RRT = 422kΩ
90
100
111
RRT = 191kΩ
205
220
235
RRT = 130kΩ
295
319
340
RRT = 69.8kΩ
540
592
638
RRT = 45.3kΩ
813
900
973
RRT = 19.1kΩ
1.86
2.08
2.3
MHz
See the Switching Frequency
(RT/SYNC) section for details
100
2200
kHz
2200
kHz
CURRENT LIMIT
Switching Frequency
fSW
Switching-Frequency Adjustable
Range
SYNC Input Frequency
1.1 x fSW
SYNC Pulse Minimum Off-Time
SYNC Rising Threshold
Hysteresis
40
ns
VSYNC-H
1
1.22
1.44
VSYNC-HYS
0.115
0.18
0.265
Number of SYNC Pulses to
Enable Synchronization
kHz
1
V
Cycles
TIMING
Minimum On-Time
Maximum Duty Cycle
Hiccup Timeout
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tON-MIN
DMAX
46
82
128
fSW ≤ 600kHz,
VFB = 0.98 x VFB-REG
90
94
98
fSW > 600kHz,
VFB = 0.98 x VFB-REG
87
92
ns
%
51
ms
Maxim Integrated │ 3
MAX17550
60V, 25mA, Ultra-Small, High-Efficiency
Synchronous Step-Down DC-DC Converter
with 22µA No-Load Supply Current
Electrical Characteristics (continued)
(VIN = 24V, VGND = 0V, VOUT = 3.3V, VFB = 0.85V, VEN/UVLO = 1.5V, RT/SYNC = 191kΩ, LX = SS = MODE = RESET = unconnected;
TA = TJ = -40°C to +125°C, unless otherwise noted. Typical values are at TA = +25°C. All voltages are referenced to GND, unless
otherwise noted.) (Note 3)
RESET
PARAMETER
SYMBOL
CONDITIONS
MIN
TYP
MAX
UNITS
FB Threshold for RESET Rising
VFB-OKR
VFB rising
93
95
97
%
FB Threshold for RESET Falling
VFB-OKF
VFB falling
90
92
94
%
RESET Delay after FB Reaches
95% Regulation
RESET Output Level Low
IRESET = 1mA
RESET Output Leakage Current
Output Leakage Current
VFB = 1.01 x VFB-REG, TA = +25°C
2.1
ms
0.23
V
1
µA
1.44
V
MODE
MODE PFM Threshold
VMODE-PFM
MODE Hysteresis
VMODE-HYS
MODE Internal Pullup Resistor
1
1.22
0.19
V
VMODE = unconnected
123
VMODE = GND
1390
Temperature rising
160
°C
20
°C
kΩ
THERMAL SHUTDOWN
Thermal-Shutdown Threshold
VMODE-PFM
Thermal-Shutdown Hysteresis
VMODE-HYS
Note 2: Actual IQ-PFM in the application circuit is higher due to additional current in the output voltage feedback resistor divider. For
example, IQ-PFM (MODE = unconnected) = 26µA for Figure 6, 22µA for Figure 7, and 78µA for Figure 11.
Note 3: Limits are 100% tested at TA = +25°C. Limits over the operating temperature range and relevant supply voltage range are
guaranteed by design and characterization.
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Maxim Integrated │ 4
MAX17550
60V, 25mA, Ultra-Small, High-Efficiency
Synchronous Step-Down DC-DC Converter
with 22µA No-Load Supply Current
Typical Operating Characteristics
(VIN = 24V, VGND = 0V, VOUT = 3.3V, VEN/UVLO = 1.5V, RT/SYNC = 191kΩ, CIN = 1μF, TA = +25°C unless otherwise noted)
EFFICIENCY vs. LOAD CURRENT
toc1
EFFICIENCY vs. LOAD CURRENT
100
90
80
80
70
70
70
V = 24V VIN = 36V VIN = 48V
VIN = 12V IN
VIN = 60V
50
40
60
VIN = 12V VIN = 24V
40
1
10
0
10
1
EFFICIENCY VS. LOAD CURRENT
toc4
30
VIN = 60V
20
FIGURE 6 APPLICATION CIRCUIT,
PWM MODE, VOUT = 5V,
FSW = 220kHz (RRT=191k)
10
0
toc5
90
80
80
80
70
70
VIN = 36V
40
VIN = 48V
30
10
0
0
5
10
15
20
50
VIN = 12V
10
0
25
toc7
1
80
70
VIN =24V
40
VIN = 12V
VIN = 36V
FIGURE 8 APPLICATION
CIRCUIT, PWM MODE,
VIN = 48V
VOUT = 5V
VIN = 60V
FSW = 600kHz (RRT = 69.8k)
30
20
10
0
EFFICIENCY (%)
70
0
5
10
15
LOAD CURRENT (mA)
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40
VIN = 12V
FIGURE 9 APPLICATION CIRCUIT,
PFM MODE, VOUT = 3.3V
FSW = 600kHz (RRT = 69.8k)
10
0
1
10
20
toc8
VIN = 60V
VIN = 36V
30
10
0
VIN = 48V
VIN = 24V FIGURE 9 APPLICATION
CIRCUIT, PWM MODE,
VIN = 12V
VOUT = 3.3V
FSW = 600kHz (RRT = 69.8k)
20
25
LOAD CURRENT (mA)
60
40
0
5
10
15
LOAD CURRENT (mA)
toc6
VIN = 24V
OUTPUT VOLTAGE vs. LOAD CURRENT
5.06
FIGURE 6 APPLICATION
CIRCUIT, PFM MODE
5.04
50
25
20
toc9
80
20
VIN = 36V VIN = 48V
VIN = 60V
50
20
10
EFFICIENCY VS. LOAD CURRENT
90
90
50
60
30
FIGURE 8 APPLICATION CIRCUIT,
PFM MODE, VOUT = 5V
FSW = 600kHz (RRT = 69.8k)
20
15
70
LOAD CURRENT (mA)
EFFICIENCY vs. LOAD CURRENT
60
VIN = 60V
40
LOAD CURRENT (mA)
100
V = 48V
VIN = 24V VIN = 36V IN
30
FIGURE 7 APPLICATION
CIRCUIT, PWM MODE
VIN = 60V
VOUT = 3.3V, FSW = 220kHz
(RRT = 191k)
20
60
OUTPUT VOLTAGE (V)
VIN = 24V
VIN = 12V
EFFICIENCY (%)
90
50
10
EFFICIENCY vs. LOAD CURRENT
100
90
60
5
LOAD CURRENT (mA)
EFFICIENCY vs. LOAD CURRENT
100
VIN = 12V
VIN = 48V
40
0
toc3
VIN = 36V
50
LOAD CURRENT (mA)
EFFICIENCY (%)
EFFICIENCY (%)
VIN = 24V
60
10
LOAD CURRENT (mA)
100
VIN = 60V
FIGURE 7 APPLICATION
CIRCUIT, PFM MODE
VOUT = 3.3V
FSW = 220kHz (RRT = 191k)
20
FIGURE 6 APPLICATION CIRCUIT,
PFM MODE
VOUT = 5V, FSW = 220kHz (RRT = 191k)
10
0
VIN = 36V VIN = 48V
50
30
20
EFFICIENCY (%)
90
60
EFFICIENCY vs. LOAD CURRENT
100
80
30
EFFICIENCY (%)
toc2
90
EFFICIENCY (%)
EFFICIENCY (%)
100
VIN = 60V
5.02
VIN = 48V
5.00
VIN = 12V
VIN = 36V
VIN = 24V
4.98
4.96
4.94
25
0
5
10
15
20
25
LOAD CURRENT (mA)
Maxim Integrated │ 5
MAX17550
60V, 25mA, Ultra-Small, High-Efficiency
Synchronous Step-Down DC-DC Converter
with 22µA No-Load Supply Current
Typical Operating Characteristics (continued)
(VIN = 24V, VGND = 0V, VOUT = 3.3V, VEN/UVLO = 1.5V, RT/SYNC = 191kΩ, CIN = 1μF, TA = +25°C unless otherwise noted)
4.96
OUTPUT VOLTAGE (V)
VIN = 12V
VIN = 24V
3.34
VIN = 36V
3.32
VIN = 48V
VIN = 60V
3.30
4.96
4.95
4.95
VIN = 12V VIN = 24V V = 36V VIN = 48V
IN
4.95
VIN = 60V
4.95
0
5
10
15
5.16
20
4.94
25
3.33
VIN = 12V VIN = 24V
0
5
10
toc13
5.04
5.00
VIN = 12V
4.96
VIN = 24V
VIN = 36V
4.92
VIN = 48V
4.88
20
VIN = 36V
VIN = 48V VIN = 60V
3.33
25
toc14
FIGURE 9 APPLICATION
CIRCUIT, PFM MODE
3.50
3.46
3.38
3.34
VIN = 12V
VIN = 24V
3.30
VIN = 36V VIN = 48V
3.26
4.95
LOAD CURRENT (mA)
0
5
10
15
20
4.94
25
toc16
toc17
FEEDBACK VOLTAGE (V)
3.332
3.331
VIN = 12V
VIN = 24V V = 36V VIN = 48V
IN
VIN = 60V
3.329
0
5
10
15
LOAD CURRENT (mA)
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20
25
NO LOAD SUPPLY CURRENT (µA)
810
3.330
0
800
790
780
-40
-20
0
20
40
60
TEMPERATURE (°C)
80
VIN = 48V
VIN = 60V
5
10
15
20
100
120
NO-LOAD SUPPLY CURRENT
VS. INPUT VOLTAGE
100
FIGURE 9 APPLICATION
CIRCUIT, PWM MODE
3.333
VIN = 36V
25
LOAD CURRENT (mA)
FEEDBACK VOLTAGE
VS. TEMPERATURE
820
toc15
VIN = 12V
LOAD CURRENT (mA)
OUTPUT VOLTAGE
vs LOAD CURRENT
3.334
VIN = 24V
4.95
3.14
25
25
FIGURE 8 APPLICATION
CIRCUIT, PWM MODE
4.95
3.18
20
OUTPUT VOLTAGE
vs. LOAD CURRENT
4.95
4.80
15
20
4.96
4.84
10
15
4.96
VIN=60V
3.42
10
4.96
4.95
5
5
4.96
3.22
0
0
LOAD CURRENT (mA)
OUTPUT VOLTAGE
vs. LOAD CURRENT
3.54
OUTPUT VOLTAGE (V)
VIN=60V
5.08
15
LOAD CURRENT (mA)
FIGURE 8 APPLICATION
CIRCUIT, PFM MODE
5.12
OUTPUT VOLTAGE (V)
3.34
4.95
OUTPUT VOLTAGE
vs. LOAD CURRENT
OUTPUT VOLTAGE (V)
toc12
FIGURE 7 APPLICATION
CIRCUIT, PWM MODE
3.34
3.33
LOAD CURRENT (mA)
3.328
OUTPUT VOLTAGE
vs. LOAD CURRENT
3.34
OUTPUT VOLTAGE (V)
3.28
toc11
FIGURE 6 APPLICATION
CIRCUIT, PWM MODE
4.96
3.38
3.36
OUTPUT VOLTAGE
vs. LOAD CURRENT
4.96
FIGURE 7 APPLICATION
CIRCUIT, PFM MODE
3.40
OUTPUT VOLTAGE (V)
toc10
OUTPUT VOLTAGE (V)
OUTPUT VOLTAGE
vs. LOAD CURRENT
3.42
toc18
PFM MODE
80
60
40
20
0
5
15
25
35
45
55
INPUT VOLTAGE (V)
Maxim Integrated │ 6
MAX17550
60V, 25mA, Ultra-Small, High-Efficiency
Synchronous Step-Down DC-DC Converter
with 22µA No-Load Supply Current
Typical Operating Characteristics (continued)
(VIN = 24V, VGND = 0V, VOUT = 3.3V, VEN/UVLO = 1.5V, RT/SYNC = 191kΩ, CIN = 1μF, TA = +25°C unless otherwise noted)
toc19
SHUTDOWN CURRENT (µA)
1
-0.5
5
15
toc22
50
SWITCH NEGATIVE CURRENT LIMIT
25
0
-40
-20
0
20
40
60
80
1.1
0.8
0
20
40
60
80
100
60
SWITCH NEGATIVE CURRENT LIMIT
40
20
0
120
5
15
25
100
120
toc23
1.22
1.18
1.14
FALLING
1.1
-40
-20
0
20
40
60
80
100
RT = 69.8KΩ
600
400
RT = 191KΩ
200
0
120
toc24
800
RT = 422KΩ
-40
-20
0
20
40
60
80
100
120
TEMPERATURE (°C)
LOAD TRANSIENT RESPONSE
PFM MODE (LOAD CURRENT STEPPED
FROM 5mA to 17.5mA)
LOAD TRANSIENT RESPONSE,
PFM MODE (LOAD CURRENT STEPPED
toc26
FROM 5mA to 17.5mA)
toc25
55
RT = 45.3KΩ
TEMPERATURE (°C)
RESET THRESHOLD
VS. TEMPERATURE
45
SWITCHING FREQUENCY
VS. TEMPERATURE
1000
RISING
1.26
35
INPUT VOLTAGE (V)
EN/UVLO THRESHOLD VOLTAGE
VS. TEMPERATURE
1.3
TEMPERATURE (°C)
96
-20
toc21
SWITCH PEAK CURRENT LIMIT
80
TEMPERATURE (°C)
SWITCH PEAK CURRENT LIMIT
75
1.4
-40
SWITCH CURRENT LIMIT
VS. INPUT VOLTAGE
100
1.7
0.5
55
SWITCH CURRENT LIMIT
VS. TEMPERATURE
100
SWITCH CURRENT LIMIT (A)
25
35
45
INPUT VOLTAGE (V)
toc20
SWITCHING FREQUENCY (KHz)
-2
EN/UVLO THRESHOLD VOLTAGE (V)
SHUTDOWN CURRENT (µA)
4
2.5
SHUTDOWN CURRENT
VS. TEMPERATURE
2
SWITCH CURRENT LIMIT (A)
SHUTDOWN CURRENT
VS. INPUT VOLTAGE
toc27
RISING
RESET THRESHOLD (%)
95
VOUT
(AC)
94
VOUT (AC)
FIGURE6
FIGURE 6
APPLICATION
APPLICATION
CIRCUITCIRCUIT
VOUT=5V
VOUT = 5V
93
92
50mV/div
FIGURE 7
FIGURE7
APPLICATION
CIRCUIT
APPLICATION
CIRCUIT
VOUT = 3.3V
VOUT=3.3V
FALLING
IOUT
91
90
100mV/div
-40
-20
0
20
40
60
80
100
120
10mA/div
400µs/div
IOUT
10mA/div
200µs/div
TEMPERATURE (°C)
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Maxim Integrated │ 7
MAX17550
60V, 25mA, Ultra-Small, High-Efficiency
Synchronous Step-Down DC-DC Converter
with 22µA No-Load Supply Current
Typical Operating Characteristics (continued)
(VIN = 24V, VGND = 0V, VOUT = 3.3V, VEN/UVLO = 1.5V, RT/SYNC = 191kΩ, CIN = 1μF, TA = +25°C unless otherwise noted)
LOAD TRANSIENT RESPONSE
PFM OR PWM MODE (LOAD CURRENT
STEPPED FROM 12.5mA TO 25mA)
LOAD TRANSIENT RESPONSE
PFM OR PWM MODE (LOAD CURRENT
STEPPED FROM 12.5mA TO 25mA)
toc28
50mV/div
VOUT (AC)
50mV/div
10mA/div
FIGURE 7
APPLICATION CIRCUIT
VOUT = 3.3V
FIGURE 6
APPLICATION CIRCUIT
VOUT = 5V
VOUT (AC)
FIGURE 6
APPLICATION CIRCUIT
VOUT = 5V
IOUT
10mA/div
IOUT
toc30
toc29
50mV/div
VOUT (AC)
LOAD TRANSIENT RESPONSE
PWM MODE (LOAD CURRENT STEPPED
FROM NO LOAD TO 12.5mA)
IOUT
10mA/div
200µs/div
200µs/div
LOAD TRANSIENT RESPONSE
PWM MODE (LOAD CURRENT STEPPED
FROM NO LOAD TO 12.5mA)
200µs/div
SWITCHING WAVEFORMS
(PFM MODE)
toc31
FULL-LOAD SWITCHING WAVEFORMS
(PWM OR PFM MODE)
toc33
toc32
FIGURE 6 APPLICATION CIRCUIT
VOUT = 5V, LOAD = 5mA
50mV/div
VOUT (AC)
FIGURE 7
APPLICATION CIRCUIT
VOUT = 3.3V
10mA/div
IOUT
100mV/div
VOUT (AC)
LX
10V/div
ILX
20mA/div
FIGURE 6 APPLICATION CIRCUIT
VOUT = 5V, LOAD = 25mA
VOUT (AC)
LX
10V/div
20mA/div
ILX
4µs/div
20µs/div
200µs/div
NO-LOAD SWITCHING WAVEFORMS
(PWM MODE)
SOFT START
toc34
FIGURE 6 APPLICATION CIRCUIT
VOUT = 5V
VOUT (AC)
VEN/UVLO
2V/div
VOUT
10mA/div
10V/div
I OUT
20mA/div
ILX
4µs/div
www.maximintegrated.com
toc35
5V/div
20mV/div
LX
20mV/div
VRESET
FIGURE 6
APPLICATION CIRCUIT
VOUT = 5V
5V/div
1ms/div
Maxim Integrated │ 8
MAX17550
60V, 25mA, Ultra-Small, High-Efficiency
Synchronous Step-Down DC-DC Converter
with 22µA No-Load Supply Current
Typical Operating Characteristics (continued)
(VIN = 24V, VGND = 0V, VOUT = 3.3V, VEN/UVLO = 1.5V, RT/SYNC = 191kΩ, CIN = 1μF, TA = +25°C unless otherwise noted)
SOFT START
SHUTDOWN WITH ENABLE
toc36
5V/div
VEN/UVLO
VOUT
10mA/div
FIGURE 7
APPLICATION
CIRCUIT
VOUT = 3.3V
I OUT
VRESET
1V/div
FIGURE 6
APPLICATION CIRCUIT
NO LOAD
PWM MODE
VOUT
2V/div
5V/div
10mA/div
VRESET
5V/div
2ms/div
EXTERNAL SYNCHRONIZATION WITH
CLOCK FREQUENCY OF 300kHz toc39
5V/div
VRESET
1ms/div
OVERLOAD PROTECTION
VOUT
VRT/SYNC
VEN/UVLO
FIGURE 6
APPLICATION CIRCUIT
VOUT = 5V
I OUT
1ms/div
VLX
5V/div
FIGURE 6
APPLICATION CIRCUIT
VOUT = 5V
2V/div
10V/div
FIGURE 6
APPLICATION
CIRCUIT
25mA LOAD
PWM MODE
2V/div
ILX
4µs/div
50mA/div
40µs/div
BODE PLOT
BODE PLOT
PHASE
FIGURE 6 APPLICATION CIRCUIT
VOUT = 5V
GAIN (dB)
GAIN
PHASE (º)
FCR = 10.6KHz,
PHASE MARGIN = 62°
toc42
toc41
PHASE
GAIN (dB)
toc40
FCR = 11.3KHz,
PHASE MARGIN = 60°
GAIN
PHASE (º)
VOUT
toc38
5V/div
VEN/UVLO
1V/div
SOFT-START WITH 3V PREBIAS
toc37
FIGURE 7 APPLICATION CIRCUIT
VOUT = 3.3V
FREQUENCY(Hz)
www.maximintegrated.com
Maxim Integrated │ 9
MAX17550
60V, 25mA, Ultra-Small, High-Efficiency
Synchronous Step-Down DC-DC Converter
with 22µA No-Load Supply Current
Pin Configuration
TOP VIEW
LX
10
GND MODE RESET VOUT
9
8
7
6
MAX17550
+
1
IN
2
3
4
5
EN/ RT/ SS
UVLO SYNC
FB
IN
1
EN/UVLO
2
RT/SYNC
3
SS
FB
+
MAX17550
10
LX
9
GND
8
MODE
4
7
RESET
5
6
VOUT
µMAX
3mm x 3mm
TDFN
3mm x 2mm
Pin Description
PIN
NAME
1
IN
2
EN/UVLO
Active-High, Enable/Undervoltage-Detection Input. Pull EN/UVLO to GND to disable the regulator output.
Connect EN/UVLO to IN for always-on operation. Connect a resistor-divider between IN,
EN/UVLO, and GND to program the input voltage at which the device is enabled and turns on.
3
RT/SYNC
Oscillator Timing Resistor Input. Connect a resistor from RT/SYNC to GND to program the switching
frequency from 100kHz to 2.2MHz. See the Switching Frequency (RT/SYNC) section for details. An
external pulse can be applied to RT/SYNC through a coupling capacitor to synchronize the internal clock
to the external pulse frequency. See the External Synchronization section for details.
4
SS
Soft-Start Capacitor Input. Connect a capacitor from SS to GND to set the soft-start time. Leave SS
unconnected for default 5.1ms internal soft-start.
5
FB
Output Feedback Connection. Connect FB to a resistor-divider between VOUT and GND to set the output
voltage. See Adjusting the Output Voltage section for details.
6
VOUT
External Bias Input for Internal Control Circuitry. Decouple to GND with a 0.22μF capacitor and connect to
output capacitor positive terminal with a 22.1Ω resistor for applications with an output voltage from 3.3V to
5V. Connect to GND for output voltages < 3.3V and > 5V. See the External Bias section for details.
7
RESET
Open-Drain Reset Output. Pull up RESET to an external power supply with an external resistor. RESET
pulls low if FB voltage drops below 92% of its set value. RESET goes high-impedance 2ms after FB
voltage rises above 95% of its set value.
8
MODE
PFM/PWM Mode-Selection Input. Connect MODE to GND to enable the fixed-frequency PWM operation.
Leave MODE unconnected for light-load PFM operation.
9
GND
Ground. Connect GND to the power ground plane. Connect all the circuit ground connections together at
a single point. See the PCB Layout Guidelines section.
10
LX
Inductor Connection. Connect LX to the switching-side of the inductor. LX is high-impedance when the
device is in shutdown.
—
EP
Exposed Pad (TDFN Only). Connect to the GND pin to the IC.
www.maximintegrated.com
FUNCTION
Switching Regulator Input. Connect a X7R 1µF ceramic capacitor from IN to GND for bypassing.
Maxim Integrated │ 10
MAX17550
60V, 25mA, Ultra-Small, High-Efficiency
Synchronous Step-Down DC-DC Converter
with 22µA No-Load Supply Current
Block Diagram
IN
INTERNAL
LDO
REGULATOR
VOUT
POK
VCC_INT
PEAK-LIMIT
EN/UVLO
CURRENTSENSE
LOGIC
CHIPEN
1.25V
PFM
THERMAL
SHUTDOWN
CLK
RT/SYNC
PFM/PWM
CONTROL
LOGIC
OSCILLATOR
SLOPE
VCC_INT
SLOPE
SS
CS
INTERNAL OR
EXTERNAL
SOFT-START
CONTROL
www.maximintegrated.com
LX
LOW-SIDE
DRIVER
SINK-LIMIT
CURRENT
SENSE
AMPLIFIER
PWM
ERROR
AMPLIFIER
NEGATIVE
CURRENT
REF
GND
RESET
0.76V
MAX17550
CLK
DH
MODE SELECT
1.22V
FB
CURRENTSENSE
AMPLIFIER
HIGH-SIDE
DRIVER
DL
MODE
CS
FB
2ms
DELAY
Maxim Integrated │ 11
MAX17550
60V, 25mA, Ultra-Small, High-Efficiency
Synchronous Step-Down DC-DC Converter
with 22µA No-Load Supply Current
Detailed Description
The MAX17550 high-efficiency, high-voltage, synchronous
step-down DC-DC converter with integrated MOSFETs
operates over a 4V to 60V input voltage range. The
converter can deliver output current up to 25mA at output
voltages of 0.8V to 0.9 x VIN. The output voltage is accurate
to within ±1.75% over -40°C to +125°C. The converter
consumes only 22µA of supply current in PFM mode,
while regulating the output voltage at no load.
The device uses an internally compensated, peakcurrent-mode-control architecture (see the Block
Diagram). On the rising-edge of the internal clock, the
high-side pMOSFET turns on. An internal error-amplifier
compares the feedback voltage to a fixed internal reference
voltage and generates an error voltage. The error voltage
is compared to a sum of the current-sense voltage and
a slope-compensation voltage by a PWM comparator to
set the “on-time.” During the on-time of the pMOSFET,
the inductor current ramps up. For the remainder of the
switching period (off-time), the pMOSFET is kept off and
the low-side nMOSFET turns on. During the off-time,
the inductor releases the stored energy as the inductor
current ramps down, providing current to the output.
Under overload conditions, the cycle-by-cycle currentlimit feature limits inductor peak current by turning off
the high-side pMOSFET and turning on the low-side
nMOSFET.
Mode Selection (MODE)
The device features a MODE pin for selecting either the
forced-PWM or PFM modes of operation. If the MODE
pin is left unconnected, the device operates in PFM mode
at light loads. If the MODE pin is grounded, the device
operates in a constant-frequency forced-PWM mode at all
loads. The mode of operation can be changed on-the-fly
during normal operation of the device.
In PWM mode, the inductor current is allowed to go
negative. PWM operation is useful in frequency-sensitive
applications and provides fixed switching frequency at all
loads. However, the PWM mode of operation gives lower
efficiency at light loads when compared to the PFM mode of
operation.
PFM mode disables negative inductor current and additionally skips pulses at light loads for high efficiency. In
PFM mode, the inductor current is forced to a fixed peak
of 23mA (typ) (IPFM) every clock cycle until the output
rises to 102% (typ) of the nominal voltage. Once the
output reaches 102% (typ) of the nominal voltage, both
www.maximintegrated.com
high-side and low-side FETs are turned off and the device
enters hibernate operation until the load discharges the
output to 101% (typ) of the nominal voltage. Most of
the internal blocks are turned off in hibernate operation
to save quiescent current. After the output falls below
101% (typ) of the nominal voltage, the device comes
out of hibernate operation, turns on all internal blocks,
and again commences the process of delivering pulses
of energy to the output until it reaches 102% (typ) of the
nominal output voltage. The device naturally exits PFM
mode when the load current increases to a magnitude of
approximately:
IPFM - (ΔI/2)
where ΔI is the peak-peak ripple current in the output
inductor. The part enters PFM mode again if the load
current reduces to approximately (ΔI/2). See the Inductor
Selection section for details. The advantage of the PFM
mode is higher efficiency at light loads because of lower
current drawn from the supply.
Enable Input (EN/UVLO) and Soft-Start (SS)
When EN/UVLO voltage increases above 1.25V (typ), the
device initiates a soft-start sequence. The duration of the
soft-start depends on the status of the SS pin voltage at
the time of power-up. If the SS pin is not connected, the
device uses a fixed 5ms internal soft-start to ramp up the
internal error-amplifier reference. If a capacitor is connected from SS to GND, a 5μA current source charges the
capacitor and ramps up the SS pin voltage. The SS pin
voltage is used as reference for the internal error amplifier. Such a reference ramp-up allows the output voltage
to increase monotonically from zero to the final set value
independent of the load current.
EN/UVLO can be used as an input voltage UVLOadjustment input. An external voltage-divider between
IN and EN/UVLO to GND adjusts the input voltage at
which the device turns on or turns off. See Setting the
Input Undervoltage-Lockout Level section for details.
If input UVLO programming is not desired, connect
EN/UVLO to IN (see the Electrical Characteristics table for
EN/UVLO rising and falling-threshold voltages). Driving
EN/UVLO low disables both power MOSFETs, as well as
other internal circuitry, and reduces IN quiescent current
to below 1.2μA. The SS capacitor is discharged with an
internal pulldown resistor when EN/UVLO is low. If the
EN/UVLO pin is driven from an external signal source,
a series resistance of minimum 1kW is recommended to
be placed between the signal source output and the EN/
UVLO pin, to reduce voltage ringing on the line.
Maxim Integrated │ 12
MAX17550
60V, 25mA, Ultra-Small, High-Efficiency
Synchronous Step-Down DC-DC Converter
with 22µA No-Load Supply Current
Switching Frequency (RT/SYNC)
Switching frequency of the device can be programmed
from 100kHz to 2.2MHz by using a resistor connected from
RT/SYNC to GND. The switching frequency (fSW) is related to the resistor connected at the RT/SYNC pin (RT) by
the following equation, where RT is in kΩ and fSW is in kHz:
RT =
42000
f SW
The switching frequency in ranges of 130kHz to
160kHz and 230kHz to 280kHz are not allowed for user
programming to ensure proper configuration of the
internal adaptive-loop compensation scheme.
External Synchronization
The RT/SYNC pin can be used to synchronize the
device’s internal oscillator to an external system clock.
The external clock should be coupled to the RT/SYNC
pin through a 47pF capacitor, as shown in Figure 1. The
external clock logic-high level should be higher than 3V,
logic-low level lower than 0.5V and the duty cycle of the
external clock should be in the range of 10% to 70%.
External-clock synchronization is allowed only in PWM
mode (MODE pin connected to GND). The RT resistor
should be selected to set the switching frequency 10%
lower than the external clock frequency. The external
clock should be applied at least 500μs after enabling
the device for proper configuration of the internal loop
compensation.
External Bias (VOUT)
The device provides a VOUT pin to power the internal
blocks from a low-voltage supply. When the VOUT pin
voltage exceeds 3.1V, the device draws switching and
quiescent current from this pin to improve the converter’s
efficiency. In applications with an output voltage setting
from 3.3V to 5V, VOUT should be decoupled to GND with
MAX17550
47pF
RT/SYNC
CLOCK
SOURCE
RT
VLOGIC-HIGH
a ceramic capacitor and be connected to the positive
terminal of the output capacitor with a resistor (R4, C1), as
shown in the typical application circuits. In the absence of
R4 and C1, the absolute maximum rating of VOUT (-0.3V)
can be exceeded (under short-circuit conditions) due to
oscillations between the ceramic output capacitor and the
inductance of the short-circuit path. In general, parasitic
board or wiring inductance should be minimized and the
output voltage waveform under short-circuit operation
should be verified to ensure that the absolute maximum
rating of VOUT is not exceeded. For applications with an
output voltage setting less than 3.3V or greater than 5V,
VOUT should be connected to GND.
Reset Output (RESET)
The device includes an open-drain RESET output to
monitor output voltage. RESET should be pulled up with
an external resistor to the desired external power supply.
RESET goes high-impedance 2ms after the output rises
above 95% of its nominal set value and pulls low when
the output voltage falls below 92% of the set nominal
output voltage. RESET asserts low during the hiccup
timeout period.
Startup Into a Prebiased Output
The device supports monotonic startup into a prebiased
output. When the device starts into a prebiased output,
both the high-side and low-side switches are turned off so
that the converter does not sink current from the output.
High-side and low-side switches do not start switching
until the PWM comparator commands the first PWM
pulse, at which point switching commences. The output
voltage is then smoothly ramped up to the target value
in alignment with the internal reference. Such a feature is
useful in applications where digital integrated circuits with
multiple rails are powered.
Operating Input Voltage Range
The maximum operating input voltage is determined by
the minimum controllable on-time. The minimum operating input voltage is determined by the maximum duty
cycle and circuit voltage drops. The minimum and maximum operating input voltages for a given output voltage
should be calculated as follows:
=
VINMIN
VOUT + (I OUT × (R DCR + 6.0))
+ (I OUT × 5.1)
D MAX
VINMAX =
VLOGIC-LOW
DUTY
Figure 1. Synchronization to an External Clock
www.maximintegrated.com
VOUT
t ONMIN × f SW
where VOUT is the steady-state output voltage, IOUT is
the maximum load current, RDCR is the DC resistance of
Maxim Integrated │ 13
MAX17550
60V, 25mA, Ultra-Small, High-Efficiency
Synchronous Step-Down DC-DC Converter
with 22µA No-Load Supply Current
the inductor, fSW is the switching frequency (max), DMAX
is the maximum duty cycle (0.9), and tONMIN is the worstcase minimum controllable switch on-time (128ns)
Overcurrent Protection, HICCUP Mode
The device implements a HICCUP-type overload protection scheme to protect the inductor and internal FETs
under output short-circuit conditions. When the inductor
peak current exceeds 0.072A (typ) 16 consecutive times,
the part enters HICCUP mode. In this mode, the part is
initially operated with hysteretic cycle-by-cycle peak-current
limit that continues for a time period equal to twice the
soft-start time. The part is then turned off for a fixed
51ms hiccup timeout period. This sequence of hysteretic
inductor current waveforms, followed by a hiccup timeout
period, continues until the short/overload on the output is
removed. Since the inductor current is bound between two
limits, inductor current runway never happens.
Thermal-Overload Protection
Thermal-overload protection limits the total power dissipation in the IC. When the junction temperature exceeds
+160°C, an on-chip thermal sensor shuts down the
device, turns off the internal power MOSFETs, allowing it
to cool down. The device turns on after the junction temperature cools by 20°C.
Applications Information
Inductor Selection
A low-loss inductor having the lowest possible DC resistance that fits in the allotted dimensions should be selected. Calculate the required inductance from the equation:
37000 x VOUT
L=
f SW
where L is inductance in μH, VOUT is output voltage
and fSW is the switching frequency in kHz. Calculate the
peak-peak ripple current (ΔI) in the output inductor from
the equation:


V
1000 × VOUT × 1 − OUT 
V
IN 

∆I =
f SW × L
Once the L value is known, the next step is to select
the right core material. Ferrite and powdered iron are
commonly-available core materials. Ferrite cores have
low core losses and are preferred for high-efficiency
designs. Powdered iron cores have more core losses, but
are relatively less expensive than ferrite cores.
Input Capacitor Selection
Small ceramic input capacitors are recommended for the
IC. The input capacitor reduces peak current drawn from
the power source and reduces noise and voltage ripple
on the input caused by the switching circuitry. A minimum
of 1μF, X7R-grade capacitor in a package larger than 0805
is recommended for the input capacitor of the IC to keep the
input-voltage ripple under 2% of the minimum input voltage,
and to meet the maximum ripple-current requirements.
Output Capacitor Selection
Small ceramic X7R-grade output capacitors are recommended for the device. The output capacitor serves two
functions: storing sufficient energy to support the output
voltage under load-transient conditions and stabilizing the
device’s internal control loop. Usually the output capacitor
is sized to support a step load of 50% of the maximum
output current in the application, such that the outputvoltage deviation is less than 3%. Calculate the minimum
required output capacitance from the following equations
Frequency
Range
(kHz)
Minimum Output
Capacitance
(μF)
100 to 130
25/VOUT
160 to 230
25/VOUT
280 to 2200
15/VOUT
It should be noted that dielectric materials used in ceramic
capacitors exhibit capacitance loss due to DC bias levels and
should be appropriately derated to ensure the required
output capacitance is obtained in the application.
where L is inductance in μH, VOUT is output voltage, VIN
is input voltage and fSW is the switching frequency in kHz.
The saturation current rating of the inductor must exceed
the maximum current-limit value (IPEAK-LIMIT). The
saturation current rating should be at least 0.078A.
www.maximintegrated.com
Maxim Integrated │ 14
MAX17550
60V, 25mA, Ultra-Small, High-Efficiency
Synchronous Step-Down DC-DC Converter
with 22µA No-Load Supply Current
Soft-Start Capacitor Selection
The MAX17550 offers a 5.1ms internal soft-start when
the SS pin is left unconnected. When adjustable soft-start
time is required, connect a capacitor from SS to GND
to program the soft-start time.
The minimum soft-start time is related to the output
capacitance (COUT) and the output voltage (VOUT) by the
following equation:
tSS > 0.05 x COUT x VOUT
where tSS is in milliseconds and COUT is in µF.
Soft-start time (tSS) is related to the capacitor connected at
SS (CSS) by the following equation:
C=
SS 6.25 × t SS
where tSS is in milliseconds and CSS is in nanofarads.
Setting the Input Undervoltage-Lockout Level
The device offers an adjustable input undervoltagelockout level. Set the voltage at which the device turns on
with a resistive voltage-divider connected from IN to GND
(see Figure 2). Connect the center node of the divider to
EN/UVLO.
Choose R1 to be 3.3MΩ max and then calculate R2 as
follows:
R2 =
R1× 1.25
(VINU - 1.25)
These transients can occur in conditions such as hotplugging from a low-impedance source or due to inductive
load-switching and surges on the supply lines.
Power Dissipation
Ensure that the junction temperature of the device does
not exceed 125°C under the operating conditions specified for the power supply. At a particular operating condition, the power losses that lead to temperature rise of the
device are estimated as follows:

 1 
PLOSS = POUT x  - 1  - (I OUT 2 x R DCR )
 η 

POUT = VOUT x I OUT
where POUT is the output power, η is the efficiency of
power conversion, and RDCR is the DC resistance of the
output inductor. See the Typical Operating Characteristics
section for the power-conversion efficiency, or measure
the efficiency to determine the total power dissipation.
VIN
IN
R1
MAX17550
EN/UVLO
R2
Figure 2. Adjustable EN/UVLO Network
where VINU is the voltage at which the device is required
to turn on.
Adjusting the Output Voltage
VOUT
The output voltage can be programmed from 0.8V to
0.9 x VIN. Set the output voltage by connecting a resistordivider from output to FB to GND (see Figure 3). Choose
R2 in the range of 25kΩ to 100kΩ and calculate R1 with
the following equation:
V

R1 R2 ×  OUT − 1
=
 0.8

Transient Protection
In applications where fast line transients or oscillations
with a slew rate in excess of 15V/µs are expected during power-up or steady-state operation, the MAX17550
should be protected with a series resistor that forms a
lowpass filter with the input ceramic capacitor (Figure 4).
www.maximintegrated.com
R1
MAX17550
FB
R2
GND
Figure 3. Setting the Output Voltage
4.7Ω
IN
CIN
1µF
MAX17550
GND
Figure 4. Transient Protection
Maxim Integrated │ 15
MAX17550
60V, 25mA, Ultra-Small, High-Efficiency
Synchronous Step-Down DC-DC Converter
with 22µA No-Load Supply Current
The junction temperature (TJ) of the device can be
estimated at any ambient temperature (TA) from the
following equation:
TJ= T A + (θ JA × PLOSS )
where θJA is the junction-to-ambient thermal impedance
of the package.
PCB Layout Guidelines
Careful PCB layout (Figure 5) is critical to achieving clean
and stable operation. The switching power stage requires
particular attention. Follow these guidelines for good PCB
layout:
Figure 5
VIN
● Place the input ceramic capacitor as close as possible
to VIN and GND pins
● Minimize the area formed by the LX pin and inductor
connection to reduce the radiated EMI
● Ensure that all feedback connections are short and
direct
● Route high-speed switching node (LX) away from the
signal pins
For a sample PCB layout that ensures the first-pass
success, refer to the MAX17550 evaluation kit data sheet.
MAX17550
R1
CIN
CSS
VOUT
COUT
GND
EN/UVLO
R2
L1
LX
IN
SS
VOUT
CF
R7
MODE
FB
RT/SYNC
R4
R5
R3
R6
VOUT
RESET
GND PLANE
CIN
VIN PLANE
R1
L1
LX
IN
MODE
RT/SYNC
R3
RESET
SS
F
CSS B
Cout
GND
EN/UVLO
R2
VOUT
PLANE
U1
R6
R4
R7
R5
GND PLANE
VOUT
Cf
Vias to Bottom -Side Ground Plane
Vias to V OUT
Vias to RESET
Figure 5. Layout Guidelines
www.maximintegrated.com
Maxim Integrated │ 16
MAX17550
60V, 25mA, Ultra-Small, High-Efficiency
Synchronous Step-Down DC-DC Converter
with 22µA No-Load Supply Current
Typical Application Circuits
VIN
6V TO 60V
CIN
1µF
IN
L1
1mH
LX
GND
MODE
C1
0.22µF
R3
191kΩ
SS
RT/SYNC
VOUT
3.3V, 25mA
COUT
10µF
GND
VOUT
MODE
R2
49.9kΩ
L1
680µH
MAX17550
R1
261kΩ
FB
RT/SYNC
LX
EN/UVLO
R4
22.1Ω
SS
VOUT
IN
CIN
1µF
COUT
10µF
MAX17550
EN/UVLO
VIN
4V TO 60V
VOUT
5V, 25mA
R4
22.1Ω
C1
0.22µF
R1
158kΩ
FB
R2
49.9kΩ
R3
191kΩ
RESET
RESET
SWITCHING FREQUENCY = 220kHz
L1 COILCRAFT LPS5030-105M
COUT MURATA 10µF/X7R/6.3V/0805 (GRM21BR70J106K)
CIN MURATA 1µF/X7R/100V/1206 (GRM31CR72A105K)
SWITCHING FREQUENCY = 220kHz
L1 COILCRAFT LPS5030-684M
COUT MURATA 10µF/X7R/6.3V/0805 (GRM21BR70J106K)
CIN MURATA 1µF/X7R/100V/1206 (GRM31CR72A105K)
Figure 6. High-Efficiency 5V, 25mA Regulator
VIN
6V TO 60V
CIN
1µF
Figure 7. High-Efficiency 3.3V, 25mA Regulator
IN
MAX17550
EN/UVLO
SS
MODE
LX
VOUT
5V, 25mA
COUT
4.7µF
GND
VOUT
R4
22.1Ω
C1
0.22µF
R1
261kΩ
FB
R2
49.9kΩ
RT/SYNC
R3
69.8kΩ
L1
330µH
RESET
SWITCHING FREQUENCY = 600kHz
L1 COILCRAFT LPS3314-334M
COUT MURATA 4.7µF/X7R/10V/0805 (GRM21BR71A475K)
CIN MURATA 1µF/X7R/100V/1206 (GRM31CR72A105K)
Figure 8. Small-Footprint 5V, 25mA Regulator
www.maximintegrated.com
Maxim Integrated │ 17
MAX17550
60V, 25mA, Ultra-Small, High-Efficiency
Synchronous Step-Down DC-DC Converter
with 22µA No-Load Supply Current
Typical Application Circuits (continued)
VIN
4V TO 45V
CIN
1µF
IN
MAX17550
EN/UVLO
SS
MODE
LX
L1
220μH
VIN
4V TO 24V
COUT
10µF
GND
VOUT
IN
CIN
1µF
MAX17550
EN/UVLO
R4
22.1Ω
SS
C1
0.22µF
R1
158kΩ
FB
MODE
R2
49.9kΩ
RT/SYNC
R3
69.8kΩ
VOUT
3.3V, 25mA
R3
69.8kΩ
GND
VOUT
R1
127kΩ
FB
R2
100kΩ
RESET
SWITCHING FREQUENCY = 600kHz
L1 COILCRAFT LPS3015-124M
COUT MURATA 10μF/X7R/6.3V/0805 (GRM21BR70J106K)
CIN MURATA 1µF/X7R/100V/1206 (GRM31CR72A105K)
SWITCHING FREQUENCY = 600kHz
L1 COILCRAFT LPS3314-224M
COUT MURATA 10μF/X7R/6.3V/0805 (GRM21BR70J106K)
CIN MURATA 1µF/X7R/100V/1206 (GRM31CR72A105K)
Figure 9. Small-Footprint 3.3V, 25mA Regulator
CIN
1µF
VOUT
1.8V, 25mA
COUT
10µF
RT/SYNC
RESET
VIN
15V TO 60V
LX
L1
120µH
Figure 10. Small-Footprint 1.8V, 25mA Regulator
IN
MAX17550
EN/UVLO
SS
MODE
LX
VOUT
12V, 25mA
COUT
4.7µF
GND
VOUT
R1
348kΩ
FB
R2
24.9kΩ
RT/SYNC
R3
69.8kΩ
L1
820µH
RESET
SWITCHING FREQUENCY = 600kHz
L1 COILCRAFT LPS4018-824M
COUT MURATA 4.7μF/X7R/16V/0805 (GRM21BR71C475K)
CIN MURATA 1µF/X7R/100V/1206 (GRM31CR72A105K)
Figure 11. Small-Footprint 12V, 25mA Step-Down Regulator
www.maximintegrated.com
Maxim Integrated │ 18
MAX17550
60V, 25mA, Ultra-Small, High-Efficiency
Synchronous Step-Down DC-DC Converter
with 22µA No-Load Supply Current
Ordering Information
PART
Package Information
TEMP RANGE
PIN-PACKAGE
MAX17550ATB+
-40°C to +125°C
10 TDFN-EP*
MAX17550AUB+
-40°C to +125°C
10 μMAX
+Denotes a lead(Pb)-free/RoHS-compliant package.
*EP = Exposed pad.
Chip Information
PROCESS: BiCMOS
www.maximintegrated.com
For the latest package outline information and land patterns
(footprints), go to www.maximintegrated.com/packages. Note
that a “+”, “#”, or “-” in the package code indicates RoHS status
only. Package drawings may show a different suffix character, but
the drawing pertains to the package regardless of RoHS status.
PACKAGE
TYPE
PACKAGE
CODE
OUTLINE
NO.
LAND
PATTERN NO.
10 TDFN-EP
T1032N+1
21-0429
90-0082
10 µMAX
U10+5
21-0061
90-0330
Maxim Integrated │ 19
MAX17550
60V, 25mA, Ultra-Small, High-Efficiency
Synchronous Step-Down DC-DC Converter
with 22µA No-Load Supply Current
Revision History
REVISION
NUMBER
REVISION
DATE
PAGES
CHANGED
0
9/14
Initial release
1
3/15
Updated to include additional Typical Operating Characteristics
DESCRIPTION
—
2, 6–9, 15, 17, 18
For pricing, delivery, and ordering information, please contact Maxim Direct at 1-888-629-4642, or visit Maxim Integrated’s website at www.maximintegrated.com.
Maxim Integrated cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a Maxim Integrated product. No circuit patent licenses
are implied. Maxim Integrated reserves the right to change the circuitry and specifications without notice at any time. The parametric values (min and max limits)
shown in the Electrical Characteristics table are guaranteed. Other parametric values quoted in this data sheet are provided for guidance.
Maxim Integrated and the Maxim Integrated logo are trademarks of Maxim Integrated Products, Inc.
© 2015 Maxim Integrated Products, Inc. │ 20

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