datasheet for ATmega164A by Atmel

datasheet for ATmega164A by Atmel

Features

High-performance, low-power 8-bit Atmel

®

Advanced RISC architecture

AVR

®

Microcontroller

– 131 powerful Instructions – most single-clock cycle execution

– 32 × 8 general purpose working registers

– Fully static operation

– Up to 20MIPS throughput at 20MHz

– On-chip 2-cycle multiplier

High endurance non-volatile memory segments

– 16/32/64/128KBytes of In-System Self-programmable Flash program memory

– 512/1K/2K/4KBytes EEPROM

– 1/2/4/16KBytes Internal SRAM

– Write/Erase Cycles: 10,000 Flash/ 100,000 EEPROM

– Data retention: 20 years at 85°C/ 100 years at 25°C

(1)

– Optional Boot Code Section with Independent Lock Bits

In-System Programming by On-chip Boot Program

True Read-While-Write Operation

– Programming Lock for Software Security

Atmel QTouch

®

library support

– Capacitive touch buttons, sliders and wheels

– QTouch and QMatrix acquisition

– Up to 64 sense channels

JTAG (IEEE std. 1149.1 Compliant) Interface

– Boundary-scan Capabilities According to the JTAG Standard

– Extensive On-chip Debug Support

– Programming of Flash, EEPROM, Fuses, and Lock Bits through the JTAG Interface

Peripheral Features

– Two 8-bit Timer/Counters with Separate Prescalers and Compare Modes

– One/two 16-bit Timer/Counter with Separate Prescaler, Compare Mode, and Capture Mode

– Real Time Counter with Separate Oscillator

– Six PWM Channels

– 8-channel, 10-bit ADC

Differential mode with selectable gain at 1×, 10× or 200×

– Byte-oriented Two-wire Serial Interface

– Two Programmable Serial USART

– Master/Slave SPI Serial Interface

– Programmable Watchdog Timer with Separate On-chip Oscillator

– On-chip Analog Comparator

– Interrupt and Wake-up on Pin Change

Special Microcontroller Features

– Power-on Reset and Programmable Brown-out Detection

– Internal Calibrated RC Oscillator

– External and Internal Interrupt Sources

– Six Sleep Modes: Idle, ADC Noise Reduction, Power-save, Power-down, Standby and

Extended Standby

I/O and Packages

– 32 Programmable I/O Lines

– 40-pin PDIP, 44-lead TQFP, 44-pad VQFN/QFN/MLF

– 44-pad DRQFN

– 49-ball VFBGA

Operating Voltages

– 1.8 - 5.5V

Speed Grades

– 0 - 4MHz @ 1.8 - 5.5V

– 0 - 10MHz @ 2.7 - 5.5V

– 0 - 20MHz @ 4.5 - 5.5V

Power Consumption at 1MHz, 1.8V, 25

°C

– Active: 0.4mA

– Power-down Mode: 0.1µA

– Power-save Mode: 0.6µA (Including 32kHz RTC)

Note: 1. See

”Data retention” on page 9

for details.

8-bit Atmel

Microcontroller with

16/32/64/128K

Bytes In-System

Programmable

Flash

ATmega164A

ATmega164PA

ATmega324A

ATmega324PA

ATmega644A

ATmega644PA

ATmega1284

ATmega1284P

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

1.

Pin configurations

1.1

Pinout - PDIP/TQFP/VQFN/QFN/MLF for

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P

Figure 1-1.

Pinout.

(PCINT8/XCK0/T0) PB0

(PCINT9/CLKO/T1) PB1

(PCINT10/INT2/AIN0) PB2

(PCINT11/OC0A/AIN1) PB3

(PCINT12/OC0B/SS) PB4

(PCINT13/ICP3/MOSI) PB5

(PCINT14/OC3A/MISO) PB6

(PCINT15/OC3B/SCK) PB7

RESET

VCC

GND

XTAL2

XTAL1

(PCINT24/RXD0/T3) PD0

(PCINT25/TXD0) PD1

(PCINT26/RXD1/INT0) PD2

(PCINT27/TXD1/INT1) PD3

(PCINT28/XCK1/OC1B) PD4

(PCINT29/OC1A) PD5

(PCINT30/OC2B/ICP) PD6

PA0 (ADC0/PCINT0)

PA1 (ADC1/PCINT1)

PA2 (ADC2/PCINT2)

PA3 (ADC3/PCINT3)

PA4 (ADC4/PCINT4)

PA5 (ADC5/PCINT5)

PA6 (ADC6/PCINT6)

PA7 (ADC7/PCINT7)

AREF

GND

AVCC

PC7 (TOSC2/PCINT23)

PC6 (TOSC1/PCINT22)

PC5 (TDI/PCINT21)

PC4 (TDO/PCINT20)

PC3 (TMS/PCINT19)

PC2 (TCK/PCINT18)

PC1 (SDA/PCINT17)

PC0 (SCL/PCINT16)

PD7 (OC2A/PCINT31)

TQFP/QFN/MLF

(PCINT13/ICP3/MOSI) PB5

(PCINT14/OC3A/MISO) PB6

(PCINT15/OC3B/SCK) PB7

RESET

VCC

GND

XTAL2

XTAL1

(PCINT24/RXD0/T3) PD0

(PCINT25/TXD0) PD1

(PCINT26/RXD1/INT0) PD2

PA4 (ADC4/PCINT4)

PA5 (ADC5/PCINT5)

PA6 (ADC6/PCINT6)

PA7 (ADC7/PCINT7)

AREF

GND

AVCC

PC7 (TOSC2/PCINT23)

PC6 (TOSC1/PCINT22)

PC5 (TDI/PCINT21)

PC4 (TDO/PCINT20)

8272D–AVR–05/12

Note: The large center pad underneath the VQFN/QFN/MLF package should be soldered to ground on the board to ensure good mechanical stability.

2

ATmega164A/PA/324A/PA/644A/PA/1284/P

1.2

Pinout - DRQFN for Atmel ATmega164A/164PA/324A/324PA

Figure 1-2.

DRQFN - pinout.

Top view Bottom view

A1

B1

A2

B2

A3

B3

A4

B4

A5

B5

A6

A18

B15

A17

B14

A16

B13

A15

B12

A14

B11

A13

A18

B15

A17

B14

A16

B13

A15

B12

A14

B11

A13

A1

B1

A2

B2

A3

B3

A4

B4

A5

B5

A6

Table 1-1.

A3

B3

A4

B4

A1

B1

A2

B2

A5

B5

A6

DRQFN - pinout.

PB5

PB6

PB7

RESET

VCC

GND

XTAL2

XTAL1

PD0

PD1

PD2

A7

B6

A8

B7

A9

B8

A10

B9

A11

B10

A12

PD3

PD4

PD5

PD6

PD7

VCC

GND

PC0

PC1

PC2

PC3

A15

B13

A16

B14

A13

B11

A14

B12

A17

B15

A18

PC4

PC5

PC6

PC7

AVCC

GND

AREF

PA7

PA6

PA5

PA4

A21

B18

A22

B19

A19

B16

A20

B17

A23

B20

A24

PA3

PA2

PA1

PA0

VCC

GND

PB0

PB1

PB2

PB3

PB4

3

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

1.3

Pinout - VFBGA for Atmel ATmega164A/164PA/324A/324PA

Figure 1-3.

VFBGA - pinout.

Top view

1

2 3 4 5 6 7

Bottom view

7 6 5 4 3 2

1

C

D

A

B

E

F

G

C

D

A

B

E

F

G

F

G

D

E

A

B

C

Table 1-2.

BGA - pinout.

1

GND

PB6

VCC

GND

XTAL1

PD2

GND

2

PB4

PB5

RESET

XTAL2

PD1

PD3

PD4

3

PB2

PB3

PB7

PD0

PD5

PD6

VCC

4

GND

PB0

PB1

GND

PD7

PC0

GND

5

VCC

PA0

PA1

PA4

PC5

PC2

PC1

6

PA2

PA3

PA6

PA7

PC7

PC4

PC3

7

GND

PA5

AREF

GND

AVCC

PC6

GND

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8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

2.

Overview

2.1

Block diagram

The Atmel ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P is a low-power CMOS

8-bit microcontroller based on the AVR enhanced RISC architecture. By executing powerful i n s t r u c t i o n s i n a s i n g l e c l o c k c y c l e , t h e

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P achieves throughputs approaching 1 MIPS per MHz allowing the system designer to optimize power consumption versus processing speed.

Figure 2-1.

Block diagram.

PA7..0

PB7..0

VCC

RESET

GND

XTAL1

Power

Supervision

POR / BOD &

RESET

Watchdog

Timer

Watchdog

Oscillator

Oscillator

Circuits /

Clock

Generation

PORT A (8)

A/D

Converter

EEPROM

Internal

Bandgap reference

PORT B (8)

Analog

Comparator

SPI

USART 0

XTAL2

JTAG/OCD

TWI FLASH

CPU

SRAM

8bit T/C 0

16bit T/C 1

8bit T/C 2

16bit T/C 3

16bit T/C 1

USART 1

8272D–AVR–05/12

PORT C (8) PORT D (8)

TOSC2/PC7 TOSC1/PC6 PC5..0

PD7..0

The AVR core combines a rich instruction set with 32 general purpose working registers. All the

32 registers are directly connected to the Arithmetic Logic Unit (ALU), allowing two independent registers to be accessed in one single instruction executed in one clock cycle. The resulting architecture is more code efficient while achieving throughputs up to ten times faster than conventional CISC microcontrollers.

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8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

The Atmel ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P provide the following features:

16/32/64/128Kbytes of In-System Programmable Flash with Read-While-Write capabilities,

512/1K/2K/4Kbytes EEPROM, 1/2/4/16Kbytes SRAM, 32 general purpose I/O lines, 32 general purpose working registers, Real Time Counter (RTC), three flexible Timer/Counters with compare modes and PWM, 2 USARTs, a byte oriented two-wire Serial Interface, a 8-channel, 10-bit

ADC with optional differential input stage with programmable gain, programmable Watchdog

Timer with Internal Oscillator, an SPI serial port, IEEE std. 1149.1 compliant JTAG test interface, also used for accessing the On-chip Debug system and programming and six software selectable power saving modes. The Idle mode stops the CPU while allowing the SRAM,

Timer/Counters, SPI port, and interrupt system to continue functioning. The Power-down mode saves the register contents but freezes the Oscillator, disabling all other chip functions until the next interrupt or Hardware Reset. In Power-save mode, the asynchronous timer continues to run, allowing the user to maintain a timer base while the rest of the device is sleeping. The ADC

Noise Reduction mode stops the CPU and all I/O modules except Asynchronous Timer and

ADC, to minimize switching noise during ADC conversions. In Standby mode, the Crystal/Resonator Oscillator is running while the rest of the device is sleeping. This allows very fast start-up combined with low power consumption. In Extended Standby mode, both the main Oscillator and the Asynchronous Timer continue to run.

Atmel offers the QTouch

®

library for embedding capacitive touch buttons, sliders and wheels functionality into AVR microcontrollers. The patented charge-transfer signal acquisition offers robust sensing and includes fully debounced reporting of touch keys and includes Adjacent Key

Suppression

®

(AKS

) technology for unambiguous detection of key events. The easy-to-use

QTouch Suite toolchain allows you to explore, develop and debug your own touch applications.

The device is manufactured using Atmel’s high-density nonvolatile memory technology. The Onchip ISP Flash allows the program memory to be reprogrammed in-system through an SPI serial interface, by a conventional nonvolatile memory programmer, or by an On-chip Boot program running on the AVR core. The boot program can use any interface to download the application program in the application Flash memory. Software in the Boot Flash section will continue to run while the Application Flash section is updated, providing true Read-While-Write operation. By combining an 8-bit RISC CPU with In-System Self-Programmable Flash on a monolithic chip, the Atmel ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P is a powerful microcontroller that provides a highly flexible and cost effective solution to many embedded control applications.

The ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P is supported with a full suite of program and system development tools including: C compilers, macro assemblers, program debugger/simulators, in-circuit emulators, and evaluation kits.

6

ATmega164A/PA/324A/PA/644A/PA/1284/P

2.2

Comparison between ATmega164A, ATmega164PA, ATmega324A, ATmega324PA,

ATmega644A, ATmega644PA, ATmega1284 and ATmega1284P

Table 2-1.

Device

ATmega164A

ATmega164PA

ATmega324A

ATmega324PA

ATmega644A

ATmega644PA

ATmega1284

ATmega1284P

Differences between ATmega164A, ATmega164PA, ATmega324A, ATmega324PA, ATmega644A,

ATmega644PA, ATmega1284 and ATmega1284P.

Units Flash

16K

16K

32K

32K

64K

64K

128K

128K

1K

2K

2K

4K

4K

EEPROM

512

512

1K

2K

4K

4K

16K

16K

RAM

1K

1K

2K bytes

2.3

Pin Descriptions

2.3.1

2.3.2

2.3.3

2.3.4

2.3.5

VCC

Digital supply voltage.

GND

Ground.

Port A (PA7:PA0)

Port A serves as analog inputs to the Analog-to-digital Converter.

Port A also serves as an 8-bit bi-directional I/O port with internal pull-up resistors (selected for each bit). The Port A output buffers have symmetrical drive characteristics with both high sink and source capability. As inputs, Port A pins that are externally pulled low will source current if the pull-up resistors are activated. The Port A pins are tri-stated when a reset condition becomes active, even if the clock is not running.

P o r t A a l s o s e r v e s t h e f u n c t i o n s o f v a r i o u s s p e c i a l f e a t u r e s o f t h e A t m e l

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P as listed on page 80

.

Port B (PB7:PB0)

Port B is an 8-bit bi-directional I/O port with internal pull-up resistors (selected for each bit). The

Port B output buffers have symmetrical drive characteristics with both high sink and source capability. As inputs, Port B pins that are externally pulled low will source current if the pull-up resistors are activated. The Port B pins are tri-stated when a reset condition becomes active, even if the clock is not running.

P o r t B a l s o s e r v e s t h e f u n c t i o n s o f v a r i o u s s p e c i a l f e a t u r e s o f t h e

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P as listed on page 82

.

Port C (PC7:PC0)

Port C is an 8-bit bi-directional I/O port with internal pull-up resistors (selected for each bit). The

Port C output buffers have symmetrical drive characteristics with both high sink and source

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8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

2.3.6

2.3.7

2.3.8

2.3.9

2.3.10

2.3.11

capability. As inputs, Port C pins that are externally pulled low will source current if the pull-up resistors are activated. The Port C pins are tri-stated when a reset condition becomes active, even if the clock is not running.

Port C also serves the functions of the JTAG interface, along with special features of the Atmel

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P as listed on page 85

.

Port D (PD7:PD0)

Port D is an 8-bit bi-directional I/O port with internal pull-up resistors (selected for each bit). The

Port D output buffers have symmetrical drive characteristics with both high sink and source capability. As inputs, Port D pins that are externally pulled low will source current if the pull-up resistors are activated. The Port D pins are tri-stated when a reset condition becomes active, even if the clock is not running.

P o r t D a l s o s e r v e s t h e f u n c t i o n s o f v a r i o u s s p e c i a l f e a t u r e s o f t h e

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P as listed on page 88

.

RESET

Reset input. A low level on this pin for longer than the minimum pulse length will generate a reset, even if the clock is not running. The minimum pulse length is given in

”” on page 336

.

Shorter pulses are not guaranteed to generate a reset.

XTAL1

Input to the inverting Oscillator amplifier and input to the internal clock operating circuit.

XTAL2

Output from the inverting Oscillator amplifier.

AVCC

AVCC is the supply voltage pin for Port A and the Analog-to-digital Converter. It should be externally connected to V

CC

, even if the ADC is not used. If the ADC is used, it should be connected to V

CC

through a low-pass filter.

AREF

This is the analog reference pin for the Analog-to-digital Converter.

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ATmega164A/PA/324A/PA/644A/PA/1284/P

3.

Resources

A comprehensive set of development tools, application notes and datasheetsare available for download on http://www.atmel.com/avr.

4.

About code examples

This documentation contains simple code examples that briefly show how to use various parts of the device. Be aware that not all C compiler vendors include bit definitions in the header files and interrupt handling in C is compiler dependent. Please confirm with the C compiler documentation for more details.

The code examples assume that the part specific header file is included before compilation. For

I/O registers located in extended I/O map, "IN", "OUT", "SBIS", "SBIC", "CBI", and "SBI" instructions must be replaced with instructions that allow access to extended I/O. Typically "LDS" and

"STS" combined with "SBRS", "SBRC", "SBR", and "CBR".

5.

Data retention

Note: 1.

Reliability Qualification results show that the projected data retention failure rate is much less than 1 PPM over 20 years at 85°C or 100 years at 25°C.

6.

Capacitive touch sensing

The Atmel QTouch Library provides a simple to use solution to realize touch sensitive interfaces on most Atmel AVR microcontrollers. The QTouch Library includes support for the QTouch and

QMatrix acquisition methods.

Touch sensing can be added to any application by linking the appropriate Atmel QTouch Library for the AVR Microcontroller. This is done by using a simple set of APIs to define the touch channels and sensors, and then calling the touch sensing API’s to retrieve the channel information and determine the touch sensor states.

The QTouch Library is FREE and downloadable from the Atmel website at the following location: www.atmel.com/qtouchlibrary . For implementation details and other information, refer to the

Atmel QTouch Library User Guide - also available for download from the Atmel website.

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7.

AVR CPU Core

7.1

Overview

This section discusses the AVR core architecture in general. The main function of the CPU core is to ensure correct program execution. The CPU must therefore be able to access memories, perform calculations, control peripherals, and handle interrupts.

Figure 7-1.

Block diagram of the AVR architecture.

Data Bus 8-bit

Program

Counter

Status and Control

Flash

Program

Memory

Instruction

Register

Instruction

Decoder

Control Lines

32 x 8

General

Purpose

Registrers

ALU

Interrupt

Unit

SPI

Unit

Watchdog

Timer

Analog

Comparator

Data

SRAM

I/O Module1

I/O Module 2

I/O Module n

EEPROM

I/O Lines

In order to maximize performance and parallelism, the AVR uses a Harvard architecture – with separate memories and buses for program and data. Instructions in the program memory are executed with a single level pipelining. While one instruction is being executed, the next instruction is pre-fetched from the program memory. This concept enables instructions to be executed in every clock cycle. The program memory is In-System Reprogrammable Flash memory.

The fast-access Register File contains 32 x 8-bit general purpose working registers with a single clock cycle access time. This allows single-cycle Arithmetic Logic Unit (ALU) operation. In a typ-

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8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

ical ALU operation, two operands are output from the Register File, the operation is executed, and the result is stored back in the Register File – in one clock cycle.

Six of the 32 registers can be used as three 16-bit indirect address register pointers for Data

Space addressing – enabling efficient address calculations. One of the these address pointers can also be used as an address pointer for look up tables in Flash program memory. These added function registers are the 16-bit X-, Y-, and Z-register, described later in this section.

The ALU supports arithmetic and logic operations between registers or between a constant and a register. Single register operations can also be executed in the ALU. After an arithmetic operation, the Status Register is updated to reflect information about the result of the operation.

Program flow is provided by conditional and unconditional jump and call instructions, able to directly address the whole address space. Most AVR instructions have a single 16-bit word format. Every program memory address contains a 16- or 32-bit instruction.

Program Flash memory space is divided in two sections, the Boot Program section and the

Application Program section. Both sections have dedicated Lock bits for write and read/write protection. The SPM instruction that writes into the Application Flash memory section must reside in the Boot Program section.

During interrupts and subroutine calls, the return address Program Counter (PC) is stored on the

Stack. The Stack is effectively allocated in the general data SRAM, and consequently the Stack size is only limited by the total SRAM size and the usage of the SRAM. All user programs must initialize the SP in the Reset routine (before subroutines or interrupts are executed). The Stack

Pointer (SP) is read/write accessible in the I/O space. The data SRAM can easily be accessed through the five different addressing modes supported in the AVR architecture.

The memory spaces in the AVR architecture are all linear and regular memory maps.

A flexible interrupt module has its control registers in the I/O space with an additional Global

Interrupt Enable bit in the Status Register. All interrupts have a separate Interrupt Vector in the

Interrupt Vector table. The interrupts have priority in accordance with their Interrupt Vector position. The lower the Interrupt Vector address, the higher the priority.

The I/O memory space contains 64 addresses for CPU peripheral functions as Control Registers, SPI, and other I/O functions. The I/O Memory can be accessed directly, or as the Data

Space locations following those of the Register File, 0x20 - 0x5F. In addition, the

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P has Extended I/O space from

0x60 - 0xFF in SRAM where only the ST/STS/STD and LD/LDS/LDD instructions can be used.

7.2

ALU – Arithmetic Logic Unit

The high-performance AVR ALU operates in direct connection with all the 32 general purpose working registers. Within a single clock cycle, arithmetic operations between general purpose registers or between a register and an immediate are executed. The ALU operations are divided into three main categories – arithmetic, logical, and bit-functions. Some implementations of the architecture also provide a powerful multiplier supporting both signed/unsigned multiplication and fractional format. See the “Instruction Set” section for a detailed description.

7.3

Status Register

The Status Register contains information about the result of the most recently executed arithmetic instruction. This information can be used for altering program flow in order to perform conditional operations. Note that the Status Register is updated after all ALU operations, as

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ATmega164A/PA/324A/PA/644A/PA/1284/P

7.3.1

specified in the Instruction Set Reference. This will in many cases remove the need for using the dedicated compare instructions, resulting in faster and more compact code.

The Status Register is not automatically stored when entering an interrupt routine and restored when returning from an interrupt. This must be handled by software.

SREG – Status Register

The AVR Status Register – SREG – is defined as:

Bit

0x3F (0x5F)

Read/Write

Initial Value

7

I

R/W

0

6

T

R/W

0

5

H

R/W

0

4

S

R/W

0

3

V

R/W

0

2

N

R/W

0

1

Z

R/W

0

0

C

R/W

0

SREG

• Bit 7 – I: Global Interrupt Enable

The Global Interrupt Enable bit must be set for the interrupts to be enabled. The individual interrupt enable control is then performed in separate control registers. If the Global Interrupt Enable

Register is cleared, none of the interrupts are enabled independent of the individual interrupt enable settings. The I-bit is cleared by hardware after an interrupt has occurred, and is set by the RETI instruction to enable subsequent interrupts. The I-bit can also be set and cleared by the application with the SEI and CLI instructions, as described in the instruction set reference.

• Bit 6 – T: Bit Copy Storage

The Bit Copy instructions BLD (Bit LoaD) and BST (Bit STore) use the T-bit as source or destination for the operated bit. A bit from a register in the Register File can be copied into T by the

BST instruction, and a bit in T can be copied into a bit in a register in the Register File by the

BLD instruction.

• Bit 5 – H: Half Carry Flag

The Half Carry Flag H indicates a Half Carry in some arithmetic operations. Half Carry Is useful in BCD arithmetic. See the “Instruction Set Description” for detailed information.

• Bit 4 – S: Sign Bit, S = N

V

The S-bit is always an exclusive or between the Negative Flag N and the Two’s Complement

Overflow Flag V. See the “Instruction Set Description” for detailed information.

• Bit 3 – V: Two’s Complement Overflow Flag

The Two’s Complement Overflow Flag V supports two’s complement arithmetics. See the

“Instruction Set Description” for detailed information.

• Bit 2 – N: Negative Flag

The Negative Flag N indicates a negative result in an arithmetic or logic operation. See the

“Instruction Set Description” for detailed information.

• Bit 1 – Z: Zero Flag

The Zero Flag Z indicates a zero result in an arithmetic or logic operation. See the “Instruction

Set Description” for detailed information.

• Bit 0 – C: Carry Flag

The Carry Flag C indicates a carry in an arithmetic or logic operation. See the “Instruction Set

Description” for detailed information.

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ATmega164A/PA/324A/PA/644A/PA/1284/P

7.4

General Purpose Register File

The Register File is optimized for the AVR Enhanced RISC instruction set. In order to achieve the required performance and flexibility, the following input/output schemes are supported by the

Register File:

• One 8-bit output operand and one 8-bit result input

• Two 8-bit output operands and one 8-bit result input

• Two 8-bit output operands and one 16-bit result input

• One 16-bit output operand and one 16-bit result input

Figure 7-2 shows the structure of the 32 general purpose working registers in the CPU.

Figure 7-2.

AVR CPU General Purpose Working Registers.

General

Purpose

Working

Registers

7 0 Addr.

R28

R29

R30

R31

R17

R26

R27

R13

R14

R15

R16

R0 0x00

R1 0x01

R2

0x02

0x0D

0x0E

0x0F

0x10

0x11

0x1A

0x1B

0x1C

0x1D

0x1E

0x1F

X-register Low Byte

X-register High Byte

Y-register Low Byte

Y-register High Byte

Z-register Low Byte

Z-register High Byte

Most of the instructions operating on the Register File have direct access to all registers, and most of them are single cycle instructions.

As shown in Figure 7-2

, each register is also assigned a data memory address, mapping them directly into the first 32 locations of the user Data Space. Although not being physically implemented as SRAM locations, this memory organization provides great flexibility in access of the registers, as the X-, Y- and Z-pointer registers can be set to index any register in the file.

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7.4.1

The X-register, Y-register, and Z-register

The registers R26..R31 have some added functions to their general purpose usage. These registers are 16-bit address pointers for indirect addressing of the data space. The three indirect

address registers X, Y, and Z are defined as described in Figure 7-3

.

Figure 7-3.

The X-, Y-, and Z-registers.

XH

X-register

15

7

R27 (0x1B)

0 7

R26 (0x1A)

XL 0

0

7.5

Stack Pointer

Y-register

15

7

R29 (0x1D)

YH

0 7

R28 (0x1C)

YL 0

0

Z-register

15

7

R31 (0x1F)

ZH

0 7

R30 (0x1E)

ZL

0

0

In the different addressing modes these address registers have functions as fixed displacement, automatic increment, and automatic decrement (see the instruction set reference for details).

The Stack is mainly used for storing temporary data, for storing local variables and for storing return addresses after interrupts and subroutine calls. Note that the Stack is implemented as growing from higher to lower memory locations. The Stack Pointer Register always points to the top of the Stack. The Stack Pointer points to the data SRAM Stack area where the Subroutine and Interrupt Stacks are located. A Stack PUSH command will decrease the Stack Pointer.

The Stack in the data SRAM must be defined by the program before any subroutine calls are executed or interrupts are enabled. Initial Stack Pointer value equals the last address of the

internal SRAM and the Stack Pointer must be set to point above start of the SRAM, see Figure

8-2 on page 21

.

See Table 7-1 for Stack Pointer details.

Table 7-1.

Stack Pointer instructions.

Instruction Stack pointer

PUSH Decremented by 1

Description

Data is pushed onto the stack

CALL

ICALL

RCALL

POP

RET

RETI

Decremented by 2 Return address is pushed onto the stack with a subroutine call or interrupt

Incremented by 1

Incremented by 2

Data is popped from the stack

Return address is popped from the stack with return from subroutine or return from interrupt

The AVR Stack Pointer is implemented as two 8-bit registers in the I/O space. The number of bits actually used is implementation dependent, see

Table 7-2 on page 15

. Note that the data space in some implementations of the AVR architecture is so small that only SPL is needed. In this case, the SPH Register will not be present.

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7.5.1

SPH and SPL – Stack Pointer High and Stack pointer Low

7.5.2

Bit

0x3E (0x5E)

0x3D (0x5D)

Read/Write

Initial Value

15

SP7

7

R

R/W

0

1

14

SP6

6

R

R/W

0

1

13

SP5

5

R

R/W

0

1

12

SP12

SP4

4

R/W

R/W

0/0

(1)

1

11

SP11

SP3

3

R/W

R/W

0/1

(1)

1

10

SP10

SP2

2

R/W

R/W

1/0

(1)

1

9

SP9

SP1

1

R/W

R/W

0

1

8

SP8

SP0

0

R/W

R/W

0

1

SPH

SPL

Note: 1. Initial values respectively for the ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P.

Table 7-2.

Stack Pointer size

Device

ATmega164A/ATmega164PA

ATmega324A/ATmega324PA

ATmega644A/ATmega644PA

ATmega1284/ATmega1284P

RAMPZ – Extended Z-pointer Register for ELPM/SPM

(1)

Stack Pointer size

SP[10:0]

SP[11:0]

SP[12:0]

SP[13:0]

Bit

0x3B (0x5B)

Read/Write

Initial Value

7

RAMPZ7

R/W

0

6

RAMPZ6

R/W

0

5

RAMPZ5

R/W

0

4

RAMPZ4

R/W

0

3

RAMPZ3

R/W

0

2

RAMPZ2

R/W

0

1

RAMPZ1

R/W

0

0

RAMPZ0

R/W

0

RAMPZ

For ELPM/SPM instructions, the Z-pointer is a concatenation of RAMPZ, ZH, and ZL, as shown in Figure 7-4 on page 15 . Note that LPM is not affected by the RAMPZ setting.

Figure 7-4.

The Z-pointer used by ELPM and SPM.

Bit (Individually) 7 0 7

RAMPZ

Bit (Z-pointer) 23 16 15

ZH

0

8

7

7

ZL

0

0

The actual number of bits is implementation dependent. Unused bits in an implementation will always read as zero. For compatibility with future devices, be sure to write these bits to zero.

Note: 1. RAMPZ is only valid for ATmega1284/ATmega1284P.

7.6

Instruction Execution Timing

This section describes the general access timing concepts for instruction execution. The AVR

CPU is driven by the CPU clock clk

CPU

, directly generated from the selected clock source for the chip. No internal clock division is used.

Figure 7-5 on page 16 shows the parallel instruction fetches and instruction executions enabled

by the Harvard architecture and the fast-access Register File concept. This is the basic pipelining concept to obtain up to 1 MIPS per MHz with the corresponding unique results for functions per cost, functions per clocks, and functions per power-unit.

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Figure 7-5.

The Parallel Instruction Fetches and Instruction Executions.

T1 T2 T3 clk

CPU

1st Instruction Fetch

1st Instruction Execute

2nd Instruction Fetch

2nd Instruction Execute

3rd Instruction Fetch

3rd Instruction Execute

4th Instruction Fetch

T4

Figure 7-6 shows the internal timing concept for the Register File. In a single clock cycle an ALU

operation using two register operands is executed, and the result is stored back to the destination register.

Figure 7-6.

Single Cycle ALU operation.

T1 T2 T3 T4 clk

CPU

Total Execution Time

Register Operands Fetch

ALU Operation Execute

Result Write Back

7.7

Reset and interrupt handling

The AVR provides several different interrupt sources. These interrupts and the separate Reset

Vector each have a separate program vector in the program memory space. All interrupts are assigned individual enable bits which must be written logic one together with the Global Interrupt

Enable bit in the Status Register in order to enable the interrupt. Depending on the Program

Counter value, interrupts may be automatically disabled when Boot Lock bits BLB02 or BLB12 are programmed. This feature improves software security. See the section

”Memory programming” on page 297 for details.

The lowest addresses in the program memory space are by default defined as the Reset and

Interrupt Vectors. The complete list of vectors is shown in

”Interrupts” on page 61 . The list also

determines the priority levels of the different interrupts. The lower the address the higher is the priority level. RESET has the highest priority, and next is INT0 – the External Interrupt Request

0. The Interrupt Vectors can be moved to the start of the Boot Flash section by setting the IVSEL bit in the MCU Control Register (MCUCR). Refer to

”Interrupts” on page 61

for more information.

The Reset Vector can also be moved to the start of the Boot Flash section by programming the

BOOTRST Fuse, see ”Memory programming” on page 297

.

When an interrupt occurs, the Global Interrupt Enable I-bit is cleared and all interrupts are disabled. The user software can write logic one to the I-bit to enable nested interrupts. All enabled

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interrupts can then interrupt the current interrupt routine. The I-bit is automatically set when a

Return from Interrupt instruction – RETI – is executed.

There are basically two types of interrupts. The first type is triggered by an event that sets the

Interrupt Flag. For these interrupts, the Program Counter is vectored to the actual Interrupt Vector in order to execute the interrupt handling routine, and hardware clears the corresponding

Interrupt Flag. Interrupt Flags can also be cleared by writing a logic one to the flag bit position(s) to be cleared. If an interrupt condition occurs while the corresponding interrupt enable bit is cleared, the Interrupt Flag will be set and remembered until the interrupt is enabled, or the flag is cleared by software. Similarly, if one or more interrupt conditions occur while the Global Interrupt

Enable bit is cleared, the corresponding Interrupt Flag(s) will be set and remembered until the

Global Interrupt Enable bit is set, and will then be executed by order of priority.

The second type of interrupts will trigger as long as the interrupt condition is present. These interrupts do not necessarily have Interrupt Flags. If the interrupt condition disappears before the interrupt is enabled, the interrupt will not be triggered.

When the AVR exits from an interrupt, it will always return to the main program and execute one more instruction before any pending interrupt is served.

Note that the Status Register is not automatically stored when entering an interrupt routine, nor restored when returning from an interrupt routine. This must be handled by software.

When using the CLI instruction to disable interrupts, the interrupts will be immediately disabled.

No interrupt will be executed after the CLI instruction, even if it occurs simultaneously with the

CLI instruction. The following example shows how this can be used to avoid interrupts during the timed EEPROM write sequence..

Assembly Code Example

in

r16, SREG

; store SREG value

cli

; disable interrupts during timed sequence

sbi

EECR, EEMPE

; start EEPROM write

sbi

EECR, EEPE

out

SREG, r16

; restore SREG value (I-bit)

C Code Example

char

cSREG; cSREG = SREG; /* store SREG value */

/* disable interrupts during timed sequence */

__disable_interrupt();

EECR |= (1<<EEMPE); /* start EEPROM write */

EECR |= (1<<EEPE);

SREG = cSREG; /* restore SREG value (I-bit) */

When using the SEI instruction to enable interrupts, the instruction following SEI will be executed before any pending interrupts, as shown in this example.

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Assembly Code Example

sei

; set Global Interrupt Enable

sleep; enter sleep, waiting for interrupt

; note: will enter sleep before any pending

; interrupt(s)

C Code Example

__enable_interrupt(); /* set Global Interrupt Enable */

__sleep(); /* enter sleep, waiting for interrupt */

/* note: will enter sleep before any pending interrupt(s) */

7.7.1

Interrupt response time

The interrupt execution response for all the enabled AVR interrupts is five clock cycles minimum.

After five clock cycles the program vector address for the actual interrupt handling routine is executed. During these five clock cycle period, the Program Counter is pushed onto the Stack. The vector is normally a jump to the interrupt routine, and this jump takes three clock cycles. If an interrupt occurs during execution of a multi-cycle instruction, this instruction is completed before the interrupt is served. If an interrupt occurs when the MCU is in sleep mode, the interrupt execution response time is increased by five clock cycles. This increase comes in addition to the start-up time from the selected sleep mode.

A return from an interrupt handling routine takes five clock cycles. During these five clock cycles, the Program Counter (three bytes) is popped back from the Stack, the Stack Pointer is incremented by three, and the I-bit in SREG is set.

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8.

AVR memories

8.1

Overview

T h i s s e c t i o n d e s c r i b e s t h e d i f f e r e n t m e m o r i e s i n t h e A t m e l

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P. The AVR architecture has two main memory spaces, the Data Memory and the Program Memory space. In addition, the

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P features an EEPROM Memory for data storage. All three memory spaces are linear and regular.

8.2

In-System Reprogrammable Flash Program Memory

The ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P contains 16/32/64/128Kbytes

On-chip In-System Reprogrammable Flash memory for program storage. Since all AVR instructions are 16 or 32 bits wide, the Flash is organized as 32/64 x 16. For software security, the

Flash Program memory space is divided into two sections, Boot Program section and Application Program section.

The F lash memory has an endurance of at least 10,000 write/erase cycles. The

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P Program Counter (PC) is 15/16 bits wide, thus addressing the 32/64K program memory locations. The operation of Boot Program section and associated Boot Lock bits for software protection are described in detail in

”Memory programming” on page 297 . ”Memory programming” on page 297 contains a detailed

description on Flash data serial downloading using the SPI pins or the JTAG interface.

Constant tables can be allocated within the entire program memory address space (see the LPM

– Load Program Memory instruction description.

Timing diagrams for instruction fetch and execution are presented in

”Instruction Execution Timing” on page 15 .

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Figure 8-1.

Program memory map.

Program Memory

0x0000

Application Flash Section

Boot Flash Section

0x1FFF/0x3FFF/0x7FFF/0xFFFF

8.3

SRAM data memory

Figure 8-2 shows how the ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P SRAM

Memory is organized.

The ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P is a complex microcontroller with more peripheral units than can be supported within the 64 location reserved in the Opcode for the IN and OUT instructions. For the Extended I/O space from $060 - $FF in SRAM, only the

ST/STS/STD and LD/LDS/LDD instructions can be used.

The first 4,352 Data Memory locations address both the Register File, the I/O Memory,

Extended I/O Memory, and the internal data SRAM. The first 32 locations address the Register file, the next 64 location the standard I/O Memory, then 160 locations of Extended I/O memory and the next 4,096 locations address the internal data SRAM.

The five different addressing modes for the data memory cover: Direct, Indirect with Displacement, Indirect, Indirect with Pre-decrement, and Indirect with Post-increment. In the Register file, registers R26 to R31 feature the indirect addressing pointer registers.

The direct addressing reaches the entire data space.

The Indirect with Displacement mode reaches 63 address locations from the base address given by the Y- or Z-register.

When using register indirect addressing modes with automatic pre-decrement and post-increment, the address registers X, Y, and Z are decremented or incremented.

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8.3.1

The 32 general purpose working registers, 64 I/O registers, 160 Extended I/O Registers and t h e 1 0 2 4 / 2 0 4 8 / 4 0 9 6 b y t e s o f i n t e r n a l d a t a S R A M i n t h e A t m e l

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P are all accessible through all these addressing modes. The Register File is described in

”General Purpose Register File” on page

13

.

Figure 8-2.

Data Memory Map for

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P.

Data Memory

32 Registers

64 I/O Registers

160 Ext I/O Reg.

0x0000 - 0x001F

0x0020 - 0x005F

0x0060 - 0x00FF

0x0100

Internal SRAM

(1024/2048/4096/16384x 8)

0x04FF/0x08FF/0x10FF /0x40FF

Data memory access times

This section describes the general access timing concepts for internal memory access. The internal data SRAM access is performed in two clk

CPU

cycles as described in

Figure 8-3

.

Figure 8-3.

On-chip data SRAM access cycles.

T1 T2 T3 clk

CPU

Address

Data

WR

Data

RD

Compute Address

Address valid

Memory Access Instruction

Next Instruction

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8.4

EEPROM data memory

8.4.1

The ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P contains 512/1K/2K/4Kbytes of data EEPROM memory. It is organized as a separate data space, in which single bytes can be read and written. The EEPROM has an endurance of at least 100,000 write/erase cycles.

The access between the EEPROM and the CPU is described in the following, specifying the

EEPROM Address Registers, the EEPROM Data Register, and the EEPROM Control Register.

For a detailed description of SPI, JTAG and Parallel data downloading to the EEPROM, see

page 301

, page 312

,and page 316 respectively.

EEPROM Read/Write Access

8.4.2

The EEPROM Access Registers are accessible in the I/O space. See ”Register Description” on page 24 for details.

The write access time for the EEPROM is given in

Table 8-2 on page 26 . A self-timing function,

however, lets the user software detect when the next byte can be written. If the user code contains instructions that write the EEPROM, some precautions must be taken. In heavily filtered power supplies, V

CC

is likely to rise or fall slowly on power-up/down. This causes the device for some period of time to run at a voltage lower than specified as minimum for the clock frequency

used. See Section “8.4.2” on page 22 for details on how to avoid problems in these situations.

In order to prevent unintentional EEPROM writes, a specific write procedure must be followed.

Refer to the description of the EEPROM Control Register for details on this.

When the EEPROM is read, the CPU is halted for four clock cycles before the next instruction is executed. When the EEPROM is written, the CPU is halted for two clock cycles before the next instruction is executed.

Preventing EEPROM corruption

During periods of low V

CC, the EEPROM data can be corrupted because the supply voltage is too low for the CPU and the EEPROM to operate properly. These issues are the same as for board level systems using EEPROM, and the same design solutions should be applied.

An EEPROM data corruption can be caused by two situations when the voltage is too low. First, a regular write sequence to the EEPROM requires a minimum voltage to operate correctly. Secondly, the CPU itself can execute instructions incorrectly, if the supply voltage is too low.

EEPROM data corruption can easily be avoided by following this design recommendation:

Keep the AVR RESET active (low) during periods of insufficient power supply voltage. This can be done by enabling the internal Brown-out Detector (BOD). If the detection level of the internal

BOD does not match the needed detection level, an external low V

CC

reset Protection circuit can be used. If a reset occurs while a write operation is in progress, the write operation will be completed provided that the power supply voltage is sufficient.

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8.5

I/O memory

The I/O space definition of the Atmel

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P is shown in ”Register summary” on page 553 .

All ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P I/Os and peripherals are placed in the I/O space. All I/O locations may be accessed by the LD/LDS/LDD and ST/STS/STD instructions, transferring data between the 32 general purpose working registers and the I/O space. I/O Registers within the address range 0x00 - 0x1F are directly bit-accessible using the

SBI and CBI instructions. In these registers, the value of single bits can be checked by using the

SBIS and SBIC instructions. Refer to the instruction set section for more details. When using the

I/O specific commands IN and OUT, the I/O addresses 0x00 - 0x3F must be used. When addressing I/O Registers as data space using LD and ST instructions, 0x20 must be added to these addresses. The ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P is a complex microcontroller with more peripheral units than can be supported within the 64 location reserved in Opcode for the IN and OUT instructions. For the Extended I/O space from 0x60 -

0xFF in SRAM, only the ST/STS/STD and LD/LDS/LDD instructions can be used.

For compatibility with future devices, reserved bits should be written to zero if accessed.

Reserved I/O memory addresses should never be written.

Some of the Status Flags are cleared by writing a logical one to them. Note that, unlike most other AVRs, the CBI and SBI instructions will only operate on the specified bit, and can therefore be used on registers containing such Status Flags. The CBI and SBI instructions work with registers 0x00 to 0x1F only.

The I/O and peripherals control registers are explained in later sections.

The ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P contains three General Pur-

pose I/O Registers, see ”Register Description” on page 24

. These registers can be used for storing any information, and they are particularly useful for storing global variables and Status

Flags. General Purpose I/O Registers within the address range 0x00 - 0x1F are directly bitaccessible using the SBI, CBI, SBIS, and SBIC instructions.

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8.6

Register Description

8.6.1

EEARH and EEARL – The EEPROM Address Register

8.6.2

Bit

0x22 (0x42)

0x21 (0x41)

Read/Write

Initial Value

15

EEAR7

7

R

R/W

0

X

14

EEAR6

6

R

R/W

0

X

13

EEAR5

5

R

R/W

0

X

12

EEAR4

4

R

R/W

0

X

11

EEAR11

EEAR3

3

R/W

R/W

X

X

10

EEAR10

EEAR2

2

R/W

R/W

X

X

9

EEAR9

EEAR1

1

R/W

R/W

X

X

8

EEAR8

EEAR0

0

R/W

R/W

X

X

EEARH

EEARL

• Bits 15:12 – Reserved

These bits are reserved bits in the Atmel

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P and will always read as zero.

• Bits 11:0 – EEAR8:0: EEPROM Address

The EEPROM Address Registers – EEARH and EEARL specify the EEPROM address in the

512/1K/2K/4Kbytes EEPROM space. The EEPROM data bytes are addressed linearly between

0 and 511/1023/2047/4096. The initial value of EEAR is undefined. A proper value must be written before the EEPROM may be accessed.

EEDR – The EEPROM Data Register

Bit

0x20 (0x40)

Read/Write

Initial Value

7

MSB

R/W

0

6

R/W

0

5

R/W

0

4

R/W

0

3

R/W

0

2

R/W

0

1

R/W

0

0

LSB

R/W

0

EEDR

• Bits 7:0 – EEDR7:0: EEPROM Data

For the EEPROM write operation, the EEDR Register contains the data to be written to the

EEPROM in the address given by the EEAR Register. For the EEPROM read operation, the

EEDR contains the data read out from the EEPROM at the address given by EEAR.

8.6.3

EECR – The EEPROM Control Register

Bit

0x1F (0x3F)

Read/Write

Initial Value

7

R

0

6

R

0

5

EEPM1

R/W

X

4

EEPM0

R/W

X

3

EERIE

R/W

0

2

EEMPE

R/W

0

1

EEPE

R/W

X

0

EERE

R/W

0

EECR

• Bits 7:6 – Reserved

These bits are reserved bits in the ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P and will always read as zero.

• Bits 5:4 – EEPM1 and EEPM0: EEPROM Programming Mode Bits

The EEPROM Programming mode bit setting defines which programming action that will be triggered when writing EEPE. It is possible to program data in one atomic operation (erase the old value and program the new value) or to split the Erase and Write operations in two different

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operations. The Programming times for the different modes are shown in

Table 8-1 on page 25 .

While EEPE is set, any write to EEPMn will be ignored. During reset, the EEPMn bits will be reset to 0b00 unless the EEPROM is busy programming.

Table 8-1.

EEPROM Mode Bits.

EEPM1 EEPM0

0 0

0 1

1

1

0

1

Programming time

3.4ms

1.8ms

1.8ms

Operation

Erase and Write in one operation (Atomic Operation)

Erase Only

Write Only

Reserved for future use

• Bit 3 – EERIE: EEPROM Ready Interrupt Enable

Writing EERIE to one enables the EEPROM Ready Interrupt if the I bit in SREG is set. Writing

EERIE to zero disables the interrupt. The EEPROM Ready interrupt generates a constant interrupt when EEPE is cleared.

• Bit 2 – EEMPE: EEPROM Master Programming Enable

The EEMPE bit determines whether setting EEPE to one causes the EEPROM to be written.

When EEMPE is set, setting EEPE within four clock cycles will write data to the EEPROM at the selected address If EEMPE is zero, setting EEPE will have no effect. When EEMPE has been written to one by software, hardware clears the bit to zero after four clock cycles. See the description of the EEPE bit for an EEPROM write procedure.

• Bit 1 – EEPE: EEPROM Programming Enable

The EEPROM Write Enable Signal EEPE is the write strobe to the EEPROM. When address and data are correctly set up, the EEPE bit must be written to one to write the value into the

EEPROM. The EEMPE bit must be written to one before a logical one is written to EEPE, otherwise no EEPROM write takes place. The following procedure should be followed when writing the EEPROM (the order of steps 3 and 4 is not essential):

1. Wait until EEPE becomes zero.

2. Wait until SPMEN in SPMCSR becomes zero.

3. Write new EEPROM address to EEAR (optional).

4. Write new EEPROM data to EEDR (optional).

5. Write a logical one to the EEMPE bit while writing a zero to EEPE in EECR.

6. Within four clock cycles after setting EEMPE, write a logical one to EEPE.

The EEPROM can not be programmed during a CPU write to the Flash memory. The software must check that the Flash programming is completed before initiating a new EEPROM write.

Step 2 is only relevant if the software contains a Boot Loader allowing the CPU to program the

Flash. If the Flash is never being updated by the CPU, step 2 can be omitted. See ”Memory programming” on page 297 for details about Boot programming.

Caution:

An interrupt between step 5 and step 6 will make the write cycle fail, since the

EEPROM Master Write Enable will time-out. If an interrupt routine accessing the EEPROM is interrupting another EEPROM access, the EEAR or EEDR Register will be modified, causing the interrupted EEPROM access to fail. It is recommended to have the Global Interrupt Flag cleared during all the steps to avoid these problems.

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When the write access time has elapsed, the EEPE bit is cleared by hardware. The user software can poll this bit and wait for a zero before writing the next byte. When EEPE has been set, the CPU is halted for two cycles before the next instruction is executed.

• Bit 0 – EERE: EEPROM Read Enable

The EEPROM Read Enable Signal EERE is the read strobe to the EEPROM. When the correct address is set up in the EEAR Register, the EERE bit must be written to a logic one to trigger the

EEPROM read. The EEPROM read access takes one instruction, and the requested data is available immediately. When the EEPROM is read, the CPU is halted for four cycles before the next instruction is executed.

The user should poll the EEPE bit before starting the read operation. If a write operation is in progress, it is neither possible to read the EEPROM, nor to change the EEAR Register.

The calibrated Oscillator is used to time the EEPROM accesses. Table 8-2 on page 26

lists the typical programming time for EEPROM access from the CPU.

Table 8-2.

Symbol

EEPROM write

(from CPU)

EEPROM programming time.

Number of calibrated RC oscillator cycles

26,368

Typical programming time

3.3ms

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The following code examples show one assembly and one C function for writing to the

EEPROM. The examples assume that interrupts are controlled (e.g. by disabling interrupts globally) so that no interrupts will occur during execution of these functions. The examples also assume that no Flash Boot Loader is present in the software. If such code is present, the

EEPROM write function must also wait for any ongoing SPM command to finish.

Assembly Code Example

(1)

EEPROM_write:

; Wait for completion of previous write

sbic

EECR,EEPE

rjmp

EEPROM_write

; Set up address (r18:r17) in address register

out

EEARH, r18

out

EEARL, r17

; Write data (r16) to Data Register

out

EEDR,r16

; Write logical one to EEMPE

sbi

EECR,EEMPE

; Start eeprom write by setting EEPE

sbi

EECR,EEPE

ret

C Code Example

(1)

void

EEPROM_write(unsigned int uiAddress, unsigned char ucData)

{

/* Wait for completion of previous write */ while(EECR & (1<<EEPE))

;

/* Set up address and Data Registers */

EEAR = uiAddress;

EEDR = ucData;

/* Write logical one to EEMPE */

EECR |= (1<<EEMPE);

/* Start eeprom write by setting EEPE */

EECR |= (1<<EEPE);

}

Note: 1.

See “About code examples” on page 9

.

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The next code examples show assembly and C functions for reading the EEPROM. The examples assume that interrupts are controlled so that no interrupts will occur during execution of these functions.

Assembly Code Example

(1)

EEPROM_read:

; Wait for completion of previous write

sbic

EECR,EEPE

rjmp

EEPROM_read

; Set up address (r18:r17) in address register

out

EEARH, r18

out

EEARL, r17

; Start eeprom read by writing EERE

sbi

EECR,EERE

; Read data from Data Register

in

r16,EEDR

ret

C Code Example

(1)

unsigned char

EEPROM_read(unsigned int uiAddress)

{

/* Wait for completion of previous write */

while(EECR & (1<<EEPE))

;

/* Set up address register */

EEAR = uiAddress;

/* Start eeprom read by writing EERE */

EECR |= (1<<EERE);

/* Return data from Data Register */

return EEDR;

}

Note: 1.

See “About code examples” on page 9

.

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ATmega164A/PA/324A/PA/644A/PA/1284/P

8.6.4

8.6.5

8.6.6

GPIOR2 – General Purpose I/O Register 2

Bit

0x2B (0x4B)

Read/Write

Initial Value

7

MSB

R/W

0

6

R/W

0

GPIOR1 – General Purpose I/O Register 1

5

R/W

0

4

R/W

0

3

R/W

0

2

R/W

0

1

R/W

0

0

LSB

R/W

0

GPIOR2

Bit

0x2A (0x4A)

Read/Write

Initial Value

7

MSB

R/W

0

6

R/W

0

GPIOR0 – General Purpose I/O Register 0

5

R/W

0

4

R/W

0

3

R/W

0

2

R/W

0

1

R/W

0

0

LSB

R/W

0

GPIOR1

Bit

0x1E (0x3E)

Read/Write

Initial Value

7

MSB

R/W

0

6

R/W

0

5

R/W

0

4

R/W

0

3

R/W

0

2

R/W

0

1

R/W

0

0

LSB

R/W

0

GPIOR0

Note: 1. SRWn1 = SRW11 (upper sector) or SRW01 (lower sector), SRWn0 = SRW10 (upper sector) or

SRW00 (lower sector). The ALE pulse in period T4 is only present if the next instruction accesses the RAM (internal or external).

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9.

System clock and clock options

9.1

Clock systems and their distribution

Figure 9-1

presents the principal clock systems in the AVR and their distribution. All of the clocks need not be active at a given time. In order to reduce power consumption, the clocks to modules

not being used can be halted by using different sleep modes, as described in ”Power management and sleep modes” on page 42

. The clock systems are detailed below.

Figure 9-1.

Clock distribution.

Asynchronous

Timer/Counter

General I/O

Modules

ADC CPU Core RAM

Flash and

EEPROM clk

I/O clk

ASY clk

ADC

AVR Clock

Control Unit clk

CPU clk

FLASH

Reset Logic Watchdog Timer

Source clock

System Clock

Prescaler

Clock

Multiplexer

Watchdog clock

Watchdog

Oscillator

9.1.1

9.1.2

Timer/Counter

Oscillator

External Clock

Crystal

Oscillator

Low-frequency

Crystal Oscillator

Calibrated RC

Oscillator

CPU Clock – clk

CPU

The CPU clock is routed to parts of the system concerned with operation of the AVR core.

Examples of such modules are the General Purpose Register File, the Status Register and the data memory holding the Stack Pointer. Halting the CPU clock inhibits the core from performing general operations and calculations.

I/O Clock – clk

I/O

The I/O clock is used by the majority of the I/O modules, like Timer/Counters, SPI, and USART.

The I/O clock is also used by the External Interrupt module, but note that some external interrupts are detected by asynchronous logic, allowing such interrupts to be detected even if the I/O clock is halted. Also note that start condition detection in the USI module is carried out asynchronously when clk

I/O

is halted, TWI address recognition in all sleep modes.

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9.1.3

9.1.4

9.1.5

Flash Clock – clk

FLASH

The Flash clock controls operation of the Flash interface. The Flash clock is usually active simultaneously with the CPU clock.

Asynchronous Timer Clock – clk

ASY

The Asynchronous Timer clock allows the Asynchronous Timer/Counter to be clocked directly from an external clock or an external 32kHz clock crystal. The dedicated clock domain allows using this Timer/Counter as a real-time counter even when the device is in sleep mode.

ADC Clock – clk

ADC

9.2

Clock Sources

The ADC is provided with a dedicated clock domain. This allows halting the CPU and I/O clocks in order to reduce noise generated by digital circuitry. This gives more accurate ADC conversion results.

9.2.1

9.2.2

The device has the following clock source options, selectable by Flash Fuse bits as shown below. The clock from the selected source is input to the AVR clock generator, and routed to the appropriate modules.

Table 9-1.

Device clocking options select

(1)

.

Device Clocking Option

Low Power Crystal Oscillator

Full Swing Crystal Oscillator

Low Frequency Crystal Oscillator

Internal 128kHz RC Oscillator

Calibrated Internal RC Oscillator

External Clock

Reserved

CKSEL3..0

1111 - 1000

0111 - 0110

0101 - 0100

0011

0010

0000

0001

Note: 1. For all fuses “1” means unprogrammed while “0” means programmed.

Default Clock Source

The device is shipped with internal RC oscillator at 8.0MHz and with the fuse CKDIV8 programmed, resulting in 1.0MHz system clock. The startup time is set to maximum and time-out period enabled. (CKSEL = "0010", SUT = "10", CKDIV8 = "0"). The default setting ensures that all users can make their desired clock source setting using any available programming interface.

Clock Startup Sequence

Any clock source needs a sufficient V

CC

to start oscillating and a minimum number of oscillating cycles before it can be considered stable.

To ensure sufficient V

CC

, the device issues an internal reset with a time-out delay (t

TOUT

) after the device reset is released by all other reset sources.

”On-chip Debug System” on page 46

describes the start conditions for the internal reset. The delay (t

TOUT

) is timed from the Watchdog

Oscillator and the number of cycles in the delay is set by the SUTx and CKSELx fuse bits. The

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9.2.3

selectable delays are shown in

Table 9-2 . The frequency of the Watchdog Oscillator is voltage

dependent as shown in

”Typical characteristics” on page 344 .

Table 9-2.

Number of Watchdog Oscillator Cycles.

Typical time-out (V

CC

= 5.0V)

0ms

4.1ms

65ms

Typical time-out (V

CC

= 3.0V)

0ms

4.3ms

69ms

Number of cycles

0

512

8K (8,192)

Main purpose of the delay is to keep the AVR in reset until it is supplied with minimum Vcc. The delay will not monitor the actual voltage and it will be required to select a delay longer than the

Vcc rise time. If this is not possible, an internal or external Brown-Out Detection circuit should be used. A BOD circuit will ensure sufficient Vcc before it releases the reset, and the time-out delay can be disabled. Disabling the time-out delay without utilizing a Brown-Out Detection circuit is not recommended.

The oscillator is required to oscillate for a minimum number of cycles before the clock is considered stable. An internal ripple counter monitors the oscillator output clock, and keeps the internal reset active for a given number of clock cycles. The reset is then released and the device will start to execute. The recommended oscillator start-up time is dependent on the clock type, and varies from 6 cycles for an externally applied clock to 32K cycles for a low frequency crystal.

The start-up sequence for the clock includes both the time-out delay and the start-up time when the device starts up from reset. When starting up from Power-save or Power-down mode, Vcc is assumed to be at a sufficient level and only the start-up time is included.

Clock source connections

The pins XTAL1 and XTAL2 are input and output, respectively, of an inverting amplifier which can be configured for use as an On-chip Oscillator, as shown in

Figure 9-2 on page 32 . Either a

quartz crystal or a ceramic resonator may be used.

C1 and C2 should always be equal for both crystals and resonators. The optimal value of the capacitors depends on the crystal or resonator in use, the amount of stray capacitance, and the electromagnetic noise of the environment. For ceramic resonators, the capacitor values given by the manufacturer should be used.

Figure 9-2.

Crystal oscillator connections.

C2

XTAL2

C1

XTAL1

GND

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9.3

Low Power Crystal Oscillator

This Crystal Oscillator is a low power oscillator, with reduced voltage swing on the XTAL2 output. It gives the lowest power consumption, but is not capable of driving other clock inputs, and

may be more susceptible to noise in noisy environments. In these cases, refer to the ”Full swing

Crystal Oscillator” on page 34 .

Some initial guidelines for choosing capacitors for use with crystals are given in Table 9-3

. The crystal should be connected as described in

”Clock source connections” on page 32

.

The Low Power Oscillator can operate in three different modes, each optimized for a specific frequency range. The operating mode is selected by the fuses CKSEL3..1 as shown in

Table 9-3

.

Table 9-3.

Low Power Crystal Oscillator Operating Modes

(1)

.

Frequency Range [MHz] CKSEL3..1

(2)

0.4 - 0.9

100

(3)

Recommended Range for Capacitors C1 and C2 [pF]

0.9 - 3.0

101 12 - 22

3.0 - 8.0

8.0 - 16.0

110

111

12 - 22

12 - 22

Notes: 1. If the crystal frequency exceeds the specification of the device (depends on V

CC

), the CKDIV8

Fuse can be programmed in order to divide the internal frequency by 8. It must be ensured that the resulting divided clock meets the frequency specification of the device.

2. This is the recommended CKSEL settings for the different frequency ranges.

3. This option should not be used with crystals, only with ceramic resonators.

The CKSEL0 Fuse together with the SUT1..0 Fuses select the start-up times as shown in

Table

9-4

.

Table 9-4.

Start-up Times for the Low Power Crystal Oscillator Clock Selection.

Start-up time from power-down and power-save

Additional delay from reset

(V

CC

= 5.0V) CKSEL0 SUT1..0

Oscillator source / power conditions

Ceramic resonator, fast rising power

Ceramic resonator, slowly rising power

Ceramic resonator, BOD enabled

Ceramic resonator, fast rising power

Ceramic resonator, slowly rising power

Crystal Oscillator, BOD enabled

Crystal Oscillator, fast rising power

Crystal Oscillator, slowly rising power

258CK

258CK

1K CK

1K CK

1K CK

16K CK

16K CK

16K CK

14CK + 4.1ms

(1)

14CK + 65ms

(1)

14CK

(2)

14CK + 4.1ms

(2)

14CK + 65ms

(2)

14CK

14CK + 4.1ms

14CK + 65ms

0

0

0

0

1

1

1

1

00

01

10

11

00

01

10

11

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Notes: 1. These options should only be used when not operating close to the maximum frequency of the device, and only if frequency stability at start-up is not important for the application. These options are not suitable for crystals.

2. These options are intended for use with ceramic resonators and will ensure frequency stability at start-up. They can also be used with crystals when not operating close to the maximum frequency of the device, and if frequency stability at start-up is not important for the application.

9.4

Full swing Crystal Oscillator

This Crystal Oscillator is a full swing oscillator, with rail-to-rail swing on the XTAL2 output. This is useful for driving other clock inputs and in noisy environments. The current consumption is higher than the

”Low Power Crystal Oscillator” on page 33 . Note that the Full Swing Crystal

Oscillator will only operate for Vcc = 2.7 - 5.5 volts.

Some initial guidelines for choosing capacitors for use with crystals are given in Table 9-6

. The crystal should be connected as described in

”Clock source connections” on page 32

.

The operating mode is selected by the fuses CKSEL3..1 as shown in Table 9-5 .

Table 9-5.

Full Swing Crystal Oscillator Operating Modes.

Frequency range

(1)

[MHz] CKSEL3..1

Recommended Range for Capacitors C1 and C2 [pF]

0.4 - 20 011 12 - 22

Notes: 1. If the crystal frequency exceeds the specification of the device (depends on V

CC

), the CKDIV8

Fuse can be programmed in order to divide the internal frequency by 8. It must be ensured that the resulting divided clock meets the frequency specification of the device.

Table 9-6.

Start-up times for the Full Swing Crystal Oscillator Clock Selection.

Oscillator source / power conditions

Ceramic resonator, fast rising power

Ceramic resonator, slowly rising power

Ceramic resonator,

BOD enabled

Ceramic resonator, fast rising power

Ceramic resonator, slowly rising power

Crystal Oscillator,

BOD enabled

Crystal Oscillator, fast rising power

Crystal Oscillator, slowly rising power

Start-up time from power-down and power-save

258CK

258CK

1K CK

1K CK

1K CK

16K CK

16K CK

16K CK

Additional delay from reset

(V

CC

= 5.0V)

14CK + 4.1ms

(1)

14CK + 65ms

(1)

14CK

(2)

14CK + 4.1ms

(2)

14CK + 65ms

(2)

14CK

14CK + 4.1ms

14CK + 65ms

CKSEL0

0

0

0

0

1

1

1

1

SUT1..0

00

01

10

11

00

01

10

11

Notes: 1. These options should only be used when not operating close to the maximum frequency of the device, and only if frequency stability at start-up is not important for the application. These options are not suitable for crystals.

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2. These options are intended for use with ceramic resonators and will ensure frequency stability at start-up. They can also be used with crystals when not operating close to the maximum frequency of the device, and if frequency stability at start-up is not important for the application.

9.5

Low Frequency Crystal Oscillator

The Low-frequency Crystal Oscillator is optimized for use with a 32.768kHz watch crystal. When selecting crystals, load capasitance and crystal’s Equivalent Series Resistance, ESR must be taken into consideration. Both values are specified by the crystal vendor. Atmel

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P oscillator is optimized for very low power consumption, and thus when selecting crystals, see

Table 9-7 on page 35 for maximum

ESR recommendations on 9pF and 12.5pF crystals.

Table 9-7.

Maximum ESR Recommendation for 32.768kHz Watch Crystal.

Crystal CL [pF] Max ESR [k

Ω]

(1)

9.0

65

12.5

30

Note: 1. Maximum ESR is typical value based on characterization.

The Low-frequency Crystal Oscillator provides an internal load capacitance, see

Table on page

35

at each TOSC pin.

Table 9-8.

Capacitance for Low-frequency oscillator.

Device

ATmega164A/164PA/324A/324PA/

644A/644PA/1284/1284P

32kHz osc. type

System osc.

Timer osc.

Cap (Xtal1/Tosc1)

18pF

6pF

Cap (Xtal2/Tosc2)

8pF

6pF

The capacitance (Ce + Ci) needed at each TOSC pin can be calculated by using:

Ce

+

Ci

= –

C s

where:

Ce - is optional external capacitors as described in

Figure 9-2 on page 32

Ci - is is the pin capacitance in Table 9-8 on page 35

CL - is the load capacitance for a 32.768kHz crystal specified by the crystal vendor.

C

S

- is the total stray capacitance for one TOSC pin.

Crystals specifying load capacitance (CL) higher than the ones given in the

Table 9-8 on page

35

, require external capacitors applied as described in

Figure 9-2 on page 32

.

Figure 9-3.

Crystal oscillator connections.

8272D–AVR–05/12

Crystals specifying load capacitance (CL) higher than listed in

Table 9-8 on page 35 , require

external capacitors applied as described in

Figure 9-2 on page 32

.

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ATmega164A/PA/324A/PA/644A/PA/1284/P

To find suitable load capacitance for a 32.768kHz crysal, please consult the crystal datasheet.

When this oscillator is selected, start-up times are determined by the SUT Fuses and CKSEL0 as shown in

Table 9-9

.

Table 9-9.

Start-up times for the Low Frequency Crystal Oscillator Clock Selection.

Power conditions

BOD enabled

Fast rising power

Slowly rising power

BOD enabled

Fast rising power

Slowly rising power

Start-up time from power-down and power-save

1K CK

1K CK

1K CK

Reserved

32K CK

32K CK

32K CK

Reserved

Additional delay from reset

(V

CC

= 5.0V)

14CK

(1)

14CK + 4.1ms

(1)

14CK + 65ms

(1)

14CK

14CK + 4.1ms

14CK + 65ms

CKSEL0

0

0

0

1

1

0

1

1

SUT1..0

00

01

10

11

00

01

10

11

Note: 1. These options should only be used if frequency stability at start-up is not important for the application.

9.6

Calibrated Internal RC Oscillator

By default, the Internal RC Oscillator provides an approximate 8MHz clock. Though voltage and temperature dependent, this clock can be very accurately calibrated by the the user. See

Table

28-10 on page 336 and

”Internal oscillator speed” on page 389

and

page 441 for more details.

The device is shipped with the CKDIV8 Fuse programmed. See ”System Clock Prescaler” on page 39 for more details.

This clock may be selected as the system clock by programming the CKSEL Fuses as shown in

Table 9-10 . If selected, it will operate with no external components. During reset, hardware loads

the pre-programmed calibration value into the OSCCAL Register and thereby automatically calibrates the RC Oscillator. The accuracy of this calibration is shown as Factory calibration in

Table 28-10 on page 336 .

By changing the OSCCAL register from SW, see ”OSCCAL – Oscillator Calibration Register” on page 40

, it is possible to get a higher calibration accuracy than by using the factory calibration.

The accuracy of this calibration is shown as User calibration in

Table 28-10 on page 336 .

When this Oscillator is used as the chip clock, the Watchdog Oscillator will still be used for the

Watchdog Timer and for the Reset Time-out. For more information on the pre-programmed calibration value, see the section

”Calibration byte” on page 300

.

Table 9-10.

Internal Calibrated RC Oscillator Operating Modes.

Frequency range

(2)

[MHz]

7.3 - 8.1

CKSEL3..0

0010

(1)

Notes: 1. The device is shipped with this option selected.

2. If 8MHz frequency exceeds the specification of the device (depends on V

CC

), the CKDIV8

Fuse can be programmed in order to divide the internal frequency by 8.

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When this Oscillator is selected, start-up times are determined by the SUT Fuses as shown in

Table 9-11 on page 37

.

Table 9-11.

Start-up times for the Internal Calibrated RC Oscillator clock selection.

Power conditions

BOD enabled

Fast rising power

Slowly rising power

Start-up time from powerdown and power-save

6CK

6CK

6CK

Reserved

Additional delay from reset (V

CC

= 5.0V)

14CK

14CK + 4.1ms

14CK + 65ms

SUT1..0

00

01

10

(1)

11

Note: 1.

The device is shipped with this option selected.

9.7

128kHz internal oscillator

The 128kHz internal Oscillator is a low power Oscillator providing a clock of 128kHz. The frequency is nominal at 3V and 25°C. This clock may be select as the system clock by programming the CKSEL Fuses to “0011” as shown in

Table 9-12

.

Table 9-12.

128kHz Internal Oscillator Operating Modes

(2)

.

Nominal frequency

128kHz

CKSEL3..0

0011

Note: 1. Note that the 128kHz oscillator is a very low power clock source, and is not designed for high accuracy.

When this clock source is selected, start-up times are determined by the SUT Fuses as shown in

Table 9-13

.

Table 9-13.

Start-up times for the 128kHz internal oscillator.

Power conditions

BOD enabled

Fast rising power

Slowly rising power

Start-up time from powerdown and power-save

6CK

6CK

6CK

Reserved

Additional delay from reset

14CK

14CK + 4ms

14CK + 64ms

SUT1..0

00

01

10

11

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9.8

External clock

To drive the device from an external clock source, XTAL1 should be driven as shown in Figure

9-4

. To run the device on an external clock, the CKSEL Fuses must be programmed to “0000”.

Figure 9-4.

External clock drive configuration.

NC

EXTERNAL

CLOCK

SIGNAL

XTAL2

XTAL1

GND

When this clock source is selected, start-up times are determined by the SUT Fuses as shown in

Table 9-15

.

Table 9-14.

Crystal oscillator clock frequency.

Nominal frequency

0 - 20MHz

CKSEL3..0

0000

Table 9-15.

Start-up rimes for the external clock selection.

Power conditions

BOD enabled

Fast rising power

Start-up time from powerdown and power-save

6CK

6CK

Additional delay from reset (V

CC

= 5.0V)

14CK

14CK + 4.1ms

Slowly rising power 6CK

Reserved

14CK + 65ms

SUT1..0

00

01

10

11

When applying an external clock, it is required to avoid sudden changes in the applied clock frequency to ensure stable operation of the MCU. A variation in frequency of more than 2% from one clock cycle to the next can lead to unpredictable behavior. If changes of more than 2% is required, ensure that the MCU is kept in Reset during the changes.

Note that the System Clock Prescaler can be used to implement run-time changes of the internal

clock frequency while still ensuring stable operation. Refer to ”System Clock Prescaler” on page

39

for details.

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9.9

Timer/Counter Oscillator

Atmel ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P uses the same type of crystal oscillator for Low-frequency Crystal Oscillator and Timer/Counter Oscillator. See

”Low

Frequency Crystal Oscillator” on page 35 for details on the oscillator and crystal requirements.

The device can operate its Timer/Counter2 from an external 32.768kHz watch crystal or a exter-

nal clock source. See ”Clock source connections” on page 32

for details.

Applying an external clock source to TOSC1 can be done if EXTCLK in the ASSR Register is written to logic one. See

”The Output Compare Register B contains an 8-bit value that is continuously compared with the counter value (TCNT2). A match can be used to generate an Output

Compare interrupt, or to generate a waveform output on the OC2B pin.” on page 160

for further description on selecting external clock as input instead of a 32.768kHz watch crystal.

9.10

Clock Output Buffer

The device can output the system clock on the CLKO pin. To enable the output, the CKOUT

Fuse has to be programmed. This mode is suitable when the chip clock is used to drive other circuits on the system. The clock also will be output during reset, and the normal operation of I/O pin will be overridden when the fuse is programmed. Any clock source, including the internal RC

Oscillator, can be selected when the clock is output on CLKO. If the System Clock Prescaler is used, it is the divided system clock that is output.

9.11

System Clock Prescaler

The ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P has a system clock prescaler, and the system clock can be divided by setting the

”CLKPR – Clock Prescale Register” on page

40

. This feature can be used to decrease the system clock frequency and the power consumption when the requirement for processing power is low. This can be used with all clock source options, and it will affect the clock frequency of the CPU and all synchronous peripherals. clk

I/O

, clk

ADC

, clk

CPU

, and clk

FLASH

are divided by a factor as shown in

Table 9-16 on page 41

.

When switching between prescaler settings, the System Clock Prescaler ensures that no glitches occurs in the clock system. It also ensures that no intermediate frequency is higher than neither the clock frequency corresponding to the previous setting, nor the clock frequency corresponding to the new setting.

The ripple counter that implements the prescaler runs at the frequency of the undivided clock, which may be faster than the CPU's clock frequency. Hence, it is not possible to determine the state of the prescaler - even if it were readable, and the exact time it takes to switch from one clock division to the other cannot be exactly predicted. From the time the CLKPS values are written, it takes between T1 + T2 and T1 + 2 × T2 before the new clock frequency is active. In this interval, 2 active clock edges are produced. Here, T1 is the previous clock period, and T2 is the period corresponding to the new prescaler setting.

To avoid unintentional changes of clock frequency, a special write procedure must be followed to change the CLKPS bits:

1. Write the Clock Prescaler Change Enable (CLKPCE) bit to one and all other bits in

CLKPR to zero.

2. Within four cycles, write the desired value to CLKPS while writing a zero to CLKPCE.

Interrupts must be disabled when changing prescaler setting to make sure the write procedure is not interrupted.

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9.12

Register description

9.12.1

OSCCAL – Oscillator Calibration Register

9.12.2

Bit

(0x66)

Read/Write

Initial Value

7

CAL7

R/W

6

CAL6

R/W

5 4 3 2

CAL5

R/W

CAL4

R/W

CAL3

R/W

Device Specific Calibration Value

CAL2

R/W

1

CAL1

R/W

0

CAL0

R/W

OSCCAL

• Bits 7:0 – CAL7:0: Oscillator Calibration Value

The Oscillator Calibration Register is used to trim the Calibrated Internal RC Oscillator to remove process variations from the oscillator frequency. A pre-programmed calibration value is automatically written to this register during chip reset, giving the Factory calibrated frequency as specified in

Table 28-10 on page 336 . The application software can write this register to change

the oscillator frequency. The oscillator can be calibrated to frequencies as specified in

Table 28-

10 on page 336 . Calibration outside that range is not guaranteed.

Note that this oscillator is used to time EEPROM and Flash write accesses, and these write times will be affected accordingly. If the EEPROM or Flash are written, do not calibrate to more than 8.8MHz. Otherwise, the EEPROM or Flash write may fail.

The CAL7 bit determines the range of operation for the oscillator. Setting this bit to 0 gives the lowest frequency range, setting this bit to 1 gives the highest frequency range. The two frequency ranges are overlapping, in other words a setting of OSCCAL = 0x7F gives a higher frequency than OSCCAL = 0x80.

The CAL6..0 bits are used to tune the frequency within the selected range. A setting of 0x00 gives the lowest frequency in that range, and a setting of 0x7F gives the highest frequency in the range.

CLKPR – Clock Prescale Register

Bit

(0x61)

Read/Write

Initial Value

7

CLKPCE

R/W

0

6

R

0

5

R

0

4

R

0

3

CLKPS3

R/W

2 1

CLKPS2

R/W

CLKPS1

R/W

See Bit Description

0

CLKPS0

R/W

CLKPR

• Bit 7 – CLKPCE: Clock Prescaler Change Enable

The CLKPCE bit must be written to logic one to enable change of the CLKPS bits. The CLKPCE bit is only updated when the other bits in CLKPR are simultaneously written to zero. CLKPCE is cleared by hardware four cycles after it is written or when CLKPS bits are written. Rewriting the

CLKPCE bit within this time-out period does neither extend the time-out period, nor clear the

CLKPCE bit.

• Bits 3:0 – CLKPS3:0: Clock Prescaler Select Bits 3 - 0

These bits define the division factor between the selected clock source and the internal system clock. These bits can be written run-time to vary the clock frequency to suit the application requirements. As the divider divides the master clock input to the MCU, the speed of all synchronous peripherals is reduced when a division factor is used. The division factors are given in

Table 9-16 on page 41

.

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The CKDIV8 Fuse determines the initial value of the CLKPS bits. If CKDIV8 is unprogrammed, the CLKPS bits will be reset to “0000”. If CKDIV8 is programmed, CLKPS bits are reset to

“0011”, giving a division factor of 8 at start up. This feature should be used if the selected clock source has a higher frequency than the maximum frequency of the device at the present operating conditions. Note that any value can be written to the CLKPS bits regardless of the CKDIV8

Fuse setting. The Application software must ensure that a sufficient division factor is chosen if the selected clock source has a higher frequency than the maximum frequency of the device at the present operating conditions. The device is shipped with the CKDIV8 Fuse programmed.

Table 9-16.

Clock prescaler select.

1

1

1

1

1

1

1

1

0

0

CLKPS3

0

0

0

0

0

0

1

1

0

0

1

1

0

0

1

1

CLKPS2

0

0

1

1

0

0

0

0

1

1

1

1

0

0

1

1

CLKPS1

0

0

0

0

1

1

0

1

0

1

0

1

0

1

0

1

CLKPS0

0

1

0

1

0

1

Clock division factor

1

2

16

32

4

8

64

128

256

Reserved

Reserved

Reserved

Reserved

Reserved

Reserved

Reserved

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10. Power management and sleep modes

10.1

Overview

Sleep modes enable the application to shut down unused modules in the MCU, thereby savingpower. The AVR provides various sleep modes allowing the user to tailor the power consumption to the application’s requirements.

When enabled, the Brown-out Detector (BOD) actively monitors the power supply voltage during the sleep periods. To further save power, it is possible to disable the BOD in some sleep modes.

See ”BOD disable(1)” on page 43 for more details.

10.2

Sleep Modes

F i g u r e 9 - 1 o n p a g e 3 0

p r e s e n t s t h e d i f f e r e n t c l o c k s y s t e m s i n t h e A t m e l

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P, and their distribution. The figure is helpful in selecting an appropriate sleep mode.

Table 10-1

shows the different sleep modes, their wake up sources and BOD disable ability.

Table 10-1.

Active Clock Domains and Wake-up Sources in the Different Sleep Modes.

Active Clock Domains Oscillators Wake-up Sources

Sleep Mode

Idle

ADCNRM

Power-down

Power-save

Standby

(1)

Extended

Standby

X X

X

X

X

X

X

(2)

X

X

X

X

X

X

X

X

(2)

(2)

(2)

(2)

X X

X X

X X

X

X

X

X

X X X X

X X X

(2)

X

X

X X X

X

X

X

X

Notes: 1. Only recommended with external crystal or resonator selected as clock source.

2. If Timer/Counter2 is running in asynchronous mode.

X

X

X

X

X

To enter any of the sleep modes, the SE bit in SMCR must be written to logic one and a SLEEP instruction must be executed. The SM2, SM1, and SM0 bits in the SMCR Register select which sleep mode will be activated by the SLEEP instruction. See

Table 10-2 on page 47

for a summary.

If an enabled interrupt occurs while the MCU is in a sleep mode, the MCU wakes up. The MCU is then halted for four cycles in addition to the start-up time, executes the interrupt routine, and resumes execution from the instruction following SLEEP. The contents of the Register File and

SRAM are unaltered when the device wakes up from sleep. If a reset occurs during sleep mode, the MCU wakes up and executes from the Reset Vector.

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10.3

BOD disable

(1)

When the Brown-out Detector (BOD) is enabled by BODLEVEL fuses,

Table 27-3 on page 298 ,

the BOD is actively monitoring the power supply voltage during a sleep period. To save power, it

is possible to disable the BOD by software for some of the sleep modes, see Table 10-1 on page

42

. The sleep mode power consumption will then be at the same level as when BOD is globally disabled by fuses. If BOD is disabled in software, the BOD function is turned off immediately after entering the sleep mode. Upon wake-up from sleep, BOD is automatically enabled again.

This ensures safe operation in case the V

CC

level has dropped during the sleep period.

When the BOD has been disabled, the wake-up time from sleep mode will be approximately 60

µs to ensure that the BOD is working correctly before the MCU continues executing code.

BOD disable is controlled by bit 6, BODS (BOD Sleep) in the control register MCUCR, see

”MCUCR – MCU Control Register” on page 48 . Writing this bit to one turns off the BOD in rele-

vant sleep modes, while a zero in this bit keeps BOD active. Default setting keeps BOD active, that is, BODS set to zero.

Writing to the BODS bit is controlled by a timed sequence and an enable bit, see

”MCUCR –

MCU Control Register” on page 48

.

Note: 1. Only available in the Atmel ATmega164PA/324PA/644PA/1284P.

10.4

Idle mode

When the SM2..0 bits are written to 000, the SLEEP instruction makes the MCU enter Idle mode, stopping the CPU but allowing the SPI, USART, Analog Comparator, ADC, two-wire

Serial Interface, Timer/Counters, Watchdog, and the interrupt system to continue operating. This sleep mode basically halts clk

CPU

and clk

FLASH

, while allowing the other clocks to run.

Idle mode enables the MCU to wake up from external triggered interrupts as well as internal ones like the Timer Overflow and USART Transmit Complete interrupts. If wake-up from the

Analog Comparator interrupt is not required, the Analog Comparator can be powered down by setting the ACD bit in the Analog Comparator Control and Status Register – ACSR. This will reduce power consumption in Idle mode. If the ADC is enabled, a conversion starts automatically when this mode is entered.

10.5

ADC Noise Reduction mode

When the SM2..0 bits are written to 001, the SLEEP instruction makes the MCU enter ADC

Noise Reduction mode, stopping the CPU but allowing the ADC, the external interrupts, two-wire

Serial Interface address match, Timer/Counter2 and the Watchdog to continue operating (if enabled). This sleep mode basically halts clkI/O, clkCPU, and clkFLASH, while allowing the other clocks to run.

This improves the noise environment for the ADC, enabling higher resolution measurements. If the ADC is enabled, a conversion starts automatically when this mode is entered. Apart form the

ADC Conversion Complete interrupt, only an External Reset, a Watchdog System Reset, a

Watchdog interrupt, a Brown-out Reset, a two-wire serial interface interrupt, a Timer/Counter2 interrupt, an SPM/EEPROM ready interrupt, an external level interrupt on INT7:4 or a pin change interrupt can wakeup the MCU from ADC Noise Reduction mode.

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10.6

Power-down mode

When the SM2..0 bits are written to 010, the SLEEP instruction makes the MCU enter Powerdown mode. In this mode, the external Oscillator is stopped, while the external interrupts, the two-wire Serial Interface, and the Watchdog continue operating (if enabled). Only an External

Reset, a Watchdog Reset, a Brown-out Reset, two-wire Serial Interface address match, an external interrupt on INT2:0, or a pin change interrupt can wake up the MCU. This sleep mode basically halts all generated clocks, allowing operation of asynchronous modules only.

Note that if a level triggered interrupt is used for wake-up from Power-down mode, the changed

level must be held for some time to wake up the MCU. Refer to ”External Interrupts” on page 67

for details.

When waking up from Power-down mode, there is a delay from the wake-up condition occurs until the wake-up becomes effective. This allows the clock to restart and become stable after having been stopped. The wake-up period is defined by the same CKSEL Fuses that define the

Reset Time-out period, as described in ”Clock Sources” on page 31 .

10.7

Power-save mode

10.8

Standby mode

When the SM2:0 bits are written to 011, the SLEEP instruction makes the MCU enter Powersave mode. This mode is identical to Power-down, with one exception:

If Timer/Counter2 is enabled, it will keep running during sleep. The device can wake up from either Timer Overflow or Output Compare event from Timer/Counter2 if the corresponding

Timer/Counter2 interrupt enable bits are set in TIMSK2, and the Global Interrupt Enable bit in

SREG is set.

If Timer/Counter2 is not running, Power-down mode is recommended instead of Power-save mode.

The Timer/Counter2 can be clocked both synchronously and asynchronously in Power-save mode. If the Timer/Counter2 is not using the asynchronous clock, the Timer/Counter Oscillator is stopped during sleep. If the Timer/Counter2 is not using the synchronous clock, the clock source is stopped during sleep. Note that even if the synchronous clock is running in Power-save, this clock is only available for the Timer/Counter2.

When the SM2..0 bits are 110 and an external crystal/resonator clock option is selected, the

SLEEP instruction makes the MCU enter Standby mode. This mode is identical to Power-down with the exception that the Oscillator is kept running. From Standby mode, the device wakes up in six clock cycles.

10.9

Extended Standby mode

When the SM2..0 bits are 111 and an external crystal/resonator clock option is selected, the

SLEEP instruction makes the MCU enter Extended Standby mode. This mode is identical to

Power-save mode with the exception that the Oscillator is kept running. From Extended Standby mode, the device wakes up in six clock cycles.

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10.10 Power Reduction Register

The Power Reduction Register(PRR), see ”PRR0 – Power Reduction Register 0” on page 48 ,

provides a method to stop the clock to individual peripherals to reduce power consumption. The current state of the peripheral is frozen and the I/O registers can not be read or written.

Resources used by the peripheral when stopping the clock will remain occupied, hence the peripheral should in most cases be disabled before stopping the clock. Waking up a peripheral, which is done by clearing the bit in PRR, puts the peripheral in the same state as before shutdown.

Peripheral shutdown can be used in Idle mode and Active mode to significantly reduce the overall power consumption. In all other sleep modes, the clock is already stopped.

10.11 Minimizing Power Consumption

There are several issues to consider when trying to minimize the power consumption in an AVR controlled system. In general, sleep modes should be used as much as possible, and the sleep mode should be selected so that as few as possible of the device’s functions are operating. All functions not needed should be disabled. In particular, the following modules may need special consideration when trying to achieve the lowest possible power consumption.

10.11.1

Analog to Digital Converter

If enabled, the ADC will be enabled in all sleep modes. To save power, the ADC should be disabled before entering any sleep mode. When the ADC is turned off and on again, the next

conversion will be an extended conversion. Refer to ”ADC - Analog-to-digital converter” on page

243 for details on ADC operation.

10.11.2

Analog Comparator

When entering Idle mode, the Analog Comparator should be disabled if not used. When entering

ADC Noise Reduction mode, the Analog Comparator should be disabled. In other sleep modes, the Analog Comparator is automatically disabled. However, if the Analog Comparator is set up to use the Internal Voltage Reference as input, the Analog Comparator should be disabled in all sleep modes. Otherwise, the Internal Voltage Reference will be enabled, independent of sleep mode. Refer to

”AC - Analog Comparator” on page 240 for details on how to configure the Ana-

log Comparator.

10.11.3

Brown-out Detector

If the Brown-out Detector is not needed by the application, this module should be turned off. If the Brown-out Detector is enabled by the BODLEVEL Fuses, it will be enabled in all sleep modes, and hence, always consume power. In the deeper sleep modes, this will contribute sig-

nificantly to the total current consumption. Refer to ”Brown-out Detection” on page 53 for details

on how to configure the Brown-out Detector.

10.11.4

Internal Voltage Reference

The Internal Voltage Reference will be enabled when needed by the Brown-out Detection, the

Analog Comparator or the ADC. If these modules are disabled as described in the sections above, the internal voltage reference will be disabled and it will not be consuming power. When turned on again, the user must allow the reference to start up before the output is used. If the reference is kept on in sleep mode, the output can be used immediately. Refer to

”Internal Voltage Reference” on page 54

for details on the start-up time.

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10.11.5

Watchdog Timer

If the Watchdog Timer is not needed in the application, the module should be turned off. If the

Watchdog Timer is enabled, it will be enabled in all sleep modes, and hence, always consume power. In the deeper sleep modes, this will contribute significantly to the total current consump-

tion. Refer to ”Watchdog Timer” on page 55 for details on how to configure the Watchdog Timer.

10.11.6

Port Pins

When entering a sleep mode, all port pins should be configured to use minimum power. The most important is then to ensure that no pins drive resistive loads. In sleep modes where both the I/O clock (clk

I/O

) and the ADC clock (clk

ADC

) are stopped, the input buffers of the device will be disabled. This ensures that no power is consumed by the input logic when not needed. In some cases, the input logic is needed for detecting wake-up conditions, and it will then be

enabled. Refer to the section ”Digital Input Enable and Sleep Modes” on page 76

for details on which pins are enabled. If the input buffer is enabled and the input signal is left floating or have an analog signal level close to V

CC

/2, the input buffer will use excessive power.

For analog input pins, the digital input buffer should be disabled at all times. An analog signal level close to V

CC

/2 on an input pin can cause significant current even in active mode. Digital input buffers can be disabled by writing to the Digital Input Disable Registers (DIDR1 and

DIDR0). Refer to

”DIDR1 – Digital Input Disable Register 1” on page 242

and

”DIDR0 – Digital

Input Disable Register 0” on page 262

for details.

10.11.7

On-chip Debug System

If the On-chip debug system is enabled by the OCDEN Fuse and the chip enters sleep mode, the main clock source is enabled, and hence, always consumes power. In the deeper sleep modes, this will contribute significantly to the total current consumption.

There are three alternative ways to disable the OCD system:

• Disable the OCDEN Fuse

• Disable the JTAGEN Fuse

• Write one to the JTD bit in MCUCR

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10.12 Register description

10.12.1

SMCR – Sleep Mode Control Register

The Sleep Mode Control Register contains control bits for power management.

Bit

0x33 (0x53)

Read/Write

Initial Value

7

R

0

6

R

0

5

R

0

4

R

0

3

SM2

R/W

0

2

SM1

R/W

0

1

SM0

R/W

0

0

SE

R/W

0

SMCR

• Bits 3, 2, 1 – SM2:0: Sleep Mode Select Bits 2, 1, and 0

These bits select between the five available sleep modes as shown in Table 10-2 .

Table 10-2.

Sleep mode select.

1

1

0

0

SM2

0

0

1

1

0

0

1

1

SM1

0

0

1

1

SM0

0

1

0

1

0

1

0

1

Sleep mode

Idle

ADC Noise Reduction

Power-down

Power-save

Reserved

Reserved

Standby

(1)

Extended Standby

(1)

Note: 1. Standby modes are only recommended for use with external crystals or resonators.

• Bit 0 – SE: Sleep Enable

The SE bit must be written to logic one to make the MCU enter the sleep mode when the SLEEP instruction is executed. To avoid the MCU entering the sleep mode unless it is the programmer’s purpose, it is recommended to write the Sleep Enable (SE) bit to one just before the execution of the SLEEP instruction and to clear it immediately after waking up.

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10.12.2

MCUCR – MCU Control Register

Bit

0x35 (0x55)

Read/Write

Initial Value

7

JTD

R/W

0

6

BODS

(1)

R/W

0

5

BODSE

(1)

R/W

0

4

PUD

R/W

0

R

0

3

R

0

2

Note: 1. Only available in the Atmel ATmega164PA/324PA/644PA/1284P.

1

IVSEL

R/W

0

0

IVCE

R/W

0

MCUCR

• Bit 6 – BODS: BOD Sleep

The BODS bit must be written to logic one in order to turn off BOD during sleep, see Table 10-1 on page 42 . Writing to the BODS bit is controlled by a timed sequence and an enable bit,

BODSE in MCUCR. To disable BOD in relevant sleep modes, both BODS and BODSE must first be set to one. Then, to set the BODS bit, BODS must be set to one and BODSE must be set to zero within four clock cycles.

The BODS bit is active three clock cycles after it is set. A sleep instruction must be executed while BODS is active in order to turn off the BOD for the actual sleep mode. The BODS bit is automatically cleared after three clock cycles.

• Bit 5 – BODSE: BOD Sleep Enable

BODSE enables setting of BODS control bit, as explained in BODS bit description. BOD disable is controlled by a timed sequence.

10.12.3

PRR0 – Power Reduction Register 0

Bit

(0x64)

Read/Write

Initial Value

7

PRTWI

R/W

0

6

PRTIM2

R/W

0

5

PRTIM0

R/W

0

4

PRUSART1

R/W

0

3

PRTIM1

R/W

0

2

PRSPI

R/W

0

1

PRUSART0

R/W

0

0

PRADC

R/W

0

PRR0

• Bit 7 – PRTWI: Power Reduction TWI

Writing a logic one to this bit shuts down the TWI by stopping the clock to the module. When waking up the TWI again, the TWI should be re initialized to ensure proper operation.

• Bit 6 – PRTIM2: Power Reduction Timer/Counter2

Writing a logic one to this bit shuts down the Timer/Counter2 module in synchronous mode (AS2 is 0). When the Timer/Counter2 is enabled, operation will continue like before the shutdown.

• Bit 5 – PRTIM0: Power Reduction Timer/Counter0

Writing a logic one to this bit shuts down the Timer/Counter0 module. When the Timer/Counter0 is enabled, operation will continue like before the shutdown.

• Bit 4 – PRUSART1: Power Reduction USART1

Writing a logic one to this bit shuts down the USART1 by stopping the clock to the module.

When waking up the USART1 again, the USART1 should be reinitialized to ensure proper operation.

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• Bit 3 – PRTIM1: Power Reduction Timer/Counter1

Writing a logic one to this bit shuts down the Timer/Counter1 module. When the Timer/Counter1 is enabled, operation will continue like before the shutdown.

• Bit 2 – PRSPI: Power Reduction Serial Peripheral Interface

Writing a logic one to this bit shuts down the Serial Peripheral Interface by stopping the clock to the module. When waking up the SPI again, the SPI should be re initialized to ensure proper operation.

• Bit 1 – PRUSART0: Power Reduction USART0

Writing a logic one to this bit shuts down the USART0 by stopping the clock to the module.

When waking up the USART0 again, the USART0 should be reinitialized to ensure proper operation.

• Bit 0 – PRADC: Power Reduction ADC

Writing a logic one to this bit shuts down the ADC. The ADC must be disabled before shut down.

The analog comparator cannot use the ADC input MUX when the ADC is shut down.

10.12.4

PRR1 – Power Reduction Register 1

Bit

(0x65)

Read/Write

Initial Value

7

R

0

6

R

0

5

R

0

4

R

0

3

R

0

2

R

0

1

R

0

0

PRTIM3

R/W

0

PRR1

• Bit 7:1 – Reserved

• Bit 0 – PRTIM3: Power Reduction Timer/Counter3

Writing a logic one to this bit shuts down the Timer/Counter3 module. When the Timer/Counter3 is enabled, operation will continue like before the shutdown.

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11. System Control and Reset

11.1

Resetting the AVR

11.1.1

Reset Sources

During reset, all I/O Registers are set to their initial values, and the program starts execution from the Reset Vector. The instruction placed at the Reset Vector must be a JMP – Absolute

Jump – instruction to the reset handling routine. If the program never enables an interrupt source, the Interrupt Vectors are not used, and regular program code can be placed at these locations. This is also the case if the Reset Vector is in the Application section while the Interrupt

Vectors are in the Boot section or vice versa. The circuit diagram in

Figure 11-1 on page 51

shows the reset logic.

”” on page 336

defines the electrical parameters of the reset circuitry.

The I/O ports of the AVR are immediately reset to their initial state when a reset source goes active. This does not require any clock source to be running.

After all reset sources have gone inactive, a delay counter is invoked, stretching the internal reset. This allows the power to reach a stable level before normal operation starts. The time-out period of the delay counter is defined by the user through the SUT and CKSEL Fuses. The different selections for the delay period are presented in

”Clock Sources” on page 31 .

The Atmel ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P has five sources of reset:

• Power-on Reset. The MCU is reset when the supply voltage is below the Power-on Reset threshold (V

POT

).

• External Reset. The MCU is reset when a low level is present on the RESET pin for longer than the minimum pulse length.

• Watchdog Reset. The MCU is reset when the Watchdog Timer period expires and the

Watchdog is enabled.

• Brown-out Reset. The MCU is reset when the supply voltage V

CC

is below the Brown-out Reset threshold (V

BOT

) and the Brown-out Detector is enabled.

• JTAG AVR Reset. The MCU is reset as long as there is a logic one in the Reset Register, one of the scan chains of the JTAG system. Refer to the section

”IEEE 1149.1 (JTAG) Boundaryscan” on page 269 for details.

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Figure 11-1.

Reset logic.

DATA BUS

BODLEVEL [2..0]

Pull-up Resistor

SPIKE

FILTER

Power-on Reset

Circuit

Brown-out

Reset Circuit

JTAG Reset

Register

Watchdog

Oscillator

Clock

Generator

CK

CKSEL[3:0]

SUT[1:0]

MCU Status

Register (MCUSR)

Delay Counters

TIMEOUT

11.1.2

Power-on Reset

A Power-on Reset (POR) pulse is generated by an On-chip detection circuit. The detection level

is defined in ”” on page 336 . The POR is activated whenever V

CC

is below the detection level.

The POR circuit can be used to trigger the start-up Reset, as well as to detect a failure in supply voltage.

A Power-on Reset (POR) circuit ensures that the device is reset from Power-on. Reaching the

Power-on Reset threshold voltage invokes the delay counter, which determines how long the device is kept in RESET after V

CC

rise. The RESET signal is activated again, without any delay, when V

CC

decreases below the detection level.

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Figure 11-2.

MCU Start-up, RESET Tied to V

CC

.

V

POT

V

CC

V

RST

RESET

TIME-OUT t

TOUT

INTERNAL

RESET

Figure 11-3.

MCU Start-up, RESET Extended Externally.

V

POT

V

CC

V

RST

RESET t

TOUT

TIME-OUT

INTERNAL

RESET

11.1.3

External Reset

An External Reset is generated by a low level on the RESET pin. Reset pulses longer than the

minimum pulse width (see ”” on page 336

) will generate a reset, even if the clock is not running.

Shorter pulses are not guaranteed to generate a reset. When the applied signal reaches the

Reset Threshold Voltage – V

RST

– on its positive edge, the delay counter starts the MCU after the Time-out period – t

TOUT

– has expired.

Figure 11-4.

External Reset During Operation

CC

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11.1.4

Brown-out Detection

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P has an On-chip Brown-out Detection (BOD) circuit for monitoring the V

CC

level during operation by comparing it to a fixed trigger level. The trigger level for the BOD can be selected by the BODLEVEL Fuses. The trigger level has a hysteresis to ensure spike free Brown-out Detection. The hysteresis on the detection level should be interpreted as V

BOT+

= V

BOT

+ V

HYST

/2 and V

BOT-

= V

BOT

- V

HYST

/2.

When the BOD is enabled, and V

CC

decreases to a value below the trigger level (V

BOT-

in

Figure

11-5 on page 53

), the Brown-out Reset is immediately activated. When V

CC

increases above the trigger level (V

BOT+

in

Figure 11-5 on page 53 ), the delay counter starts the MCU after the Time-

out period t

TOUT

has expired.

The BOD circuit will only detect a drop in V

CC

if the voltage stays below the trigger level for longer than t

BOD

given in

”” on page 336

.

Figure 11-5.

Brown-out Reset during operation.

V

CC

V

BOT-

V

BOT+

RESET

TIME-OUT t

TOUT

11.1.5

INTERNAL

RESET

Watchdog Reset

When the Watchdog times out, it will generate a short reset pulse of one CK cycle duration. On the falling edge of this pulse, the delay timer starts counting the Time-out period t

TOUT

. Refer to

”Watchdog Timer” on page 55 for details on operation of the Watchdog Timer.

Figure 11-6.

Watchdog Reset during operation.

CC

CK

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11.2

Internal Voltage Reference

11.2.1

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P features an internal bandgap reference. This reference is used for Brown-out Detection, and it can be used as an input to the

Analog Comparator or the ADC.

Voltage Reference Enable Signals and Start-up Time

The voltage reference has a start-up time that may influence the way it should be used. The start-up time is given in

”” on page 336

. To save power, the reference is not always turned on.

The reference is on during the following situations:

1. When the BOD is enabled (by programming the BODLEVEL [2:0] Fuse).

2. When the bandgap reference is connected to the Analog Comparator (by setting the

ACBG bit in ACSR).

3. When the ADC is enabled.

Thus, when the BOD is not enabled, after setting the ACBG bit or enabling the ADC, the user must always allow the reference to start up before the output from the Analog Comparator or

ADC is used. To reduce power consumption in Power-down mode, the user can avoid the three conditions above to ensure that the reference is turned off before entering Power-down mode.

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11.3

Watchdog Timer

11.3.1

Features

Clocked from separate On-chip Oscillator

Three operating modes

– Interrupt

– System Reset

– Interrupt and System Reset

Selectable Time-out period from 16ms to 8s

Possible Hardware fuse Watchdog always on (WDTON) for fail-safe mode

11.3.2

Overview

Atmel ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P has an Enhanced Watchdog Timer (WDT). The WDT is a timer counting cycles of a separate on-chip 128kHz oscillator.

The WDT gives an interrupt or a system reset when the counter reaches a given time-out value.

In normal operation mode, it is required that the system uses the WDR - Watchdog Timer Reset

- instruction to restart the counter before the time-out value is reached. If the system doesn't restart the counter, an interrupt or system reset will be issued.

Figure 11-7.

Watchdog Timer.

128kHz

OSCILLATOR

WATCHDOG

RESET

WDE

WDP0

WDP1

WDP2

WDP3

MCU RESET

WDIF

WDIE

INTERRUPT

In Interrupt mode, the WDT gives an interrupt when the timer expires. This interrupt can be used to wake the device from sleep-modes, and also as a general system timer. One example is to limit the maximum time allowed for certain operations, giving an interrupt when the operation has run longer than expected. In System Reset mode, the WDT gives a reset when the timer expires. This is typically used to prevent system hang-up in case of runaway code. The third mode, Interrupt and System Reset mode, combines the other two modes by first giving an interrupt and then switch to System Reset mode. This mode will for instance allow a safe shutdown by saving critical parameters before a system reset.

The Watchdog always on (WDTON) fuse, if programmed, will force the Watchdog Timer to System Reset mode. With the fuse programmed the System Reset mode bit (WDE) and Interrupt mode bit (WDIE) are locked to 1 and 0 respectively. To further ensure program security, alterations to the Watchdog set-up must follow timed sequences. The sequence for clearing WDE and changing time-out configuration is as follows:

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1. In the same operation, write a logic one to the Watchdog change enable bit (WDCE) and

WDE. A logic one must be written to WDE regardless of the previous value of the WDE bit.

2. Within the next four clock cycles, write the WDE and Watchdog prescaler bits (WDP) as desired, but with the WDCE bit cleared. This must be done in one operation.

The following code example shows one assembly and one C function for turning off the Watchdog Timer. The example assumes that interrupts are controlled (for example, by disabling interrupts globally) so that no interrupts will occur during the execution of these functions.

Assembly Code Example

(1)

WDT_off:

; Turn off global interrupt

cli

; Reset Watchdog Timer

wdr

; Clear WDRF in MCUSR

in

r16, MCUSR

andi

r16, ~(1<<WDRF)

out

MCUSR, r16

; Write logical one to WDCE and WDE

; Keep old prescaler setting to prevent unintentional time-out

in

r16, WDTCSR

ori

r16, (1<<WDCE) | (1<<WDE)

out

WDTCSR, r16

; Turn off WDT

ldi

r16, (0<<WDE)

out

WDTCSR, r16

; Turn on global interrupt

sei ret

C Code Example

(1)

void WDT_off(void)

{

__disable_interrupt();

__watchdog_reset();

/* Clear WDRF in MCUSR */

MCUSR &= ~(1<<WDRF);

/* Write logical one to WDCE and WDE */

/* Keep old prescaler setting to prevent unintentional time-out */

WDTCSR |= (1<<WDCE) | (1<<WDE);

/* Turn off WDT */

WDTCSR = 0x00;

__enable_interrupt();

}

Note: 1. The example code assumes that the part specific header file is included.

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Note: If the Watchdog is accidentally enabled, for example by a runaway pointer or brown-out condition, the device will be reset and the Watchdog Timer will stay enabled. If the code is not set up to handle the Watchdog, this might lead to an eternal loop of time-out resets. To avoid this situation, the application software should always clear the Watchdog System Reset Flag

(WDRF) and the WDE control bit in the initialisation routine, even if the Watchdog is not in use.

The following code example shows one assembly and one C function for changing the time-out value of the Watchdog Timer.

Assembly Code Example

(1)

WDT_Prescaler_Change:

; Turn off global interrupt

cli

; Reset Watchdog Timer

wdr

; Start timed sequence

in

r16, WDTCSR

ori

r16, (1<<WDCE) | (1<<WDE)

out

WDTCSR, r16

; -- Got four cycles to set the new values from here -

; Set new prescaler(time-out) value = 64K cycles (~0.5 s)

ldi

r16, (1<<WDE) | (1<<WDP2) | (1<<WDP0)

out

WDTCSR, r16

; -- Finished setting new values, used 2 cycles -

; Turn on global interrupt

sei ret

C Code Example

(1)

void WDT_Prescaler_Change(void)

{

__disable_interrupt();

__watchdog_reset();

/* Start timed equence */

WDTCSR |= (1<<WDCE) | (1<<WDE);

/* Set new prescaler(time-out) value = 64K cycles (~0.5 s) */

WDTCSR = (1<<WDE) | (1<<WDP2) | (1<<WDP0);

__enable_interrupt();

}

Note: 1. The example code assumes that the part specific header file is included.

Note: The Watchdog Timer should be reset before any change of the WDP bits, since a change in the WDP bits can result in a time-out when switching to a shorter time-out period.

57

ATmega164A/PA/324A/PA/644A/PA/1284/P

11.4

Register description

11.4.1

MCUSR – MCU Status Register

The MCU Status Register provides information on which reset source caused an MCU reset.

Bit

0x34 (0x54)

Read/Write

Initial Value

7

R

0

6

R

0

5

R

0

4

JTRF

R/W

3 2 1

WDRF

R/W

BORF

R/W

See Bit Description

EXTRF

R/W

0

PORF

R/W

MCUSR

• Bit 4 – JTRF: JTAG Reset Flag

This bit is set if a reset is being caused by a logic one in the JTAG Reset Register selected by the JTAG instruction AVR_RESET. This bit is reset by a Power-on Reset, or by writing a logic zero to the flag.

• Bit 3 – WDRF: Watchdog Reset Flag

This bit is set if a Watchdog Reset occurs. The bit is reset by a Power-on Reset, or by writing a logic zero to the flag.

• Bit 2 – BORF: Brown-out Reset Flag

This bit is set if a Brown-out Reset occurs. The bit is reset by a Power-on Reset, or by writing a logic zero to the flag.

• Bit 1 – EXTRF: External Reset Flag

This bit is set if an External Reset occurs. The bit is reset by a Power-on Reset, or by writing a logic zero to the flag.

• Bit 0 – PORF: Power-on Reset Flag

This bit is set if a Power-on Reset occurs. The bit is reset only by writing a logic zero to the flag.

To make use of the Reset Flags to identify a reset condition, the user should read and then

Reset the MCUSR as early as possible in the program. If the register is cleared before another reset occurs, the source of the reset can be found by examining the Reset Flags.

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11.4.2

WDTCSR – Watchdog Timer Control Register

Bit

(0x60)

Read/Write

Initial Value

7

WDIF

R/W

0

6

WDIE

R/W

0

5

WDP3

R/W

0

4

WDCE

R/W

0

3

WDE

R/W

X

2

WDP2

R/W

0

1

WDP1

R/W

0

0

WDP0

R/W

0

WDTCSR

• Bit 7 - WDIF: Watchdog Interrupt Flag

This bit is set when a time-out occurs in the Watchdog Timer and the Watchdog Timer is configured for interrupt. WDIF is cleared by hardware when executing the corresponding interrupt handling vector. Alternatively, WDIF is cleared by writing a logic one to the flag. When the I-bit in

SREG and WDIE are set, the Watchdog Time-out Interrupt is executed.

• Bit 6 - WDIE: Watchdog Interrupt Enable

When this bit is written to one and the I-bit in the Status Register is set, the Watchdog Interrupt is enabled. If WDE is cleared in combination with this setting, the Watchdog Timer is in Interrupt

Mode, and the corresponding interrupt is executed if time-out in the Watchdog Timer occurs.

If WDE is set, the Watchdog Timer is in Interrupt and System Reset Mode. The first time-out in the Watchdog Timer will set WDIF. Executing the corresponding interrupt vector will clear WDIE and WDIF automatically by hardware (the Watchdog goes to System Reset Mode). This is useful for keeping the Watchdog Timer security while using the interrupt. To stay in Interrupt and

System Reset Mode, WDIE must be set after each interrupt. This should however not be done within the interrupt service routine itself, as this might compromise the safety-function of the

Watchdog System Reset mode. If the interrupt is not executed before the next time-out, a System Reset will be applied.

Table 11-1.

Watchdog Timer configuration.

WDTON

1

1

1

1

0

WDE

0

0

1

1 x

WDIE

0

1

0

1 x

Mode

Stopped

Interrupt Mode

System Reset Mode

Interrupt and System Reset

Mode

System Reset Mode

Action on time-out

None

Interrupt

Reset

Interrupt, then go to System

Reset Mode

Reset

• Bit 4 - WDCE: Watchdog Change Enable

This bit is used in timed sequences for changing WDE and prescaler bits. To clear the WDE bit, and/or change the prescaler bits, WDCE must be set.

Once written to one, hardware will clear WDCE after four clock cycles.

• Bit 3 - WDE: Watchdog System Reset Enable

WDE is overridden by WDRF in MCUSR. This means that WDE is always set when WDRF is set. To clear WDE, WDRF must be cleared first. This feature ensures multiple resets during conditions causing failure, and a safe start-up after the failure.

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.

• Bit 5, 2:0 - WDP3:0: Watchdog Timer Prescaler 3, 2, 1 and 0

The WDP3:0 bits determine the Watchdog Timer prescaling when the Watchdog Timer is running. The different prescaling values and their corresponding time-out periods are shown in

Table 11-2 on page 60

.

Table 11-2.

Watchdog Timer Prescale Select.

1

1

1

1

1

1

1

0

1

0

0

0

0

WDP3 WDP2 WDP1 WDP0

0 0 0 0

0

0

0

0

0

1

1

0

0

1

1

1

1

0

0

1

1

0

1

0

1

0

0

0

0

1

1

1

1

1

0

0

1

1

0

0

1

1

1

0

1

0

1

1

0

1

0

Number of WDT oscillator cycles

2K (2048) cycles

4K (4096) cycles

8K (8192) cycles

16K (16384) cycles

32K (32768) cycles

64K (65536) cycles

128K (131072) cycles

256K (262144) cycles

512K (524288) cycles

1024K (1048576) cycles

Reserved

Typical time-out at

V

CC

= 5.0V

16ms

32ms

64ms

0.125s

0.25s

0.5s

1.0s

2.0s

4.0s

8.0s

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ATmega164A/PA/324A/PA/644A/PA/1284/P

12. Interrupts

12.1

Overview

This section describes the specifics of the interrupt handling as performed in Atmel

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P. For a general explanation of the

AVR interrupt handling, refer to ”Reset and interrupt handling” on page 16 .

12.2

Interrupt Vectors in ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P

Table 12-1.

Reset and Interrupt Vectors.

Vector no.

Program address

(2)

Source

1 $0000

(1)

RESET

14

15

16

17

10

11

12

13

8

9

6

7

4

5

2

3

22

23

24

25

18

19

20

21

26

27

$0012

$0014

$0016

$0018

$001A

$001C

$001E

$0020

$0002

$0004

$0006

$0008

$000A

$000C

$000E

$0010

$0022

$0024

$0026

$0028

$002A

$002C

$002E

$0030

$0032

$0034

INT0

INT1

INT2

PCINT0

PCINT1

PCINT2

PCINT3

WDT

TIMER2_COMPA

TIMER2_COMPB

TIMER2_OVF

TIMER1_CAPT

TIMER1_COMPA

TIMER1_COMPB

TIMER1_OVF

TIMER0_COMPA

TIMER0_COMPB

TIMER0_OVF

SPI_STC

USART0_RX

USART0_UDRE

USART0_TX

ANALOG_COMP

ADC

EE_READY

TWI

Interrupt definition

External Pin, Power-on Reset, Brown-out Reset,

Watchdog Reset, and JTAG AVR Reset

External Interrupt Request 0

External Interrupt Request 1

External Interrupt Request 2

Pin Change Interrupt Request 0

Pin Change Interrupt Request 1

Pin Change Interrupt Request 2

Pin Change Interrupt Request 3

Watchdog Time-out Interrupt

Timer/Counter2 Compare Match A

Timer/Counter2 Compare Match B

Timer/Counter2 Overflow

Timer/Counter1 Capture Event

Timer/Counter1 Compare Match A

Timer/Counter1 Compare Match B

Timer/Counter1 Overflow

Timer/Counter0 Compare Match A

Timer/Counter0 Compare match B

Timer/Counter0 Overflow

SPI Serial Transfer Complete

USART0 Rx Complete

USART0 Data Register Empty

USART0 Tx Complete

Analog Comparator

ADC Conversion Complete

EEPROM Ready two-wire Serial Interface

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Table 12-1.

Reset and Interrupt Vectors. (Continued)

Vector no.

28

29

30

31

32

33

34

35

Program address

(2)

$0036

$0038

$003A

$003C

$003E

$0040

$0042

$0044

Source

SPM_READY

USART1_RX

USART1_UDRE

USART1_TX

TIMER3_CAPT

(3)

TIMER3_COMPA

(3)

TIMER3_COMPB

(3)

TIMER3_OVF

(3)

Interrupt definition

Store Program Memory Ready

USART1 Rx Complete

USART1 Data Register Empty

USART1 Tx Complete

Timer/Counter3 Capture Event

Timer/Counter3 Compare Match A

Timer/Counter3 Compare Match B

Timer/Counter3 Overflow

Notes: 1. When the BOOTRST Fuse is programmed, the device will jump to the Boot Loader address at

reset, see ”Memory programming” on page 297

.

2. When the IVSEL bit in MCUCR is set, Interrupt Vectors will be moved to the start of the Boot

Flash Section. The address of each Interrupt Vector will then be the address in this table added to the start address of the Boot Flash Section.

3. Applies only to Atmel ATmega1284P.

Table 12-2

shows reset and Interrupt Vectors placement for the various combinations of

BOOTRST and IVSEL settings. If the program never enables an interrupt source, the Interrupt

Vectors are not used, and regular program code can be placed at these locations. This is also the case if the Reset Vector is in the Application section while the Interrupt Vectors are in the

Boot section or vice versa.

Table 12-2.

Reset and Interrupt Vectors placement

(1)

.

BOOTRST

1

1

0

0

IVSEL

0

1

0

1

Reset Address

0x0000

0x0000

Boot Reset Address

Boot Reset Address

Interrupt Vectors Start Address

0x0002

Boot Reset Address + 0x0002

0x0002

Boot Reset Address + 0x0002

Note: 1. The Boot Reset Address is shown in

Table 26-10 on page 292

. For the BOOTRST Fuse “1” means unprogrammed while “0” means programmed.

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The most typical and general program setup for the Reset and Interrupt Vector Addresses in

Atmel ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P is:

Labels

0x001C

0x001E

0x0020

0x0022

0x0024

0x0026

0x0028

0x002A

0x002C

0x002E

0x0030

Address

0x0000

0x0002

0x0004

0x0006

0x0008

0x000A

0x000C

0x000E

0x0010

0x0012

0x0014

0x0016

0x0018

0x001A

0x0032

0x0034

0x0036

0x0038

0x003A

0x003C

0x003E

0x0040

0x0042

0x0044

;

0x003E

0x003F

0x0040

0x0041

0x0042

0x0043

...

RESET:

...

ldi out ldi out sei

<instr

>

...

RESET

INT0

INT1

INT2

PCINT0

PCINT1

PCINT2

PCINT3

WDT

TIM2_COMPA

TIM2_COMPB

TIM2_OVF

TIM1_CAPT

TIM1_COMPA

TIM1_COMPB

TIM1_OVF

TIM0_COMPA

TIM0_COMPB

TIM0_OVF

SPI_STC

USART0_RXC

USART0_UDRE

USART0_TXC

ANA_COMP

ADC

EE_RDY

TWI

SPM_RDY

USART1_RXC

USART1_UDRE

USART1_TXC

TIM3_CAPT

TIM3_COMPA

TIM3_COMPB

TIM3_OVF jmp jmp jmp jmp jmp jmp jmp jmp jmp jmp jmp jmp jmp jmp jmp jmp jmp jmp jmp

Code jmp jmp jmp jmp jmp jmp jmp jmp jmp jmp jmp jmp jmp jmp jmp jmp r16,high(RAMEND)

SPH,r16 r16,low(RAMEND)

SPL,r16 xxx

...

Comments

; Reset

; IRQ0

; IRQ1

; IRQ2

; PCINT0

; PCINT1

; PCINT2

; PCINT3

; Watchdog Timeout

; Timer2 CompareA

; Timer2 CompareB

; Timer2 Overflow

; Timer1 Capture

; Timer1 CompareA

; Timer1 CompareB

; Timer1 Overflow

; Timer0 CompareA

; Timer0 CompareB

; Timer0 Overflow

; SPI Transfer Complete

; USART0 RX Complete

; USART0,UDR Empty

; USART0 TX Complete

; Analog Comparator

; ADC Conversion

Complete

; EEPROM Ready

; two-wire Serial

; SPM Ready

; USART1 RX Complete

; USART1,UDR Empty

; USART1 TX Complete

; Timer3 Capture

(1)

; Timer3 Compare

(1)

; Timer3 CompareB

(1)

; Timer3 Overflow

(1)

; Main program start

; Set Stack Pointer to top of RAM

; Enable interrupts

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Notes: 1. Applies only to Atmel ATmega1284P.

When the BOOTRST Fuse is unprogrammed, the Boot section size set to 8K bytes and the

IVSEL bit in the MCUCR Register is set before any interrupts are enabled, the most typical and general program setup for the Reset and Interrupt Vector Addresses is:

Address Labels Code

0x00000 RESET: ldi

0x00001

0x00002

0x00003

0x00004

0x00005

; out ldi out sei r16,high(RAMEND); Main program start

SPH,r16 r16,low(RAMEND)

SPL,r16

<instr> xxx

Comments

; Set Stack Pointer to top of RAM

; Enable interrupts

.org 0x1F002

0x1F002

0x1F004

...

jmp jmp

...

EXT_INT0

EXT_INT1

...

; IRQ0 Handler

; IRQ1 Handler

;

0x1FO36 jmp SPM_RDY ; SPM Ready Handler

When the BOOTRST Fuse is programmed and the Boot section size set to 8K bytes, the most typical and general program setup for the Reset and Interrupt Vector Addresses is:

Address Labels Code

.org 0x0002

0x00002

0x00004

...

0x00036 jmp jmp

...

jmp

EXT_INT0

EXT_INT1

...

SPM_RDY

Comments

; IRQ0 Handler

; IRQ1 Handler

;

; SPM Ready Handler

;

.org 0x1F000

0x1F000 RESET: ldi

0x1F001

0x1F002

0x1F003

0x1F004

0x1F005 out ldi out sei r16,high(RAMEND); Main program start

SPH,r16 r16,low(RAMEND)

SPL,r16

<instr> xxx

; Set Stack Pointer to top of RAM

; Enable interrupts

When the BOOTRST Fuse is programmed, the Boot section size set to 8K bytes and the IVSEL bit in the MCUCR Register is set before any interrupts are enabled, the most typical and general program setup for the Reset and Interrupt Vector Addresses is:

Comments Address Labels Code

;

.org 0x1F000

0x1F000

0x1F002

0x1F004 jmp jmp jmp

RESET

EXT_INT0

EXT_INT1

; Reset handler

; IRQ0 Handler

; IRQ1 Handler

64

ATmega164A/PA/324A/PA/644A/PA/1284/P

...

0x1F036

...

jmp

...

SPM_RDY

;

; SPM Ready Handler

;

0x1F03E RESET: ldi

0x1F03F

0x1F040

0x1F041

0x1F042

0x1FO43 out ldi out sei r16,high(RAMEND); Main program start

SPH,r16 r16,low(RAMEND)

SPL,r16

<instr> xxx

; Set Stack Pointer to top of RAM

; Enable interrupts

12.2.1

Moving Interrupts Between Application and Boot Space

The General Interrupt Control Register controls the placement of the Interrupt Vector table.

12.3

Register description

12.3.1

MCUCR – MCU Control Register

Bit

0x35 (0x55)

Read/Write

Initial Value

7

JTD

R/W

0

6

BODS

(1)

R/W

0

5

BODSE

(1)

R/W

0

4

PUD

R/W

0

3

R

0

2

R

0

Note: 1. Only available in the Atmel ATmega164PA/324PA/644PA/1284P.

1

IVSEL

R/W

0

0

IVCE

R/W

0

MCUCR

• Bit 1 – IVSEL: Interrupt Vector Select

When the IVSEL bit is cleared (zero), the Interrupt Vectors are placed at the start of the Flash memory. When this bit is set (one), the Interrupt Vectors are moved to the beginning of the Boot

Loader section of the Flash. The actual address of the start of the Boot Flash Section is determined by the BOOTSZ Fuses. Refer to the section

”Memory programming” on page 297 for

details. To avoid unintentional changes of Interrupt Vector tables, a special write procedure must be followed to change the IVSEL bit: a. Write the Interrupt Vector Change Enable (IVCE) bit to one.

b.

Within four cycles, write the desired value to IVSEL while writing a zero to IVCE.

Interrupts will automatically be disabled while this sequence is executed. Interrupts are disabled in the cycle IVCE is set, and they remain disabled until after the instruction following the write to

IVSEL. If IVSEL is not written, interrupts remain disabled for four cycles. The I-bit in the Status

Register is unaffected by the automatic disabling.

Note: If Interrupt Vectors are placed in the Boot Loader section and Boot Lock bit BLB02 is programmed, interrupts are disabled while executing from the Application section. If Interrupt Vectors are placed in the Application section and Boot Lock bit BLB12 is programed, interrupts are disabled while

executing from the Boot Loader section. Refer to the section ”Memory programming” on page 297

for details on Boot Lock bits.

• Bit 0 – IVCE: Interrupt Vector Change Enable

The IVCE bit must be written to logic one to enable change of the IVSEL bit. IVCE is cleared by hardware four cycles after it is written or when IVSEL is written. Setting the IVCE bit will disable interrupts, as explained in the IVSEL description above. See the following Code Example.

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Assembly Code Example

Move_interrupts:

; Get MCUCR

in

r16, MCUCR

mov

r17, r16

; Enable change of Interrupt Vectors

ori

r16, (1<<IVCE)

out

MCUCR, r16

; Move interrupts to Boot Flash section

ori

r17, (1<<IVSEL)

out

MCUCR, r17

ret

C Code Example

void

Move_interrupts(void)

{ uchar temp;

/* GET MCUCR*/ temp = MCUCR;

/* Enable change of Interrupt Vectors */

MCUCR = temp|(1<<IVCE);

/* Move interrupts to Boot Flash section */

MCUCR = temp|(1<<IVSEL);

}

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ATmega164A/PA/324A/PA/644A/PA/1284/P

13. External Interrupts

13.1

Overview

The External Interrupts are triggered by the INT2:0 pin or any of the PCINT31:0 pins. Observe that, if enabled, the interrupts will trigger even if the INT2:0 or PCINT31:0 pins are configured as outputs. This feature provides a way of generating a software interrupt.

The Pin change interrupt PCI3 will trigger if any enabled PCINT31:24 pin toggle, Pin change interrupt PCI2 will trigger if any enabled PCINT23:16 pin toggles, Pin change interrupt PCI1 if any enabled PCINT15:8 toggles and Pin change interrupts PCI0 will trigger if any enabled

PCINT7:0 pin toggles. PCMSK3, PCMSK2, PCMSK1 and PCMSK0 Registers control which pins contribute to the pin change interrupts. Pin change interrupts on PCINT31:0 are detected asynchronously. This implies that these interrupts can be used for waking the part also from sleep modes other than Idle mode.

In order for a pin change interrupt (PCINT) to be generated, the device must have an active I/O

clock. As shown in Table 10-1 on page 42 , the I/O clock domain is active in Idle Mode, but not in

deeper sleep modes. In sleep modes deeper than Idle Mode, a toggled pin must remain in its toggled state until the device has fully woken up. See

Section 9. ”System clock and clock options” on page 30 for wake up times. If the pin toggles back to its initial state during wake up,

the device will still complete the procedure, but will not generate an interrupt once awake.

The External Interrupts can be triggered by a falling or rising edge or a low level. This is set up as indicated in the specification for the External Interrupt Control Registers – EICRA (INT2:0).

When the external interrupt is enabled and is configured as level triggered, the interrupt will trigger as long as the pin is held low. Low level interrupts and the edge interrupt on INT2:0 are detected asynchronously. This implies that these interrupts can be used for waking the part also from sleep modes other than Idle mode. The I/O clock is halted in all sleep modes except Idle mode.

Note that if a level triggered interrupt is used for wake-up from Power-down, the required level must be held long enough for the MCU to complete the wake-up to trigger the level interrupt. If the level disappears before the end of the Start-up Time, the MCU will still wake up, but no interrupt will be generated. The start-up time is defined by the SUT and CKSEL Fuses as described

in ”System clock and clock options” on page 30 .

13.2

Register description

13.2.1

EICRA – External Interrupt Control Register A

The External Interrupt Control Register A contains control bits for interrupt sense control.

Bit

(0x69)

Read/Write

Initial Value

R

0

7

R

0

6

5

ISC21

R/W

0

4

ISC20

R/W

0

3

ISC11

R/W

0

2

ISC10

R/W

0

1

ISC01

R/W

0

0

ISC00

R/W

0

EICRA

• Bits 7:6 – Reserved

These bits are reserved in the ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P, and will always read as zero.

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• Bits 5:0 – ISC21, ISC20 – ISC00, ISC00: External Interrupt 2 - 0 Sense Control Bits

The External Interrupts 2 - 0 are activated by the external pins INT2:0 if the SREG I-flag and the corresponding interrupt mask in the EIMSK is set. The level and edges on the external pins that activate the interrupts are defined in

Table 13-1

. Edges on INT2:INT0 are registered asynchronously. Pulses on INT2:0 pins wider than the minimum pulse width given in

”External interrupts characteristics” on page 337

will generate an interrupt. Shorter pulses are not guaranteed to generate an interrupt. If low level interrupt is selected, the low level must be held until the completion of the currently executing instruction to generate an interrupt. If enabled, a level triggered interrupt will generate an interrupt request as long as the pin is held low. When changing the

ISCn bit, an interrupt can occur. Therefore, it is recommended to first disable INTn by clearing its

Interrupt Enable bit in the EIMSK Register. Then, the ISCn bit can be changed. Finally, the INTn interrupt flag should be cleared by writing a logical one to its Interrupt Flag bit (INTFn) in the

EIFR Register before the interrupt is re-enabled.

13.2.2

Table 13-1.

Interrupt Sense Control

(1)

.

ISCn1

0

0

1

ISCn0 Description

0 The low level of INTn generates an interrupt request

1

0

Any edge of INTn generates asynchronously an interrupt request

The falling edge of INTn generates asynchronously an interrupt request

1 1 The rising edge of INTn generates asynchronously an interrupt request

Note: 1. n = 2, 1 or 0.

When changing the ISCn1/ISCn0 bits, the interrupt must be disabled by clearing its Interrupt

Enable bit in the EIMSK Register. Otherwise an interrupt can occur when the bits are changed.

EIMSK – External Interrupt Mask Register

13.2.3

Bit

0x1D (0x3D)

Read/Write

Initial Value

R

0

7

R

0

6

R

0

5

R

0

4

R

0

3

2

INT2

R/W

0

1

INT1

R/W

0

0

IINT0

R/W

0

EIMSK

• Bits 2:0 – INT2:0: External Interrupt Request 2 - 0 Enable

When an INT2:0 bit is written to one and the I-bit in the Status Register (SREG) is set (one), the corresponding external pin interrupt is enabled. The Interrupt Sense Control bits in the External

Interrupt Control Register, EICRA, defines whether the external interrupt is activated on rising or falling edge or level sensed. Activity on any of these pins will trigger an interrupt request even if the pin is enabled as an output. This provides a way of generating a software interrupt.

EIFR –External Interrupt Flag Register

Bit

0x1C (0x3C)

Read/Write

Initial Value

7

R/W

0

6

R

0

5

R

0

4

R

0

3

R

0

2

INTF2

R/W

0

1

INTF1

R/W

0

0

IINTF0

R/W

0

EIFR

• Bits 2:0 – INTF2:0: External Interrupt Flags 2 - 0

When an edge or logic change on the INT2:0 pin triggers an interrupt request, INTF2:0 becomes set (one). If the I-bit in SREG and the corresponding interrupt enable bit, INT2:0 in EIMSK, are set (one), the MCU will jump to the interrupt vector. The flag is cleared when the interrupt routine

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13.2.4

13.2.5

is executed. Alternatively, the flag can be cleared by writing a logical one to it. These flags are always cleared when INT2:0 are configured as level interrupt. Note that when entering sleep mode with the INT2:0 interrupts disabled, the input buffers on these pins will be disabled. This

may cause a logic change in internal signals which will set the INTF2:0 flags. See ”Digital Input

Enable and Sleep Modes” on page 76

for more information.

PCICR – Pin Change Interrupt Control Register

Bit

(0x68)

Read/Write

Initial Value

R

0

7

R

0

6

R

0

5

R

0

4

3

PCIE3

R/W

0

2

PCIE2

R/W

0

1

PCIE1

R/W

0

0

PCIE0

R/W

0

PCICR

• Bit 3 – PCIE3: Pin Change Interrupt Enable 3

When the PCIE3 bit is set (one) and the I-bit in the Status Register (SREG) is set (one), pin change interrupt 3 is enabled. Any change on any enabled PCINT31:24 pin will cause an interrupt. The corresponding interrupt of Pin Change Interrupt Request is executed from the PCI3

Interrupt Vector. PCINT31:24 pins are enabled individually by the PCMSK3 Register.

• Bit 2 – PCIE2: Pin Change Interrupt Enable 2

When the PCIE2 bit is set (one) and the I-bit in the Status Register (SREG) is set (one), pin change interrupt 2 is enabled. Any change on any enabled PCINT23:16 pin will cause an interrupt. The corresponding interrupt of Pin Change Interrupt Request is executed from the PCI2

Interrupt Vector. PCINT23:16 pins are enabled individually by the PCMSK2 Register.

• Bit 1 – PCIE1: Pin Change Interrupt Enable 1

When the PCIE1 bit is set (one) and the I-bit in the Status Register (SREG) is set (one), pin change interrupt 1 is enabled. Any change on any enabled PCINT15:8 pin will cause an interrupt. The corresponding interrupt of Pin Change Interrupt Request is executed from the PCI1

Interrupt Vector. PCINT15:8 pins are enabled individually by the PCMSK1 Register.

• Bit 0 – PCIE0: Pin Change Interrupt Enable 0

When the PCIE0 bit is set (one) and the I-bit in the Status Register (SREG) is set (one), pin change interrupt 0 is enabled. Any change on any enabled PCINT7:.0 pin will cause an interrupt.

The corresponding interrupt of Pin Change Interrupt Request is executed from the PCI0 Interrupt

Vector. PCINT7:0 pins are enabled individually by the PCMSK0 Register.

PCIFR – Pin Change Interrupt Flag Register

Bit

0x1B (0x3B)

Read/Write

Initial Value

7

R

0

6

R

0

R

0

5

R

0

4

3

PCIF3

R/W

0

2

PCIF2

R/W

0

1

PCIF1

R/W

0

0

PCIF0

R/W

0

PCIFR

• Bit 3– PCIF3: Pin Change Interrupt Flag 3

When a logic change on any PCINT31:24 pin triggers an interrupt request, PCIF3 becomes set

(one). If the I-bit in SREG and the PCIE3 bit in PCICR are set (one), the MCU will jump to the corresponding Interrupt Vector. The flag is cleared when the interrupt routine is executed. Alternatively, the flag can be cleared by writing a logical one to it.

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13.2.6

13.2.7

13.2.8

• Bit 2 – PCIF2: Pin Change Interrupt Flag 2

When a logic change on any PCINT23:16 pin triggers an interrupt request, PCIF2 becomes set

(one). If the I-bit in SREG and the PCIE2 bit in PCICR are set (one), the MCU will jump to the corresponding Interrupt Vector. The flag is cleared when the interrupt routine is executed. Alternatively, the flag can be cleared by writing a logical one to it.

• Bit 1 – PCIF1: Pin Change Interrupt Flag 1

When a logic change on any PCINT15:8 pin triggers an interrupt request, PCIF1 becomes set

(one). If the I-bit in SREG and the PCIE1 bit in PCICR are set (one), the MCU will jump to the corresponding Interrupt Vector. The flag is cleared when the interrupt routine is executed. Alternatively, the flag can be cleared by writing a logical one to it.

• Bit 0 – PCIF0: Pin Change Interrupt Flag 0

When a logic change on any PCINT7:0 pin triggers an interrupt request, PCIF0 becomes set

(one). If the I-bit in SREG and the PCIE0 bit in PCICR are set (one), the MCU will jump to the corresponding Interrupt Vector. The flag is cleared when the interrupt routine is executed. Alternatively, the flag can be cleared by writing a logical one to it.

PCMSK3 – Pin Change Mask Register 3

Bit

(0x73)

Read/Write

Initial Value

7

PCINT31

R/W

0

6

PCINT30

R/W

0

5

PCINT29

R/W

0

4

PCINT28

R/W

0

3

PCINT27

R/W

0

2

PCINT26

R/W

0

1

PCINT25

R/W

0

0

PCINT24

R/W

0

PCMSK3

• Bit 7:0 – PCINT31:24: Pin Change Enable Mask 31:24

Each PCINT31:24-bit selects whether pin change interrupt is enabled on the corresponding I/O pin. If PCINT31:24 is set and the PCIE3 bit in PCICR is set, pin change interrupt is enabled on the corresponding I/O pin. If PCINT31:24 is cleared, pin change interrupt on the corresponding

I/O pin is disabled.

PCMSK2 – Pin Change Mask Register 2

Bit

(0x6D)

Read/Write

Initial Value

7

PCINT23

R/W

0

6

PCINT22

R/W

0

5

PCINT21

R/W

0

4

PCINT20

R/W

0

3

PCINT19

R/W

0

2

PCINT18

R/W

0

1

PCINT17

R/W

0

0

PCINT16

R/W

0

PCMSK2

• Bit 7:0 – PCINT23:16: Pin Change Enable Mask 23..16

Each PCINT23:16-bit selects whether pin change interrupt is enabled on the corresponding I/O pin. If PCINT23:16 is set and the PCIE2 bit in PCICR is set, pin change interrupt is enabled on the corresponding I/O pin. If PCINT23:16 is cleared, pin change interrupt on the corresponding

I/O pin is disabled.

PCMSK1 – Pin Change Mask Register 1

Bit

(0x6C)

Read/Write

Initial Value

7

PCINT15

R/W

0

6

PCINT14

R/W

0

5

PCINT13

R/W

0

4

PCINT12

R/W

0

3

PCINT11

R/W

0

2

PCINT10

R/W

0

1

PCINT9

R/W

0

0

PCINT8

R/W

0

PCMSK1

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13.2.9

• Bit 7:0 – PCINT15:8: Pin Change Enable Mask 15..8

Each PCINT15:8-bit selects whether pin change interrupt is enabled on the corresponding I/O pin. If PCINT15:8 is set and the PCIE1 bit in EIMSK is set, pin change interrupt is enabled on the corresponding I/O pin. If PCINT15:8 is cleared, pin change interrupt on the corresponding I/O pin is disabled.

PCMSK0 – Pin Change Mask Register 0

Bit

(0x6B)

Read/Write

Initial Value

7

PCINT7

R/W

0

6

PCINT6

R/W

0

5

PCINT5

R/W

0

4

PCINT4

R/W

0

3

PCINT3

R/W

0

2

PCINT2

R/W

0

1

PCINT1

R/W

0

0

PCINT0

R/W

0

PCMSK0

• Bit 7:0 – PCINT7:0: Pin Change Enable Mask 7..0

Each PCINT7:0 bit selects whether pin change interrupt is enabled on the corresponding I/O pin.

If PCINT7:0 is set and the PCIE0 bit in PCICR is set, pin change interrupt is enabled on the corresponding I/O pin. If PCINT7..0 is cleared, pin change interrupt on the corresponding I/O pin is disabled.

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14. I/O-Ports

14.1

Overview

All AVR ports have true Read-Modify-Write functionality when used as general digital I/O ports.

This means that the direction of one port pin can be changed without unintentionally changing the direction of any other pin with the SBI and CBI instructions. The same applies when changing drive value (if configured as output) or enabling/disabling of pull-up resistors (if configured as input). Each output buffer has symmetrical drive characteristics with both high sink and source capability. The pin driver is strong enough to drive LED displays directly. All port pins have individually selectable pull-up resistors with a supply-voltage invariant resistance. All I/O pins have protection diodes to both V

CC

and Ground as indicated in Figure 14-1

. Refer to ”Electrical characteristics” on page 329 for a complete list of parameters.

Figure 14-1.

I/O pin equivalent schematic.

8272D–AVR–05/12

Pxn

C

pin

R

pu

Logic

See Figure

"General Digital I/O" for

Details

All registers and bit references in this section are written in general form. A lower case “x” represents the numbering letter for the port, and a lower case “n” represents the bit number. However, when using the register or bit defines in a program, the precise form must be used. For example,

PORTB3 for bit no. 3 in Port B, here documented generally as PORTxn. The physical I/O Regis-

ters and bit locations are listed in ”Register description” on page 91 .

Three I/O memory address locations are allocated for each port, one each for the Data Register

– PORTx, Data Direction Register – DDRx, and the Port Input Pins – PINx. The Port Input Pins

I/O location is read only, while the Data Register and the Data Direction Register are read/write.

However, writing a logic one to a bit in the PINx Register, will result in a toggle in the corresponding bit in the Data Register. In addition, the Pull-up Disable – PUD bit in MCUCR disables the pull-up function for all pins in all ports when set.

Using the I/O port as General Digital I/O is described in

”Ports as General Digital I/O” on page

73 . Most port pins are multiplexed with alternate functions for the peripheral features on the

device. How each alternate function interferes with the port pin is described in

”Alternate Port

Functions” on page 77 . Refer to the individual module sections for a full description of the alter-

nate functions.

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ATmega164A/PA/324A/PA/644A/PA/1284/P

Note that enabling the alternate function of some of the port pins does not affect the use of the other pins in the port as general digital I/O.

14.2

Ports as General Digital I/O

The ports are bi-directional I/O ports with optional internal pull-ups.

Figure 14-2 shows a func-

tional description of one I/O-port pin, here generically called Pxn.

Figure 14-2.

General digital I/O

(1)

.

PUD

Q D

DDxn

Q

CLR

RESET

WDx

RDx

Pxn

SLEEP

Q D

PORTxn

Q

CLR

RESET

RRx

1

0

WRx

WPx

SYNCHRONIZER

D Q

L

Q

D Q

PINxn

Q

RPx

14.2.1

clk

I/O

PUD:

SLEEP: clk

I/O

:

PULLUP DISABLE

SLEEP CONTROL

I/O CLOCK

WDx:

RDx:

WRx:

RRx:

RPx:

WPx:

WRITE DDRx

READ DDRx

WRITE PORTx

READ PORTx REGISTER

READ PORTx PIN

WRITE PINx REGISTER

Note: 1. WRx, WPx, WDx, RRx, RPx, and RDx are common to all pins within the same port. clk

I/O

,

SLEEP, and PUD are common to all ports.

Configuring the Pin

Each port pin consists of three register bits: DDxn, PORTxn, and PINxn. As shown in ”Register description” on page 91

, the DDxn bits are accessed at the DDRx I/O address, the PORTxn bits at the PORTx I/O address, and the PINxn bits at the PINx I/O address.

The DDxn bit in the DDRx Register selects the direction of this pin. If DDxn is written logic one,

Pxn is configured as an output pin. If DDxn is written logic zero, Pxn is configured as an input pin.

If PORTxn is written logic one when the pin is configured as an input pin, the pull-up resistor is activated. To switch the pull-up resistor off, PORTxn has to be written logic zero or the pin has to be configured as an output pin. The port pins are tri-stated when reset condition becomes active, even if no clocks are running.

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14.2.2

14.2.3

14.2.4

If PORTxn is written logic one when the pin is configured as an output pin, the port pin is driven high (one). If PORTxn is written logic zero when the pin is configured as an output pin, the port pin is driven low (zero).

Toggling the pin

Writing a logic one to PINxn toggles the value of PORTxn, independent on the value of DDRxn.

Note that the SBI instruction can be used to toggle one single bit in a port.

Switching between input and output

When switching between tri-state ({DDxn, PORTxn} = 0b00) and output high ({DDxn, PORTxn}

= 0b11), an intermediate state with either pull-up enabled {DDxn, PORTxn} = 0b01) or output low ({DDxn, PORTxn} = 0b10) must occur. Normally, the pull-up enabled state is fully acceptable, as a high-impedant environment will not notice the difference between a strong high driver and a pull-up. If this is not the case, the PUD bit in the MCUCR Register can be set to disable all pull-ups in all ports.

Switching between input with pull-up and output low generates the same problem. The user must use either the tri-state ({DDxn, PORTxn} = 0b00) or the output high state ({DDxn, PORTxn}

= 0b11) as an intermediate step.

Table 14-1

summarizes the control signals for the pin value.

Table 14-1.

Port pin configurations.

DDxn

0

0

0

1

1

Reading the Pin Value

PORTxn

0

1

1

0

1

PUD

(in MCUCR)

X

0

1

X

X

I/O

Input

Input

Input

Output

Output

Pull-up Comment

No Tri-state (Hi-Z)

Yes Pxn will source current if ext. pulled low.

No

No

No

Tri-state (Hi-Z)

Output Low (Sink)

Output High (Source)

Independent of the setting of Data Direction bit DDxn, the port pin can be read through the

PINxn Register bit. As shown in Figure 14-2 , the PINxn Register bit and the preceding latch con-

stitute a synchronizer. This is needed to avoid metastability if the physical pin changes value near the edge of the internal clock, but it also introduces a delay.

Figure 14-3

shows a timing diagram of the synchronization when reading an externally applied pin value. The maximum and minimum propagation delays are denoted t pd,max

and t pd,min

respectively.

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Figure 14-3.

Synchronization when reading an externally applied pin value.

SYSTEM CLK

INSTRUCTIONS

SYNC LATCH

PINxn r17

XXX XXX in r17, PINx

0xFF 0x00 t pd, max t pd, min

Consider the clock period starting shortly after the first falling edge of the system clock. The latch is closed when the clock is low, and goes transparent when the clock is high, as indicated by the shaded region of the “SYNC LATCH” signal. The signal value is latched when the system clock goes low. It is clocked into the PINxn Register at the succeeding positive clock edge. As indicated by the two arrows tpd,max and tpd,min, a single signal transition on the pin will be delayed between ½ and 1½ system clock period depending upon the time of assertion.

When reading back a software assigned pin value, a nop instruction must be inserted as indi-

cated in Figure 14-4 . The out instruction sets the “SYNC LATCH” signal at the positive edge of

the clock. In this case, the delay tpd through the synchronizer is 1 system clock period.

Figure 14-4.

Synchronization when reading a software assigned pin value.

SYSTEM CLK r16

INSTRUCTIONS

SYNC LATCH

PINxn r17 out PORTx, r16 nop

0xFF in r17, PINx

0x00 t pd

0xFF

The following code example shows how to set port B pins 0 and 1 high, 2 and 3 low, and define the port pins from 4 to 7 as input with pull-ups assigned to port pins 6 and 7. The resulting pin values are read back again, but as previously discussed, a nop instruction is included to be able to read back the value recently assigned to some of the pins.

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14.2.5

Assembly Code Example

(1)

...

; Define pull-ups and set outputs high

; Define directions for port pins

ldi

r16,(1<<PB7)|(1<<PB6)|(1<<PB1)|(1<<PB0)

ldi

r17,(1<<DDB3)|(1<<DDB2)|(1<<DDB1)|(1<<DDB0)

out

PORTB,r16

out

DDRB,r17

; Insert nop for synchronization

nop

; Read port pins

in

r16,PINB

...

C Code Example

unsigned char

i;

...

/* Define pull-ups and set outputs high */

/* Define directions for port pins */

PORTB = (1<<PB7)|(1<<PB6)|(1<<PB1)|(1<<PB0);

DDRB = (1<<DDB3)|(1<<DDB2)|(1<<DDB1)|(1<<DDB0);

/* Insert nop for synchronization*/

__no_operation();

/* Read port pins */ i = PINB;

...

Note: 1. For the assembly program, two temporary registers are used to minimize the time from pullups are set on pins 0, 1, 6, and 7, until the direction bits are correctly set, defining bit 2 and 3 as low and redefining bits 0 and 1 as strong high drivers.

Digital Input Enable and Sleep Modes

As shown in

Figure 14-2 , the digital input signal can be clamped to ground at the input of the

schmitt-trigger. The signal denoted SLEEP in the figure, is set by the MCU Sleep Controller in

Power-down mode, Power-save mode, and Standby mode to avoid high power consumption if some input signals are left floating, or have an analog signal level close to V

CC

/2.

SLEEP is overridden for port pins enabled as external interrupt pins. If the external interrupt request is not enabled, SLEEP is active also for these pins. SLEEP is also overridden by various other alternate functions as described in

”Alternate Port Functions” on page 77 .

If a logic high level (“one”) is present on an asynchronous external interrupt pin configured as

“Interrupt on Rising Edge, Falling Edge, or Any Logic Change on Pin” while the external interrupt is not enabled, the corresponding External Interrupt Flag will be set when resuming from the above mentioned Sleep mode, as the clamping in these sleep mode produces the requested logic change.

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14.2.6

Unconnected Pins

If some pins are unused, it is recommended to ensure that these pins have a defined level. Even though most of the digital inputs are disabled in the deep sleep modes as described above, floating inputs should be avoided to reduce current consumption in all other modes where the digital inputs are enabled (Reset, Active mode, and Idle mode).

The simplest method to ensure a defined level of an unused pin, is to enable the internal pull-up.

In this case, the pull-up will be disabled during reset. If low power consumption during reset is important, it is recommended to use an external pull-up or pull-down. Connecting unused pins directly to V

CC

or GND is not recommended, since this may cause excessive currents if the pin is accidentally configured as an output.

14.3

Alternate Port Functions

Most port pins have alternate functions in addition to being general digital I/Os.

Figure 14-5

shows how the port pin control signals from the simplified Figure 14-2 on page 73

can be overridden by alternate functions. The overriding signals may not be present in all port pins, but the figure serves as a generic description applicable to all port pins in the AVR microcontroller family.

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Figure 14-5.

Alternate port functions

(1)

.

PUOExn

PUOVxn

1

0

PUD

DDOExn

DDOVxn

1

0

PVOExn

PVOVxn

Q D

DDxn

Q

CLR

RESET

W Dx

RDx

Pxn

1

0

1

0

DIEOExn

DIEOVxn

SLEEP

SYNCHRONIZER

D

SET

Q

L

CLR

Q

D Q

PINxn

CLR

Q

Q D

PORTxn

Q

CLR

RESET

1

0

RRx

W Rx

PTOExn

W Px

RPx clk

I/O

DIxn

AIOxn

PUOExn: Pxn PULL-UP OVERRIDE ENABLE

PUOVxn: Pxn PULL-UP OVERRIDE VALUE

DDOExn: Pxn DATA DIRECTION OVERRIDE ENABLE

DDOVxn: Pxn DATA DIRECTION OVERRIDE VALUE

PVOExn: Pxn PORT VALUE OVERRIDE ENABLE

PVOVxn: Pxn PORT VALUE OVERRIDE VALUE

DIEOExn: Pxn DIGITAL INPUT-ENABLE OVERRIDE ENABLE

DIEOVxn: Pxn DIGITAL INPUT-ENABLE OVERRIDE VALUE

SLEEP: SLEEP CONTROL

PTOExn: Pxn, PORT TOGGLE OVERRIDE ENABLE

PUD:

W Dx:

RDx:

RRx:

W Rx:

RPx:

W Px: clk

I/O

:

DIxn:

AIOxn:

PULLUP DISABLE

WRITE DDRx

READ DDRx

READ PORTx REGISTER

WRITE PORTx

READ PORTx PIN

W RITE PINx

I/O CLOCK

DIGITAL INPUT PIN n ON PORTx

ANALOG INPUT/OUTPUT PIN n ON PORTx

Note: 1. WRx, WPx, WDx, RRx, RPx, and RDx are common to all pins within the same port. clk

I/O

,

SLEEP, and PUD are common to all ports. All other signals are unique for each pin.

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Table 14-2

summarizes the function of the overriding signals. The pin and port indexes from Figure 14-5

are not shown in the succeeding tables. The overriding signals are generated internally in the modules having the alternate function.

Table 14-2.

Generic description of overriding signals for alternate functions.

Signal name

PUOE

PUOV

DDOE

DDOV

PVOE

PVOV

Full name

Pull-up Override

Enable

Pull-up Override

Value

Data Direction

Override Enable

Data Direction

Override Value

Port Value

Override Enable

Description

If this signal is set, the pull-up enable is controlled by the PUOV signal. If this signal is cleared, the pull-up is enabled when

{DDxn, PORTxn, PUD} = 0b010.

If PUOE is set, the pull-up is enabled/disabled when PUOV is set/cleared, regardless of the setting of the DDxn, PORTxn, and PUD Register bits.

If this signal is set, the Output Driver Enable is controlled by the

DDOV signal. If this signal is cleared, the Output driver is enabled by the DDxn Register bit.

If DDOE is set, the Output Driver is enabled/disabled when

DDOV is set/cleared, regardless of the setting of the DDxn

Register bit.

If this signal is set and the Output Driver is enabled, the port value is controlled by the PVOV signal. If PVOE is cleared, and the Output Driver is enabled, the port Value is controlled by the

PORTxn Register bit.

If PVOE is set, the port value is set to PVOV, regardless of the setting of the PORTxn Register bit.

PTOE

DIEOE

DIEOV

DI

AIO

Port Value

Override Value

Port Toggle

Override Enable

Digital Input

Enable Override

Enable

Digital Input

Enable Override

Value

Digital Input

Analog

Input/Output

If PTOE is set, the PORTxn Register bit is inverted.

If this bit is set, the Digital Input Enable is controlled by the

DIEOV signal. If this signal is cleared, the Digital Input Enable is determined by MCU state (Normal mode, sleep mode).

If DIEOE is set, the Digital Input is enabled/disabled when

DIEOV is set/cleared, regardless of the MCU state (Normal mode, sleep mode).

This is the Digital Input to alternate functions. In the figure, the signal is connected to the output of the schmitt trigger but before the synchronizer. Unless the Digital Input is used as a clock source, the module with the alternate function will use its own synchronizer.

This is the Analog Input/output to/from alternate functions. The signal is connected directly to the pad, and can be used bidirectionally.

The following subsections shortly describe the alternate functions for each port, and relate the overriding signals to the alternate function. Refer to the alternate function description for further details.

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14.3.1

Alternate Functions of Port A

The Port A pins with alternate functions are shown in

Table 14-3

.

Table 14-3.

Port A pins alternate functions.

Port pin

PA7

PA6

PA5

PA4

PA3

PA2

PA1

PA0

Alternate function

ADC7 (ADC input channel 7)

PCINT7 (Pin Change Interrupt 7)

ADC6 (ADC input channel 6)

PCINT6 (Pin Change Interrupt 6)

ADC5 (ADC input channel 5)

PCINT5 (Pin Change Interrupt 5)

ADC4 (ADC input channel 4)

PCINT4 (Pin Change Interrupt 4)

ADC3 (ADC input channel 3)

PCINT3 (Pin Change Interrupt 3)

ADC2 (ADC input channel 2)

PCINT2 (Pin Change Interrupt 2)

ADC1 (ADC input channel 1)

PCINT1 (Pin Change Interrupt 1)

ADC0 (ADC input channel 0)

PCINT0 (Pin Change Interrupt 0)

• ADC7:0/PCINT7:0 – Port A, Bit 7:0

ADC7:0, Analog to Digital Converter, Channels 7:0

.

PCINT7:0, Pin Change Interrupt source 7:0: The PA7:0 pins can serve as external interrupt sources.

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Table 14-4 on page 81 and Table 14-5 on page 81 relate the alternate functions of Port A to the

overriding signals shown in

Figure 14-5 on page 78 .

Table 14-4.

Overriding Signals for Alternate Functions in PA7:PA4.

Signal name

PUOE

PUOV

DDOE

DDOV

PVOE

PVOV

DIEOE

DIEOV

DI

AIO

0

0

0

0

PA7/ADC7/

PCINT7

0

0

PCINT7 • PCIE0 +

ADC7D

PCINT7 • PCIE0

PCINT7 INPUT

ADC7 INPUT

0

0

0

0

PA6/ADC6/

PCINT6

0

0

PCINT6 • PCIE0 +

ADC6D

PCINT6 • PCIE0

PCINT6 INPUT

ADC6 INPUT

0

0

0

0

PA5/ADC5/

PCINT5

0

0

PCINT5 • PCIE0 +

ADC5D

PCINT5 • PCIE0

PCINT5 INPUT

ADC5 INPUT

0

0

0

0

PA4/ADC4/

PCINT4

0

0

PCINT4 • PCIE0 +

ADC4D

PCINT4 • PCIE0

PCINT4 INPUT

ADC4 INPUT

Table 14-5.

Overriding Signals for Alternate Functions in PA3:PA0.

Signal

Name

PUOE

PUOV

DDOE

DDOV

PVOE

PVOV

DIEOE

DIEOV

DI

AIO

0

0

0

0

PA3/ADC3/

PCINT3

0

0

PCINT3 • PCIE0 +

ADC3D

PCINT3 • PCIE0

PCINT3 INPUT

ADC3 INPUT

0

0

0

0

PA2/ADC2/

PCINT2

0

0

PCINT2 • PCIE0 +

ADC2D

PCINT2 • PCIE0

PCINT2 INPUT

ADC2 INPUT

0

0

0

0

PA1/ADC1/

PCINT1

0

0

PCINT1 • PCIE0 +

ADC1D

PCINT1 • PCIE0

PCINT1 INPUT

ADC1 INPUT

0

0

0

0

PA0/ADC0/

PCINT0

0

0

PCINT0 • PCIE0 +

ADC0D

PCINT0 • PCIE0

PCINT0 INPUT

ADC0 INPUT

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14.3.2

Alternate Functions of Port B

The Port B pins with alternate functions are shown in

Table 14-6

.

Table 14-6.

Port B pins alternate functions.

Port Pin Alternate Functions

PB7

SCK (SPI Bus Master clock input)

OC3B (Timer/Conter 3 Output Compare Match B Output)

PCINT15 (Pin Change Interrupt 15)

PB6

PB5

MISO (SPI Bus Master Input/Slave Output)

OC3A (Timer/Conter 3 Output Compare Match A Output)

PCINT14 (Pin Change Interrupt 14)

MOSI (SPI Bus Master Output/Slave Input)

ICP3 (Timer/Counter3 Input Capture Trigger)

PCINT13 (Pin Change Interrupt 13)

PB4

PB3

PB2

PB1

PB0

SS (SPI Slave Select input)

OC0B (Timer/Conter 0 Output Compare Match B Output)

PCINT12 (Pin Change Interrupt 12)

AIN1 (Analog Comparator Negative Input)

OC0A (Timer/Conter 0 Output Compare Match A Output)

PCINT11 (Pin Change Interrupt 11)

AIN0 (Analog Comparator Positive Input)

INT2 (External Interrupt 2 Input)

PCINT10 (Pin Change Interrupt 10)

T1 (Timer/Counter 1 External Counter Input)

CLKO (Divided System Clock Output)

PCINT9 (Pin Change Interrupt 9)

T0 (Timer/Counter 0 External Counter Input)

XCK0 (USART0 External Clock Input/Output)

PCINT8 (Pin Change Interrupt 8)

The alternate pin configuration is as follows:

• SCK/OC3B/PCINT15 – Port B, Bit 7

SCK: Master Clock output, Slave Clock input pin for SPI channel. When the SPI is enabled as a slave, this pin is configured as an input regardless of the setting of DDB7. When the SPI0 is enabled as a master, the data direction of this pin is controlled by DDB7. When the pin is forced to be an input, the pull-up can still be controlled by the PORTB7 bit.

OC3B, Output Compare Match B output: The PB7 pin can serve as an external output for the

Timer/Counter3 Output Compare. The pin has to be configured as an output (DDB7 set “one”) to serve this function. The OC3B pin is also the output pin for the PWM mode timer function.

PCINT15, Pin Change Interrupt source 15: The PB7 pin can serve as an external interrupt source.

• MISO/OC3A/PCINT14 – Port B, Bit 6

MISO: Master Data input, Slave Data output pin for SPI channel. When the SPI is enabled as a master, this pin is configured as an input regardless of the setting of DDB6. When the SPI is enabled as a slave, the data direction of this pin is controlled by DDB6. When the pin is forced to be an input, the pull-up can still be controlled by the PORTB6 bit.

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OC3A, Output Compare Match A output: The PB6 pin can serve as an external output for the

Timer/Counter0 Output Compare. The pin has to be configured as an output (DDB6 set “one”) to serve this function. The OC3A pin is also the output pin for the PWM mode timer function.

PCINT14, Pin Change Interrupt source 14: The PB6 pin can serve as an external interrupt source.

• MOSI/ICP3/PCINT13 – Port B, Bit 5

MOSI: SPI Master Data output, Slave Data input for SPI channel. When the SPI is enabled as a slave, this pin is configured as an input regardless of the setting of DDB5. When the SPI is enabled as a master, the data direction of this pin is controlled by DDB5. When the pin is forced to be an input, the pull-up can still be controlled by the PORTB5 bit.

ICP3, Input Capture Pin 3: The PB5 pin can act as an input capture pin for Timer/Counter3.

PCINT13, Pin Change Interrupt source 13: The PB5 pin can serve as an external interrupt source.

• SS/OC0B/PCINT12 – Port B, Bit 4

SS: Slave Port Select input. When the SPI is enabled as a slave, this pin is configured as an input regardless of the setting of DDB4. As a slave, the SPI is activated when this pin is driven low. When the SPI is enabled as a master, the data direction of this pin is controlled by DDB4.

When the pin is forced to be an input, the pull-up can still be controlled by the PORTB4 bit.

OC0B, Output Compare Match B output: The PB4 pin can serve as an external output for the

Timer/Counter0 Output Compare. The pin has to be configured as an output (DDB4 set “one”) to serve this function. The OC0B pin is also the output pin for the PWM mode timer function.

PCINT12, Pin Change Interrupt source 12: The PB4 pin can serve as an external interrupt source.

• AIN1/OC0A/PCINT11, Bit 3

AIN1, Analog Comparator Negative input. This pin is directly connected to the negative input of the Analog Comparator.

OC0A, Output Compare Match A output: The PB3 pin can serve as an external output for the

Timer/Counter0 Output Compare. The pin has to be configured as an output (DDB3 set “one”) to serve this function. The OC0A pin is also the output pin for the PWM mode timer function.

PCINT11, Pin Change Interrupt source 11: The PB3 pin can serve as an external interrupt source.

• AIN0/INT2/PCINT10, Bit 2

AIN0, Analog Comparator Positive input. This pin is directly connected to the positive input of the Analog Comparator.

INT2, External Interrupt source 2. The PB2 pin can serve as an External Interrupt source to the

MCU.

PCINT10, Pin Change Interrupt source 10: The PB2 pin can serve as an external interrupt source.

• T1/CLKO/PCINT9, Bit 1

T1, Timer/Counter1 counter source.

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CLKO, Divided System Clock: The divided system clock can be output on the PB1 pin. The divided system clock will be output if the CKOUT Fuse is programmed, regardless of the

PORTB1 and DDB1 settings. It will also be output during reset.

PCINT9, Pin Change Interrupt source 9: The PB1 pin can serve as an external interrupt source.

• T0/XCK0/PCINT8, Bit 0

T0, Timer/Counter0 counter source.

XCK0, USART0 External clock. The Data Direction Register (DDB0) controls whether the clock is output (DDD0 set “one”) or input (DDD0 cleared). The XCK0 pin is active only when the

USART0 operates in Synchronous mode.

PCINT8, Pin Change Interrupt source 8: The PB0 pin can serve as an external interrupt source.

Table 14-7

and

Table 14-8 relate the alternate functions of Port B to the overriding signals

shown in

Figure 14-5 on page 78

. SPI MSTR INPUT and SPI SLAVE OUTPUT constitute the

MISO signal, while MOSI is divided into SPI MSTR OUTPUT and SPI SLAVE INPUT.

Table 14-7.

Overriding Signals for Alternate Functions in PB7:PB4.

Signal name

PUOE

PUOV

DDOE

DDOV

PVOE

PVOV

DIEOE

DIEOV

DI

AIO

PB7/SCK/

PCINT15

SPE • MSTR

PORTB7 • PUD

SPE • MSTR

0

SPE • MSTR

SCK OUTPUT

PCINT15 • PCIE1

1

SCK INPUT

PCINT17 INPUT

PB6/MISO/

PCINT14

SPE • MSTR

PORTB14 • PUD

SPE • MSTR

0

SPE • MSTR

SPI SLAVE

OUTPUT

PCINT14 • PCIE1

1

SPI MSTR INPUT

PCINT14 INPUT

PB5/MOSI/

PCINT13

SPE • MSTR

PORTB13 • PUD

SPE • MSTR

0

SPE • MSTR

PB4/SS/OC0B/

PCINT12

SPE • MSTR

PORTB12 • PUD

SPE • MSTR

0

OC0A ENABLE

SPI MSTR OUTPUT OC0A

PCINT13 • PCIE1

1

SPI SLAVE INPUT

PCINT13 INPUT

PCINT12 • PCIE1

1

SPI SS

PCINT12 INPUT

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14.3.3

Table 14-8.

Overriding Signals for Alternate Functions in PB3:PB0.

Signal name

PUOE

PUOV

DDOE

DDOV

PVOE

PVOV

DIEOE

DIEOV

DI

AIO

0

0

PB3/AIN1/OC0B/

PCINT11

0

0

OC0B ENABLE

OC0B

PCINT11 • PCIE1

1

PCINT11 INPUT

AIN1 INPUT

Alternate Functions of Port C

0

0

PB2/AIN0/INT2/

PCINT10

0

0

0

0

INT2 ENABLE

PCINT10 • PCIE1

1

INT2 INPUT

PCINT10 INPUT

AIN0 INPUT

0

0

PB1/T1/CLKO/PCIN

T9

CKOUT

CKOUT

CKOUT

CLK I/O

PCINT9 • PCIE1

1

T1 INPUT

PCINT9 INPUT

The Port C pins with alternate functions are shown in Table 14-9

.

0

0

0

0

0

0

PB0/T0/XCK/

PCINT8

PCINT8 • PCIE1

1

T0 INPUT

PCINT8 INPUT

Table 14-9.

Port C pins alternate functions.

Port pin Alternate function

PC7

TOSC2 (Timer Oscillator pin 2)

PCINT23 (Pin Change Interrupt 23)

PC6

PC5

TOSC1 (Timer Oscillator pin 1)

PCINT22 (Pin Change Interrupt 22)

TDI (JTAG Test Data Input)

PCINT21 (Pin Change Interrupt 21)

PC4

PC3

PC2

PC1

PC0

TDO (JTAG Test Data Output)

PCINT20 (Pin Change Interrupt 20)

TMS (JTAG Test Mode Select)

PCINT19 (Pin Change Interrupt 19)

TCK (JTAG Test Clock)

PCINT18 (Pin Change Interrupt 18)

SDA (two-wire Serial Bus Data Input/Output Line)

PCINT17 (Pin Change Interrupt 17)

SCL (two-wire Serial Bus Clock Line)

PCINT16 (Pin Change Interrupt 16)

• TOSC2/PCINT23 – Port C, Bit7

TOSC2, Timer Oscillator pin 2. The PC7 pin can serve as an external interrupt source to the

MCU.

PCINT23, Pin Change Interrupt source 23: The PC7 pin can serve as an external interrupt source.

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• TOSC1/PCINT22 – Port C, Bit 6

TOSC1, Timer Oscillator pin 1. The PC6 pin can serve as an external interrupt source to the

MCU.

PCINT22, Pin Change Interrupt source 22: The PC6 pin can serve as an external interrupt source.

• TDI/PCINT21 – Port C, Bit 5

TDI, JTAG Test Data Input.

PCINT21, Pin Change Interrupt source 21: The PC5 pin can serve as an external interrupt source.

• TDO/PCINT20 – Port C, Bit 4

TDO, JTAG Test Data Output.

PCINT20, Pin Change Interrupt source 20: The PC4 pin can serve as an external interrupt source.

• TMS/PCINT19 – Port C, Bit 3

TMS, JTAG Test Mode Select.

PCINT19, Pin Change Interrupt source 19: The PC3 pin can serve as an external interrupt source.

• TCK/PCINT18 – Port C, Bit 2

TCK, JTAG Test Clock.

PCINT18, Pin Change Interrupt source 18: The PC2 pin can serve as an external interrupt source.

• SDA/PCINT17 – Port C, Bit 1

SDA, two-wire Serial Bus Data Input/Output Line.

PCINT17, Pin Change Interrupt source 17: The PC1 pin can serve as an external interrupt source.

• SCL/PCINT16 – Port C, Bit 0

SCL, two-wire Serial Bus Clock Line.

PCINT16, Pin Change Interrupt source 16: The PC0 pin can serve as an external interrupt source.

Table 14-10 and Table 14-11 relate the alternate functions of Port C to the overriding signals

shown in

Figure 14-5 on page 78 .

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Table 14-10.

Overriding Signals for Alternate Functions in PC7:PC4.

Signal name

PUOE

PUOV

DDOE

PC7/TOSC2/

PCINT23

AS2 • EXCLK

0

AS2 • EXCLK

PC6/TOSC1/

PCINT22

AS2

0

AS2

PC5/TDI/

PCINT21

JTAGEN

1

JTAGEN

DDOV 0 0 0

PVOE

PVOV

DIEOE

DIEOV

DI

AIO

0

0

AS2 • EXCLK +

PCINT23 • PCIE2

AS2

PCINT23 INPUT

T/C2 OSC OUTPUT

0

0

AS2 +

PCINT22 • PCIE2

EXCLK + AS2

PCINT22 INPUT

T/C2 OSC

INPUT

0

0

JTAGEN +

PCINT21 • PCIE2

JTAGEN

PCINT21 INPUT

TDI INPUT

PC4/TDO/

PCINT20

JTAGEN

1

JTAGEN

SHIFT_IR +

SHIFT_DR

JTAGEN

TDO

JTAGEN +

PCINT20 • PCIE2

JTAGEN

PCINT20 INPUT

Table 14-11.

Overriding Signals for Alternate Functions in PC3:PC0.

Signal name

PUOE

PUOV

DDOE

DDOV

PVOE

PVOV

DIEOE

DIEOV

DI

AIO

PC3/TMS/

PCINT19

JTAGEN

0

0

1

JTAGEN

0

JTAGEN +

PCINT19 • PCIE2

JTAGEN

PCINT19 INPUT

TMS INPUT

PC2/TCK/

PCINT18

JTAGEN

0

0

1

JTAGEN

0

JTAGEN +

PCINT18 • PCIE2

JTAGEN

PCINT18 INPUT

TCK INPUT

PC1/SDA/

PCINT17

TWEN

PORTC1 • PUD

TWEN

0

TWEN

SDA OUT

PCINT17 • PCIE2

1

PCINT17 INPUT

SDA INPUT

PC0/SCL/

PCINT16

TWEN

PORTC0 • PUD

TWEN

0

TWEN

SCL OUT

PCINT16 • PCIE2

1

PCINT16 INPUT

SCL INPUT

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14.3.4

Alternate Functions of Port D

The Port D pins with alternate functions are shown in Table 14-12

.

Table 14-12.

Port D pins alternate functions.

Port pin

PD7

PD6

PD5

PD4

PD3

PD2

PD1

PD0

Alternate function

OC2A (Timer/Counter2 Output Compare Match A Output)

PCINT31 (Pin Change Interrupt 31)

ICP1 (Timer/Counter1 Input Capture Trigger)

OC2B (Timer/Counter2 Output Compare Match B Output)

PCINT30 (Pin Change Interrupt 30)

OC1A (Timer/Counter1 Output Compare Match A Output)

PCINT29 (Pin Change Interrupt 29)

OC1B (Timer/Counter1 Output Compare Match B Output)

XCK1 (USART1 External Clock Input/Output)

PCINT28 (Pin Change Interrupt 28)

INT1 (External Interrupt1 Input)

TXD1 (USART1 Transmit Pin)

PCINT27 (Pin Change Interrupt 27)

INT0 (External Interrupt0 Input)

RXD1 (USART1 Receive Pin)

PCINT26 (Pin Change Interrupt 26)

TXD0 (USART0 Transmit Pin)

PCINT25 (Pin Change Interrupt 25)

RXD0 (USART0 Receive Pin)

PCINT24 (Pin Change Interrupt 24)

T3 (Timer/Counter 3 External Counter Input)

The alternate pin configuration is as follows:

• OC2A/PCINT31 – Port D, Bit 7

OC2A, Output Compare Match A output: The PD7 pin can serve as an external output for the

Timer/Counter2 Output Compare A. The pin has to be configured as an output (DDD7 set (one)) to serve this function. The OC2A pin is also the output pin for the PWM mode timer function.

PCINT31, Pin Change Interrupt Source 31:The PD7 pin can serve as an external interrupt source.

• ICP1/OC2B/PCINT30 – Port D, Bit 6

ICP1, Input Capture Pin 1: The PD6 pin can act as an input capture pin for Timer/Counter1.

OC2B, Output Compare Match B output: The PD6 pin can serve as an external output for the

Timer/Counter2 Output Compare B. The pin has to be configured as an output (DDD6 set (one)) to serve this function. The OC2B pin is also the output pin for the PWM mode timer function.

PCINT30, Pin Change Interrupt Source 30: The PD6 pin can serve as an external interrupt source.

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• OC1A/PCINT29 – Port D, Bit 5

OC1A, Output Compare Match A output: The PD5 pin can serve as an external output for the

Timer/Counter1 Output Compare A. The pin has to be configured as an output (DDD5 set (one)) to serve this function. The OC1A pin is also the output pin for the PWM mode timer function.

PCINT29, Pin Change Interrupt Source 29: The PD5 pin can serve as an external interrupt source.

• OC1B/XCK1/PCINT28 – Port D, Bit 4

OC1B, Output Compare Match B output: The PB4 pin can serve as an external output for the

Timer/Counter1 Output Compare B. The pin has to be configured as an output (DDD4 set (one)) to serve this function. The OC1B pin is also the output pin for the PWM mode timer function.

XCK1, USART1 External clock. The Data Direction Register (DDB4) controls whether the clock is output (DDD4 set “one”) or input (DDD4 cleared). The XCK4 pin is active only when the

USART1 operates in Synchronous mode.

PCINT28, Pin Change Interrupt Source 28: The PD4 pin can serve as an external interrupt source.

• INT1/TXD1/PCINT27 – Port D, Bit 3

INT1, External Interrupt source 1. The PD3 pin can serve as an external interrupt source to the

MCU.

TXD1, Transmit Data (Data output pin for the USART1). When the USART1 Transmitter is enabled, this pin is configured as an output regardless of the value of DDD3.

PCINT27, Pin Change Interrupt Source 27: The PD3 pin can serve as an external interrupt source.

• INT0/RXD1/PCINT26 – Port D, Bit 2

INT0, External Interrupt source 0. The PD2 pin can serve as an external interrupt source to the

MCU.

RXD1, RXD0, Receive Data (Data input pin for the USART1). When the USART1 receiver is enabled this pin is configured as an input regardless of the value of DDD2. When the USART forces this pin to be an input, the pull-up can still be controlled by the PORTD2 bit.

PCINT26, Pin Change Interrupt Source 26: The PD2 pin can serve as an external interrupt source.

• TXD0/PCINT25 – Port D, Bit 1

TXD0, Transmit Data (Data output pin for the USART0). When the USART0 Transmitter is enabled, this pin is configured as an output regardless of the value of DDD1.

PCINT25, Pin Change Interrupt Source 25: The PD1 pin can serve as an external interrupt source.

• RXD0/T3/PCINT24 – Port D, Bit 0

RXD0, Receive Data (Data input pin for the USART0). When the USART0 receiver is enabled this pin is configured as an input regardless of the value of DDD0. When the USART forces this pin to be an input, the pull-up can still be controlled by the PORTD0 bit.

T3, Timer/Counter3 counter source.

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PCINT24, Pin Change Interrupt Source 24: The PD0 pin can serve as an external interrupt source.

Table 14-13 on page 90 and Table 14-14 on page 90

relate the alternate functions of Port D to the overriding signals shown in

Figure 14-5 on page 78

.

Table 14-13.

Overriding Signals for Alternate Functions PD7:PD4.

Signal name

PUOE

PUOV

DDOE

DDOV

PVOE

PVOV

DIEOE

DIEOV

DI

AIO

PD7/OC2A/

PCINT31

0

0

0

0

OC2A ENABLE

PD6/ICP1/

OC2B/

PCINT30

0

0

0

0

OC2B ENABLE

PD5/OC1A/

PCINT29

0

0

0

0

OC1A ENABLE

PD4/OC1B/XCK1/

PCINT28

0

0

0

0

OC1B ENABLE

OCA2A OC2B OC1A OC1B

PCINT31 • PCIE3 PCINT30 • PCIE3 PCINT29 • PCIE3 PCINT28 • PCIE3

1 1 1

PCINT31 INPUT

1

ICP1 INPUT

PCINT30 INPUT

PCINT29 INPUT

PCINT28 INPUT

Table 14-14.

Overriding Signals for Alternate Functions in PD3:PD0

(1)

.

Signal name

PUOE

PUOV

PD3/INT1/TXD1/

PCINT27

TXEN1

0

PD2/INT0/RXD1/

PCINT26

RXEN1

PORTD2 • PUD

PD1/TXD0/

PCINT25

TXEN0

0

PD0/RXD0/

PCINT27

RXEN1

PORTD0 • PUD

DDOE

DDOV

PVOE

PVOV

TXEN1

1

TXEN1

TXD1

0

0

RXEN1

0

INT2 ENABLE

PCINT26 • PCIE3

TXEN0

1

TXEN0

TXD0

RXEN1

0

0

0

DIEOE

INT1 ENABLE

PCINT27 • PCIE3

1

PCINT25 • PCIE3 PCINT24 • PCIE3

DIEOV

DI

INT1 INPUT

PCINT27 INPUT

1

INT0 INPUT

RXD1

PCINT26 INPUT

1

PCINT25 INPUT

1

RXD0

PCINT24 INPUT

AIO – – – –

Note: 1. When enabled, the two-wire Serial Interface enables Slew-Rate controls on the output pins

PD0 and PD1. This is not shown in this table. In addition, spike filters are connected between the AIO outputs shown in the port figure and the digital logic of the TWI module.

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Register description

14.3.5

MCUCR – MCU Control Register

14.3.6

Bit

0x35 (0x55)

Read/Write

Initial Value

7

JTD

R/W

0

6

BODS

(1)

R/W

0

5

BODSE

(1)

R/W

0

4

PUD

R/W

0

3

R

0

2

R

0

Note: 1. Only available in the Atmel ATmega164PA/324PA/644PA/1284P.

1

IVSEL

R/W

0

0

IVCE

R/W

0

MCUCR

• Bit 4 – PUD: Pull-up Disable

When this bit is written to one, the pull-ups in the I/O ports are disabled even if the DDxn and

PORTxn Registers are configured to enable the pull-ups ({DDxn, PORTxn} = 0b01). See ”Configuring the Pin” on page 73 for more details about this feature.

PORTA – Port A Data Register

Bit

0x02 (0x22)

Read/Write

Initial Value

7

PORTA7

R/W

0

DDRA – Port A Data Direction Register

6

PORTA6

R/W

0

5

PORTA5

R/W

0

4

PORTA4

R/W

0

3

PORTA3

R/W

0

2

PORTA2

R/W

0

1

PORTA1

R/W

0

0

PORTA0

R/W

0

PORTA

14.3.7

14.3.8

14.3.9

Bit

0x01 (0x21)

Read/Write

Initial Value

7

DDA7

R/W

0

PINA – Port A Input Pins Address

Bit

0x00 (0x20)

Read/Write

Initial Value

PORTB – Port B Data Register

7

PINA7

R/W

N/A

6

DDA6

R/W

0

6

PINA6

R/W

N/A

Bit

0x04 (0x24)

Read/Write

Initial Value

7

DDB7

R/W

0

14.3.11

PINB – Port B Input Pins Address

Bit

0x03 (0x23)

Read/Write

Initial Value

7

PINB7

R/W

N/A

6

DDB6

R/W

0

6

PINB6

R/W

N/A

5

DDA5

R/W

0

5

PINA5

R/W

N/A

Bit

0x05 (0x25)

Read/Write

Initial Value

7

PORTB7

R/W

0

14.3.10

DDRB – Port B Data Direction Register

6

PORTB6

R/W

0

5

PORTB5

R/W

0

4

PORTB4

R/W

0

3

PORTB3

R/W

0

2

PORTB2

R/W

0

1

PORTB1

R/W

0

0

PORTB0

R/W

0

5

DDB5

R/W

0

5

PINB5

R/W

N/A

4

DDA4

R/W

0

4

PINA4

R/W

N/A

4

DDB4

R/W

0

4

PINB4

R/W

N/A

3

DDA3

R/W

0

3

PINA3

R/W

N/A

3

DDB3

R/W

0

3

PINB3

R/W

N/A

2

DDA2

R/W

0

2

PINA2

R/W

N/A

2

DDB2

R/W

0

2

PINB2

R/W

N/A

1

DDA1

R/W

0

1

PINA1

R/W

N/A

1

DDB1

R/W

0

1

PINB1

R/W

N/A

0

DDA0

R/W

0

0

PINA0

R/W

N/A

0

DDB0

R/W

0

0

PINB0

R/W

N/A

DDRA

PINA

PORTB

DDRB

PINB

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14.3.12

PORTC – Port C Data Register

Bit

0x08 (0x28)

Read/Write

Initial Value

7

PORTC7

R/W

0

14.3.13

DDRC – Port C Data Direction Register

6

PORTC6

R/W

0

5

PORTC5

R/W

0

4

PORTC4

R/W

0

3

PORTC3

R/W

0

2

PORTC2

R/W

0

1

PORTC1

R/W

0

0

PORTC0

R/W

0

Bit

0x07 (0x27)

Read/Write

Initial Value

7

DDC7

R/W

0

14.3.14

PINC – Port C Input Pins Address

6

DDC6

R/W

0

5

DDC5

R/W

0

4

DDC4

R/W

0

3

DDC3

R/W

0

2

DDC2

R/W

0

1

DDC1

R/W

0

0

DDC0

R/W

0

PORTC

DDRC

Bit

0x06 (0x26)

Read/Write

Initial Value

14.3.15

PORTD – Port D Data Register

7

PINC7

R/W

N/A

Bit

0x0A (0x2A)

Read/Write

Initial Value

7

DDD7

R/W

0

14.3.17

PIND – Port D Input Pins Address

Bit

0x09 (0x29)

Read/Write

Initial Value

7

PIND7

R/W

N/A

6

PINC6

R/W

N/A

6

DDD6

R/W

0

6

PIND6

R/W

N/A

5

PINC5

R/W

N/A

5

DDD5

R/W

0

5

PIND5

R/W

N/A

4

PINC4

R/W

N/A

4

DDD4

R/W

0

4

PIND4

R/W

N/A

3

PINC3

R/W

N/A

3

DDD3

R/W

0

3

PIND3

R/W

N/A

2

PINC2

R/W

N/A

2

DDD2

R/W

0

2

PIND2

R/W

N/A

1

PINC1

R/W

N/A

0

PINC0

R/W

N/A

Bit

0x0B (0x2B)

Read/Write

Initial Value

7

PORTD7

R/W

0

14.3.16

DDRD – Port D Data Direction Register

6

PORTD6

R/W

0

5

PORTD5

R/W

0

4

PORTD4

R/W

0

3

PORTD3

R/W

0

2

PORTD2

R/W

0

1

PORTD1

R/W

0

0

PORTD0

R/W

0

1

DDD1

R/W

0

1

PIND1

R/W

N/A

0

DDD0

R/W

0

0

PIND0

R/W

N/A

PINC

PORTD

DDRD

PIND

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15. 8-bit Timer/Counter0 with PWM

15.1

Features

Two independent output compare units

Double buffered output compare registers

Clear timer on compare match (auto reload)

Glitch free, phase correct Pulse Width Modulator (PWM)

Variable PWM Period

Frequency generator

Three independent interrupt sources (TOV0, OCF0A, and OCF0B)

15.2

Overview

Timer/Counter0 is a general purpose 8-bit Timer/Counter module, with two independent Output

Compare Units, and with PWM support. It allows accurate program execution timing (event management) and wave generation.

A simplified block diagram of the 8-bit Timer/Counter is shown in

Figure 15-1

. For the actual

placement of I/O pins, see ”Pin configurations” on page 2 . CPU accessible I/O Registers, includ-

ing I/O bits and I/O pins, are shown in bold. The device-specific I/O Register and bit locations

are listed in the ”Register description” on page 104

.

Figure 15-1.

8-bit Timer/Counter block diagram.

Count

Clear

Direction

Control Logic clk

Tn

TOVn

(Int.Req.)

Clock Select

Edge

Detector

Tn

TOP BOTTOM

( From Prescaler )

Timer/Counter

TCNTn

= =

0

=

OCnA

(Int.Req.)

Waveform

Generation

OCnA

OCRnA

=

OCRnB

Fixed

TOP

Value

OCnB

(Int.Req.)

Waveform

Generation

OCnB

TCCRnA TCCRnB

15.2.1

Registers

The Timer/Counter (TCNT0) and Output Compare Registers (OCR0A and OCR0B) are 8-bit registers. Interrupt request (abbreviated to Int.Req. in the figure) signals are all visible in the

Timer Interrupt Flag Register (TIFR0). All interrupts are individually masked with the Timer Interrupt Mask Register (TIMSK0). TIFR0 and TIMSK0 are not shown in the figure.

The Timer/Counter can be clocked internally, via the prescaler, or by an external clock source on the T0 pin. The Clock Select logic block controls which clock source and edge the Timer/Counter

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uses to increment (or decrement) its value. The Timer/Counter is inactive when no clock source is selected. The output from the Clock Select logic is referred to as the timer clock (clk

T0

).

The double buffered Output Compare Registers (OCR0A and OCR0B) are compared with the

Timer/Counter value at all times. The result of the compare can be used by the Waveform Generator to generate a PWM or variable frequency output on the Output Compare pins (OC0A and

OC0B).

See Section “15.5” on page 95

for details. The Compare Match event will also set the

Compare Flag (OCF0A or OCF0B) which can be used to generate an Output Compare interrupt request.

15.2.2

Definitions

Many register and bit references in this section are written in general form. A lower case “n” replaces the Timer/Counter number, in this case 0. A lower case “x” replaces the Output Compare Unit, in this case Compare Unit A or Compare Unit B. However, when using the register or bit defines in a program, the precise form must be used, that is, TCNT0 for accessing

Timer/Counter0 counter value and so on.

The definitions in Table 15-1 are also used extensively throughout the document.

Table 15-1.

Definitions.

BOTTOM The counter reaches the BOTTOM when it becomes 0x00.

MAX

TOP

The counter reaches its MAXimum when it becomes 0xFF (decimal 255).

The counter reaches the TOP when it becomes equal to the highest value in the count sequence. The TOP value can be assigned to be the fixed value 0xFF

(MAX) or the value stored in the OCR0A Register. The assignment is dependent on the mode of operation.

15.3

Timer/Counter Clock Sources

The Timer/Counter can be clocked by an internal or an external clock source. The clock source is selected by the Clock Select logic which is controlled by the Clock Select (CS02:0) bits located in the Timer/Counter Control Register (TCCR0B). For details on clock sources and prescaler, see

”Timer/Counter Prescaler” on page 155

.

15.4

Counter Unit

The main part of the 8-bit Timer/Counter is the programmable bi-directional counter unit.

Figure

15-2

shows a block diagram of the counter and its surroundings.

Figure 15-2.

Counter Unit block diagram.

DATA BUS

TOVn

(Int.Req.)

TCNTn

count clear direction

Control Logic clk

Tn

Clock Select

Edge

Detector

Tn

( From Prescaler ) bottom top

Signal description (internal signals):

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T

n

top

Increment or decrement TCNT0 by 1.

Select between increment and decrement.

Clear TCNT0 (set all bits to zero).

Timer/Counter clock, referred to as clk

T0

in the following.

Signalize that TCNT0 has reached maximum value.

bottom

Signalize that TCNT0 has reached minimum value (zero).

Depending of the mode of operation used, the counter is cleared, incremented, or decremented at each timer clock (clk

T0

). clk

T0

can be generated from an external or internal clock source, selected by the Clock Select bits (CS02:0). When no clock source is selected (CS02:0 = 0) the timer is stopped. However, the TCNT0 value can be accessed by the CPU, regardless of whether clk

T0

is present or not. A CPU write overrides (has priority over) all counter clear or count operations.

The counting sequence is determined by the setting of the WGM01 and WGM00 bits located in the Timer/Counter Control Register (TCCR0A) and the WGM02 bit located in the Timer/Counter

Control Register B (TCCR0B). There are close connections between how the counter behaves

(counts) and how waveforms are generated on the Output Compare outputs OC0A and OC0B.

For more details about advanced counting sequences and waveform generation, see ”Modes of operation” on page 98

.

The Timer/Counter Overflow Flag (TOV0) is set according to the mode of operation selected by the WGM02:0 bits. TOV0 can be used for generating a CPU interrupt.

15.5

Output Compare unit

The 8-bit comparator continuously compares TCNT0 with the Output Compare Registers

(OCR0A and OCR0B). Whenever TCNT0 equals OCR0A or OCR0B, the comparator signals a match. A match will set the Output Compare Flag (OCF0A or OCF0B) at the next timer clock cycle. If the corresponding interrupt is enabled, the Output Compare Flag generates an Output

Compare interrupt. The Output Compare Flag is automatically cleared when the interrupt is executed. Alternatively, the flag can be cleared by software by writing a logical one to its I/O bit location. The Waveform Generator uses the match signal to generate an output according to operating mode set by the WGM02:0 bits and Compare Output mode (COM0x1:0) bits. The max and bottom signals are used by the Waveform Generator for handling the special cases of the

extreme values in some modes of operation ( ”Modes of operation” on page 98

).

Figure 15-3

shows a block diagram of the Output Compare unit.

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Figure 15-3.

Output Compare unit, block diagram.

DATA BUS

OCRnx TCNTn

=

(8-bit Comparator )

OCFn

x (Int.Req.) top bottom

FOCn

Waveform Generator

OCnx

WGMn1:0 COMnX1:0

15.5.1

15.5.2

15.5.3

The OCR0x Registers are double buffered when using any of the Pulse Width Modulation

(PWM) modes. For the normal and Clear Timer on Compare (CTC) modes of operation, the double buffering is disabled. The double buffering synchronizes the update of the OCR0x Compare

Registers to either top or bottom of the counting sequence. The synchronization prevents the occurrence of odd-length, non-symmetrical PWM pulses, thereby making the output glitch-free.

The OCR0x Register access may seem complex, but this is not case. When the double buffering is enabled, the CPU has access to the OCR0x Buffer Register, and if double buffering is disabled the CPU will access the OCR0x directly.

Force Output Compare

In non-PWM waveform generation modes, the match output of the comparator can be forced by writing a one to the Force Output Compare (FOC0x) bit. Forcing Compare Match will not set the

OCF0x Flag or reload/clear the timer, but the OC0x pin will be updated as if a real Compare

Match had occurred (the COM0x1:0 bits settings define whether the OC0x pin is set, cleared or toggled).

Compare Match Blocking by TCNT0 Write

All CPU write operations to the TCNT0 Register will block any Compare Match that occur in the next timer clock cycle, even when the timer is stopped. This feature allows OCR0x to be initialized to the same value as TCNT0 without triggering an interrupt when the Timer/Counter clock is enabled.

Using the Output Compare Unit

Since writing TCNT0 in any mode of operation will block all Compare Matches for one timer clock cycle, there are risks involved when changing TCNT0 when using the Output Compare

Unit, independently of whether the Timer/Counter is running or not. If the value written to TCNT0 equals the OCR0x value, the Compare Match will be missed, resulting in incorrect waveform

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generation. Similarly, do not write the TCNT0 value equal to BOTTOM when the counter is down-counting.

The setup of the OC0x should be performed before setting the Data Direction Register for the port pin to output. The easiest way of setting the OC0x value is to use the Force Output Compare (FOC0x) strobe bits in Normal mode. The OC0x Registers keep their values even when changing between Waveform Generation modes.

Be aware that the COM0x1:0 bits are not double buffered together with the compare value.

Changing the COM0x1:0 bits will take effect immediately.

15.6

Compare Match Output unit

The Compare Output mode (COM0x1:0) bits have two functions. The Waveform Generator uses the COM0x1:0 bits for defining the Output Compare (OC0x) state at the next Compare Match.

Also, the COM0x1:0 bits control the OC0x pin output source. Figure 15-4 shows a simplified

schematic of the logic affected by the COM0x1:0 bit setting. The I/O Registers, I/O bits, and I/O pins in the figure are shown in bold. Only the parts of the general I/O Port Control Registers

(DDR and PORT) that are affected by the COM0x1:0 bits are shown. When referring to the

OC0x state, the reference is for the internal OC0x Register, not the OC0x pin. If a system reset occur, the OC0x Register is reset to “0”.

Figure 15-4.

Compare Match Output unit, schematic.

COMnx1

COMnx0

FOCn

Waveform

Generator

D Q

OCnx

D Q

PORT

D Q

1

0

OCnx

Pin

DDR

clk

I/O

The general I/O port function is overridden by the Output Compare (OC0x) from the Waveform

Generator if either of the COM0x1:0 bits are set. However, the OC0x pin direction (input or output) is still controlled by the Data Direction Register (DDR) for the port pin. The Data Direction

Register bit for the OC0x pin (DDR_OC0x) must be set as output before the OC0x value is visible on the pin. The port override function is independent of the Waveform Generation mode.

The design of the Output Compare pin logic allows initialization of the OC0x state before the output is enabled. Note that some COM0x1:0 bit settings are reserved for certain modes of

operation. See Section “15.9” on page 104

.

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15.6.1

Compare Output Mode and Waveform Generation

The Waveform Generator uses the COM0x1:0 bits differently in Normal, CTC, and PWM modes.

For all modes, setting the COM0x1:0 = 0 tells the Waveform Generator that no action on the

OC0x Register is to be performed on the next Compare Match. For compare output actions in the non-PWM modes refer to

Table 15-2 on page 104 . For fast PWM mode, refer to Table 15-3 on page 104 , and for phase correct PWM refer to

Table 15-4 on page 105 .

A change of the COM0x1:0 bits state will have effect at the first Compare Match after the bits are written. For non-PWM modes, the action can be forced to have immediate effect by using the

FOC0x strobe bits.

15.7

Modes of operation

15.7.1

15.7.2

The mode of operation, that is, the behavior of the Timer/Counter and the Output Compare pins, is defined by the combination of the Waveform Generation mode (WGM02:0) and Compare Output mode (COM0x1:0) bits. The Compare Output mode bits do not affect the counting sequence, while the Waveform Generation mode bits do. The COM0x1:0 bits control whether the PWM output generated should be inverted or not (inverted or non-inverted PWM). For non-PWM modes the COM0x1:0 bits control whether the output should be set, cleared, or toggled at a Compare

Match ( See Section “16.8” on page 122

).

For detailed timing information see

”Timer/Counter Timing diagrams” on page 102 .

Normal mode

The simplest mode of operation is the Normal mode (WGM02:0 = 0). In this mode the counting direction is always up (incrementing), and no counter clear is performed. The counter simply overruns when it passes its maximum 8-bit value (TOP = 0xFF) and then restarts from the bottom (0x00). In normal operation the Timer/Counter Overflow Flag (TOV0) will be set in the same timer clock cycle as the TCNT0 becomes zero. The TOV0 Flag in this case behaves like a ninth bit, except that it is only set, not cleared. However, combined with the timer overflow interrupt that automatically clears the TOV0 Flag, the timer resolution can be increased by software.

There are no special cases to consider in the Normal mode, a new counter value can be written anytime.

The Output Compare Unit can be used to generate interrupts at some given time. Using the Output Compare to generate waveforms in Normal mode is not recommended, since this will occupy too much of the CPU time.

Clear Timer on Compare Match (CTC) mode

In Clear Timer on Compare or CTC mode (WGM02:0 = 2), the OCR0A Register is used to manipulate the counter resolution. In CTC mode the counter is cleared to zero when the counter value (TCNT0) matches the OCR0A. The OCR0A defines the top value for the counter, hence also its resolution. This mode allows greater control of the Compare Match output frequency. It also simplifies the operation of counting external events.

The timing diagram for the CTC mode is shown in

Figure 15-5 . The counter value (TCNT0)

increases until a Compare Match occurs between TCNT0 and OCR0A, and then counter

(TCNT0) is cleared.

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Figure 15-5.

CTC mode, timing diagram.

OCnx Interrupt Flag Set

TCNTn

OCn

(Toggle)

Period

1 2 3 4

(COMnx1:0 = 1)

15.7.3

An interrupt can be generated each time the counter value reaches the TOP value by using the

OCF0A Flag. If the interrupt is enabled, the interrupt handler routine can be used for updating the TOP value. However, changing TOP to a value close to BOTTOM when the counter is running with none or a low prescaler value must be done with care since the CTC mode does not have the double buffering feature. If the new value written to OCR0A is lower than the current value of TCNT0, the counter will miss the Compare Match. The counter will then have to count to its maximum value (0xFF) and wrap around starting at 0x00 before the Compare Match can occur.

For generating a waveform output in CTC mode, the OC0A output can be set to toggle its logical level on each Compare Match by setting the Compare Output mode bits to toggle mode

(COM0A1:0 = 1). The OC0A value will not be visible on the port pin unless the data direction for the pin is set to output. The waveform generated will have a maximum frequency of f

OC0

= f clk_I/O

/2 when OCR0A is set to zero (0x00). The waveform frequency is defined by the following equation:

f

OCnx

=

⋅ ⋅

f

( clk_I/O

1

+

OCRnx

The N variable represents the prescale factor (1, 8, 64, 256, or 1024).

As for the Normal mode of operation, the TOV0 Flag is set in the same timer clock cycle that the counter counts from MAX to 0x00.

Fast PWM mode

The fast Pulse Width Modulation or fast PWM mode (WGM02:0 = 3 or 7) provides a high frequency PWM waveform generation option. The fast PWM differs from the other PWM option by its single-slope operation. The counter counts from BOTTOM to TOP then restarts from BOT-

TOM. TOP is defined as 0xFF when WGM2:0 = 3, and OCR0A when WGM2:0 = 7. In noninverting Compare Output mode, the Output Compare (OC0x) is cleared on the Compare Match between TCNT0 and OCR0x, and set at BOTTOM. In inverting Compare Output mode, the output is set on Compare Match and cleared at BOTTOM. Due to the single-slope operation, the operating frequency of the fast PWM mode can be twice as high as the phase correct PWM mode that use dual-slope operation. This high frequency makes the fast PWM mode well suited for power regulation, rectification, and DAC applications. High frequency allows physically small sized external components (coils, capacitors), and therefore reduces total system cost.

In fast PWM mode, the counter is incremented until the counter value matches the TOP value.

The counter is then cleared at the following timer clock cycle. The timing diagram for the fast

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PWM mode is shown in Figure 15-6

. The TCNT0 value is in the timing diagram shown as a histogram for illustrating the single-slope operation. The diagram includes non-inverted and inverted PWM outputs. The small horizontal line marks on the TCNT0 slopes represent Compare Matches between OCR0x and TCNT0.

Figure 15-6.

Fast PWM mode, timing diagram.

OCRnx Interrupt Flag Set

OCRnx Update and

TOVn Interrupt Flag Set

TCNTn

OCnx

OCnx

(COMnx1:0 = 2)

(COMnx1:0 = 3)

Period

1 2 3 4 5 6 7

The Timer/Counter Overflow Flag (TOV0) is set each time the counter reaches TOP. If the interrupt is enabled, the interrupt handler routine can be used for updating the compare value.

In fast PWM mode, the compare unit allows generation of PWM waveforms on the OC0x pins.

Setting the COM0x1:0 bits to two will produce a non-inverted PWM and an inverted PWM output can be generated by setting the COM0x1:0 to three: Setting the COM0A1:0 bits to one allows the OC0A pin to toggle on Compare Matches if the WGM02 bit is set. This option is not available for the OC0B pin (See

Table 15-3 on page 104

). The actual OC0x value will only be visible on the port pin if the data direction for the port pin is set as output. The PWM waveform is generated by setting (or clearing) the OC0x Register at the Compare Match between OCR0x and

TCNT0, and clearing (or setting) the OC0x Register at the timer clock cycle the counter is cleared (changes from TOP to BOTTOM).

The PWM frequency for the output can be calculated by the following equation:

f

OCnxPWM

=

f

clk_I/O

------------------

The N variable represents the prescale factor (1, 8, 64, 256, or 1024).

The extreme values for the OCR0A Register represents special cases when generating a PWM waveform output in the fast PWM mode. If the OCR0A is set equal to BOTTOM, the output will be a narrow spike for each MAX+1 timer clock cycle. Setting the OCR0A equal to MAX will result in a constantly high or low output (depending on the polarity of the output set by the COM0A1:0 bits.)

A frequency (with 50% duty cycle) waveform output in fast PWM mode can be achieved by setting OC0x to toggle its logical level on each Compare Match (COM0x1:0 = 1). The waveform generated will have a maximum frequency of f

OC0

= f clk_I/O

/2 when OCR0A is set to zero. This

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15.7.4

feature is similar to the OC0A toggle in CTC mode, except the double buffer feature of the Output Compare unit is enabled in the fast PWM mode.

Phase Correct PWM mode

The phase correct PWM mode (WGM02:0 = 1 or 5) provides a high resolution phase correct

PWM waveform generation option. The phase correct PWM mode is based on a dual-slope operation. The counter counts repeatedly from BOTTOM to TOP and then from TOP to BOT-

TOM. TOP is defined as 0xFF when WGM2:0 = 1, and OCR0A when WGM2:0 = 5. In noninverting Compare Output mode, the Output Compare (OC0x) is cleared on the Compare Match between TCNT0 and OCR0x while upcounting, and set on the Compare Match while downcounting. In inverting Output Compare mode, the operation is inverted. The dual-slope operation has lower maximum operation frequency than single slope operation. However, due to the symmetric feature of the dual-slope PWM modes, these modes are preferred for motor control applications.

In phase correct PWM mode the counter is incremented until the counter value matches TOP.

When the counter reaches TOP, it changes the count direction. The TCNT0 value will be equal to TOP for one timer clock cycle. The timing diagram for the phase correct PWM mode is shown on

Figure 15-7

. The TCNT0 value is in the timing diagram shown as a histogram for illustrating the dual-slope operation. The diagram includes non-inverted and inverted PWM outputs. The small horizontal line marks on the TCNT0 slopes represent Compare Matches between OCR0x and TCNT0.

Figure 15-7.

Phase Correct PWM mode, timing diagram.

OCnx Interrupt Flag Set

OCRnx Update

TOVn Interrupt Flag Set

TCNTn

OCnx

OCnx

Period

1 2 3

(COMnx1:0 = 2)

(COMnx1:0 = 3)

The Timer/Counter Overflow Flag (TOV0) is set each time the counter reaches BOTTOM. The

Interrupt Flag can be used to generate an interrupt each time the counter reaches the BOTTOM value.

In phase correct PWM mode, the compare unit allows generation of PWM waveforms on the

OC0x pins. Setting the COM0x1:0 bits to two will produce a non-inverted PWM. An inverted

PWM output can be generated by setting the COM0x1:0 to three: Setting the COM0A0 bits to

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one allows the OC0A pin to toggle on Compare Matches if the WGM02 bit is set. This option is not available for the OC0B pin (See

Table 15-4 on page 105 ). The actual OC0x value will only

be visible on the port pin if the data direction for the port pin is set as output. The PWM waveform is generated by clearing (or setting) the OC0x Register at the Compare Match between

OCR0x and TCNT0 when the counter increments, and setting (or clearing) the OC0x Register at

Compare Match between OCR0x and TCNT0 when the counter decrements. The PWM frequency for the output when using phase correct PWM can be calculated by the following equation:

f

OCnxPCPWM

=

f

clk_I/O

------------------

The N variable represents the prescale factor (1, 8, 64, 256, or 1024).

The extreme values for the OCR0A Register represent special cases when generating a PWM waveform output in the phase correct PWM mode. If the OCR0A is set equal to BOTTOM, the output will be continuously low and if set equal to MAX the output will be continuously high for non-inverted PWM mode. For inverted PWM the output will have the opposite logic values.

At the very start of period 2 in

Figure 15-7

OCnx has a transition from high to low even though there is no Compare Match. The point of this transition is to guarantee symmetry around BOT-

TOM. There are two cases that give a transition without Compare Match.

• OCR0A changes its value from MAX, like in

Figure 15-7 . When the OCR0A value is MAX the

OCn pin value is the same as the result of a down-counting Compare Match. To ensure symmetry around BOTTOM the OCn value at MAX must correspond to the result of an upcounting Compare Match.

• The timer starts counting from a value higher than the one in OCR0A, and for that reason misses the Compare Match and hence the OCn change that would have happened on the way up.

15.8

Timer/Counter Timing diagrams

The Timer/Counter is a synchronous design and the timer clock (clk

T0

) is therefore shown as a clock enable signal in the following figures. The figures include information on when Interrupt

Flags are set. Figure 15-8

contains timing data for basic Timer/Counter operation. The figure shows the count sequence close to the MAX value in all modes other than phase correct PWM mode.

Figure 15-8.

Timer/Counter Timing diagram, no prescaling.

clk

I/O clk

(clk

I/O

Tn

/1)

TCNTn

TOVn

MAX - 1 MAX BOTTOM BOTTOM + 1

Figure 15-9 on page 103 shows the same timing data, but with the prescaler enabled.

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Figure 15-9.

Timer/Counter Timing diagram, with prescaler (f clk_I/O

/8).

clk

I/O clk

(clk

I/O

Tn

/8)

TCNTn MAX - 1 MAX BOTTOM

TOVn

BOTTOM + 1

Figure 15-10

shows the setting of OCF0B in all modes and OCF0A in all modes except CTC mode and PWM mode, where OCR0A is TOP.

Figure 15-10.

Timer/Counter Timing diagram, setting of OCF0x, with prescaler (f clk_I/O

/8).

clk

I/O clk

(clk

I/O

Tn

/8)

TCNTn OCRnx - 1 OCRnx OCRnx + 1 OCRnx + 2

OCRnx Value OCRnx

OCFnx

Figure 15-11 shows the setting of OCF0A and the clearing of TCNT0 in CTC mode and fast

PWM mode where OCR0A is TOP.

Figure 15-11.

Timer/Counter Timing diagram, Clear Timer on Compare Match mode, with prescaler (f clk_I/O

/8).

clk

I/O clk

(clk

I/O

Tn

/8)

TCNTn

(CTC)

OCRnx

TOP - 1 TOP

TOP

BOTTOM BOTTOM + 1

OCFnx

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ATmega164A/PA/324A/PA/644A/PA/1284/P

15.9

Register description

15.9.1

TCCR0A – Timer/Counter Control Register A

Bit

0x24 (0x44)

Read/Write

Initial Value

7

COM0A1

R/W

0

6

COM0A0

R/W

0

5

COM0B1

R/W

0

4

COM0B0

R/W

0

3

R

0

2

R

0

1

WGM01

R/W

0

0

WGM00

R/W

0

TCCR0A

• Bits 7:6 – COM0A1:0: Compare Match Output A Mode

These bits control the Output Compare pin (OC0A) behavior. If one or both of the COM0A1:0 bits are set, the OC0A output overrides the normal port functionality of the I/O pin it is connected to. However, note that the Data Direction Register (DDR) bit corresponding to the OC0A pin must be set in order to enable the output driver.

When OC0A is connected to the pin, the function of the COM0A1:0 bits depends on the

WGM02:0 bit setting.

Table 15-2 shows the COM0A1:0 bit functionality when the WGM02:0 bits

are set to a normal or CTC mode (non-PWM).

Table 15-2.

Compare Output mode, non-PWM mode.

COM0A1

0

0

1

1

COM0A0

0

1

0

1

Description

Normal port operation, OC0A disconnected

Toggle OC0A on Compare Match

Clear OC0A on Compare Match

Set OC0A on Compare Match

Table 15-3 shows the COM0A1:0 bit functionality when the WGM01:0 bits are set to fast PWM

mode.

Table 15-3.

Compare Output mode, Fast PWM mode

(1)

.

COM0A1

0

0

1

1

COM0A0

0

1

0

1

Description

Normal port operation, OC0A disconnected.

WGM02 = 0: Normal Port Operation, OC0A Disconnected.

WGM02 = 1: Toggle OC0A on Compare Match.

Clear OC0A on Compare Match, set OC0A at BOTTOM,

(non-inverting mode).

Set OC0A on Compare Match, clear OC0A at BOTTOM,

(inverting mode).

Note: 1. A special case occurs when OCR0A equals TOP and COM0A1 is set. In this case, the Com-

pare Match is ignored, but the set or clear is done at BOTTOM. See ”Fast PWM mode” on page 99 for more details.

Table 15-4 on page 105 shows the COM0A1:0 bit functionality when the WGM02:0 bits are set

to phase correct PWM mode.

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Table 15-4.

Compare Output mode, Phase Correct PWM mode

(1)

.

COM0A1

0

0

1

1

COM0A0

0

1

0

1

Description

Normal port operation, OC0A disconnected.

WGM02 = 0: Normal Port Operation, OC0A Disconnected.

WGM02 = 1: Toggle OC0A on Compare Match.

Clear OC0A on Compare Match when up-counting. Set OC0A on

Compare Match when down-counting.

Set OC0A on Compare Match when up-counting. Clear OC0A on

Compare Match when down-counting.

Note: 1. A special case occurs when OCR0A equals TOP and COM0A1 is set. In this case, the Com-

pare Match is ignored, but the set or clear is done at TOP. See ”Phase Correct PWM mode” on page 101

for more details.

• Bits 5:4 – COM0B1:0: Compare Match Output B mode

These bits control the Output Compare pin (OC0B) behavior. If one or both of the COM0B1:0 bits are set, the OC0B output overrides the normal port functionality of the I/O pin it is connected to. However, note that the Data Direction Register (DDR) bit corresponding to the OC0B pin must be set in order to enable the output driver.

When OC0B is connected to the pin, the function of the COM0B1:0 bits depends on the

WGM02:0 bit setting. Table 15-2 on page 104

shows the COM0A1:0 bit functionality when the

WGM02:0 bits are set to a normal or CTC mode (non-PWM).

Table 15-5.

Compare Output mode, non-PWM mode.

COM0B1

0

0

1

1

COM0B0

0

1

0

1

Description

Normal port operation, OC0B disconnected.

Toggle OC0B on Compare Match

Clear OC0B on Compare Match

Set OC0B on Compare Match

Table 15-6 shows the COM0B1:0 bit functionality when the WGM02:0 bits are set to fast PWM

mode.

Table 15-6.

Compare Output mode, Fast PWM mode

(1)

.

COM0B1

0

0

1

1

COM0B0

0

1

0

1

Description

Normal port operation, OC0B disconnected.

Reserved

Clear OC0B on Compare Match, set OC0B at BOTTOM,

(non-inverting mode).

Set OC0B on Compare Match, clear OC0B at BOTTOM,

(inverting mode).

Note: 1. A special case occurs when OCR0B equals TOP and COM0B1 is set. In this case, the Compare Match is ignored, but the set or clear is done atBOTTOM. See

”Fast PWM mode” on page

99 for more details.

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Table 15-7 on page 106 shows the COM0B1:0 bit functionality when the WGM02:0 bits are set

to phase correct PWM mode.

Table 15-7.

Compare Output mode, Phase Correct PWM mode

(1)

.

COM0B1

0

0

1

1

COM0B0

0

1

0

1

Description

Normal port operation, OC0B disconnected.

Reserved

Clear OC0B on Compare Match when up-counting. Set OC0B on

Compare Match when down-counting.

Set OC0B on Compare Match when up-counting. Clear OC0B on

Compare Match when down-counting.

Note: 1. A special case occurs when OCR0B equals TOP and COM0B1 is set. In this case, the Com-

pare Match is ignored, but the set or clear is done at TOP. See ”Phase Correct PWM mode” on page 101

for more details.

• Bits 3:2 – Reserved

These bits are reserved bits in the Atmel

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P and will always read as zero.

• Bits 1:0 – WGM01:0: Waveform Generation mode

Combined with the WGM02 bit found in the TCCR0B Register, these bits control the counting sequence of the counter, the source for maximum (TOP) counter value, and what type of waveform generation to be used, see

Table 15-8 on page 106 . Modes of operation supported by the

Timer/Counter unit are: Normal mode (counter), Clear Timer on Compare Match (CTC) mode, and two types of Pulse Width Modulation (PWM) modes (see

”Modes of Operation” on page

123 ).

Table 15-8.

Waveform Generation mode bit description.

Mode WGM2 WGM1 WGM0

0 0 0 0

1

2

3

4

5

6

7

0

0

0

1

1

1

1

0

1

1

0

0

1

1

1

0

1

0

1

0

1

Timer/Counter mode of operation

Normal

PWM, Phase

Correct

CTC

Fast PWM

Reserved

PWM, Phase

Correct

Reserved

Fast PWM

TOP

0xFF

0xFF

OCRA

0xFF

OCRA

OCRA

Notes: 1. MAX = 0xFF

2. BOTTOM = 0x00

Update of

OCRx at

Immediate

TOP

Immediate

BOTTOM

TOP

BOTTOM

TOV Flag set on

(1)(2)

MAX

BOTTOM

MAX

MAX

BOTTOM

TOP

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15.9.2

TCCR0B – Timer/Counter Control Register B

Bit

0x25 (0x45)

Read/Write

Initial Value

7

FOC0A

W

0

6

FOC0B

W

0

5

R

0

4

R

0

3

WGM02

R/W

0

2

CS02

R/W

0

1

CS01

R/W

0

0

CS00

R/W

0

TCCR0B

• Bit 7 – FOC0A: Force Output Compare A

The FOC0A bit is only active when the WGM bits specify a non-PWM mode.

However, for ensuring compatibility with future devices, this bit must be set to zero when

TCCR0B is written when operating in PWM mode. When writing a logical one to the FOC0A bit, an immediate Compare Match is forced on the Waveform Generation unit. The OC0A output is changed according to its COM0A1:0 bits setting. Note that the FOC0A bit is implemented as a strobe. Therefore it is the value present in the COM0A1:0 bits that determines the effect of the forced compare.

A FOC0A strobe will not generate any interrupt, nor will it clear the timer in CTC mode using

OCR0A as TOP.

The FOC0A bit is always read as zero.

• Bit 6 – FOC0B: Force Output Compare B

The FOC0B bit is only active when the WGM bits specify a non-PWM mode.

However, for ensuring compatibility with future devices, this bit must be set to zero when

TCCR0B is written when operating in PWM mode. When writing a logical one to the FOC0B bit, an immediate Compare Match is forced on the Waveform Generation unit. The OC0B output is changed according to its COM0B1:0 bits setting. Note that the FOC0B bit is implemented as a strobe. Therefore it is the value present in the COM0B1:0 bits that determines the effect of the forced compare.

A FOC0B strobe will not generate any interrupt, nor will it clear the timer in CTC mode using

OCR0B as TOP.

The FOC0B bit is always read as zero.

• Bits 5:4 – Reserved

These bits are reserved and will always read as zero.

• Bit 3 – WGM02: Waveform Generation Mode

See the description in the

”TCCR0A – Timer/Counter Control Register A” on page 104

.

• Bits 2:0 – CS02:0: Clock Select

The three Clock Select bits select the clock source to be used by the Timer/Counter.

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15.9.3

15.9.4

15.9.5

Table 15-9.

Clock Select bit description.

1

1

0

1

1

CS02

0

0

0

0

1

1

0

1

CS01

0

0

1

CS00 Description

0 No clock source (Timer/Counter stopped)

1

0

1

0

1

0

1 clk clk

I/O

I/O

/(No prescaling)

/8 (From prescaler) clk

I/O

/64 (From prescaler) clk

I/O

/256 (From prescaler) clk

I/O

/1024 (From prescaler)

External clock source on T0 pin. Clock on falling edge.

External clock source on T0 pin. Clock on rising edge.

If external pin modes are used for the Timer/Counter0, transitions on the T0 pin will clock the counter even if the pin is configured as an output. This feature allows software control of the counting.

TCNT0 – Timer/Counter Register

Bit

0x26 (0x46)

Read/Write

Initial Value

7

R/W

0

6

R/W

0

5

R/W

0

4

TCNT0[7:0]

3

R/W

0

R/W

0

2

R/W

0

1

R/W

0

0

R/W

0

TCNT0

The Timer/Counter Register gives direct access, both for read and write operations, to the

Timer/Counter unit 8-bit counter. Writing to the TCNT0 Register blocks (removes) the Compare

Match on the following timer clock. Modifying the counter (TCNT0) while the counter is running, introduces a risk of missing a Compare Match between TCNT0 and the OCR0x Registers.

OCR0A – Output Compare Register A

Bit

0x27 (0x47)

Read/Write

Initial Value

7

R/W

0

6

R/W

0

5

R/W

0

4

OCR0A[7:0]

3

R/W

0

R/W

0

2

R/W

0

1

R/W

0

0

R/W

0

OCR0A

The Output Compare Register A contains an 8-bit value that is continuously compared with the counter value (TCNT0). A match can be used to generate an Output Compare interrupt, or to generate a waveform output on the OC0A pin.

OCR0B – Output Compare Register B

Bit

0x28 (0x48)

Read/Write

Initial Value

7

R/W

0

6

R/W

0

5

R/W

0

4 3

OCR0B[7:0]

R/W R/W

0 0

2

R/W

0

1

R/W

0

0

R/W

0

OCR0B

The Output Compare Register B contains an 8-bit value that is continuously compared with the counter value (TCNT0). A match can be used to generate an Output Compare interrupt, or to generate a waveform output on the OC0B pin.

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15.9.6

15.9.7

TIMSK0 – Timer/Counter Interrupt Mask Register

Bit

(0x6E)

Read/Write

Initial Value

7

R

0

6

R

0

5

R

0

4

R

0

3

R

0

2

OCIE0B

R/W

0

1

OCIE0A

R/W

0

0

TOIE0

R/W

0

TIMSK0

• Bits 7:3 – Reserved

These bits are reserved and will always read as zero.

• Bit 2 – OCIE0B: Timer/Counter Output Compare Match B Interrupt Enable

When the OCIE0B bit is written to one, and the I-bit in the Status Register is set, the

Timer/Counter Compare Match B interrupt is enabled. The corresponding interrupt is executed if a Compare Match in Timer/Counter occurs, that is, when the OCF0B bit is set in the

Timer/Counter Interrupt Flag Register – TIFR0.

• Bit 1 – OCIE0A: Timer/Counter0 Output Compare Match A Interrupt Enable

When the OCIE0A bit is written to one, and the I-bit in the Status Register is set, the

Timer/Counter0 Compare Match A interrupt is enabled. The corresponding interrupt is executed if a Compare Match in Timer/Counter0 occurs, that is, when the OCF0A bit is set in the

Timer/Counter 0 Interrupt Flag Register – TIFR0.

• Bit 0 – TOIE0: Timer/Counter0 Overflow Interrupt Enable

When the TOIE0 bit is written to one, and the I-bit in the Status Register is set, the

Timer/Counter0 Overflow interrupt is enabled. The corresponding interrupt is executed if an overflow in Timer/Counter0 occurs, that is, when the TOV0 bit is set in the Timer/Counter 0 Interrupt Flag Register – TIFR0.

TIFR0 – Timer/Counter 0 Interrupt Flag Register

Bit

0x15 (0x35)

Read/Write

Initial Value

R

0

7

R

0

6

R

0

5

R

0

4

R

0

3

2

OCF0B

R/W

0

1

OCF0A

R/W

0

0

TOV0

R/W

0

TIFR0

• Bits 7:3 – Reserved

These bits are reserved and will always read as zero.

• Bit 2 – OCF0B: Timer/Counter 0 Output Compare B Match Flag

The OCF0B bit is set when a Compare Match occurs between the Timer/Counter and the data in

OCR0B – Output Compare Register0 B. OCF0B is cleared by hardware when executing the corresponding interrupt handling vector. Alternatively, OCF0B is cleared by writing a logic one to the flag. When the I-bit in SREG, OCIE0B (Timer/Counter Compare B Match Interrupt Enable), and OCF0B are set, the Timer/Counter Compare Match Interrupt is executed.

• Bit 1 – OCF0A: Timer/Counter 0 Output Compare A Match Flag

The OCF0A bit is set when a Compare Match occurs between the Timer/Counter0 and the data in OCR0A – Output Compare Register0. OCF0A is cleared by hardware when executing the corresponding interrupt handling vector. Alternatively, OCF0A is cleared by writing a logic one to the flag. When the I-bit in SREG, OCIE0A (Timer/Counter0 Compare Match Interrupt Enable), and OCF0A are set, the Timer/Counter0 Compare Match Interrupt is executed.

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• Bit 0 – TOV0: Timer/Counter0 Overflow Flag

The bit TOV0 is set when an overflow occurs in Timer/Counter0. TOV0 is cleared by hardware when executing the corresponding interrupt handling vector. Alternatively, TOV0 is cleared by writing a logic one to the flag. When the SREG I-bit, TOIE0 (Timer/Counter0 Overflow Interrupt

Enable), and TOV0 are set, the Timer/Counter0 Overflow interrupt is executed.

The setting of this flag is dependent of the WGM02:0 bit setting. Refer to Table 15-8 , ”Waveform

Generation mode bit description.” on page 106 .

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16. 16-bit Timer/Counter1 and Timer/Counter3 with PWM

16.1

Features

True 16-bit design (that is, allows 16-bit PWM)

Two independent Output Compare units

Double Buffered Output Compare Registers

One Input Capture unit

Input Capture Noise Canceler

Clear Timer on Compare Match (Auto Reload)

Glitch-free, Phase Correct Pulse Width Modulator (PWM)

Variable PWM Period

Frequency Generator

External Event Counter

Four independent interrupt Sources (TOV1, OCF1A, OCF1B, and ICF1)

16.2

Overview

The 16-bit Timer/Counter unit allows accurate program execution timing (event management), wave generation, and signal timing measurement.

Most register and bit references in this section are written in general form. A lower case “n” replaces the Timer/Counter number, and a lower case “x” replaces the Output Compare unit channel. However, when using the register or bit defines in a program, the precise form must be used, that is, TCNT1 for accessing Timer/Counter1 counter value and so on.

A simplified block diagram of the 16-bit Timer/Counter is shown in Figure 16-1 . For the actual

placement of I/O pins, see ”Pin configurations” on page 2 . CPU accessible I/O Registers, includ-

ing I/O bits and I/O pins, are shown in bold. The device-specific I/O Register and bit locations

are listed in the ”Register description” on page 132

.

The PRTIM1 bit in

”PRR0 – Power Reduction Register 0” on page 48

must be written to zero to enable Timer/Counter1 module.

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Figure 16-1.

16-bit Timer/Counter block diagram

(Note:)

.

Count

Clear

Direction

Control Logic clk

Tn

TOP BOTTOM

TOVn

(Int.Req.)

Clock Select

Edge

Detector

( From Prescaler )

Tn

Timer/Counter

TCNTn

= =

0

=

OCRnA

OCnA

(Int.Req.)

Waveform

Generation

OCnA

=

OCRnB

ICRn

TCCRnA

Fixed

TOP

Values

TCCRnB

ICFn

(Int.Req.)

Edge

Detector

OCnB

(Int.Req.)

Waveform

Generation

OCnB

( From Analog

Comparator Ouput )

Noise

Canceler

ICPn

16.2.1

Registers

Note: Refer to

Figure 1-1 on page 2

and ”Alternate Port Functions” on page 77 for Timer/Counter1 pin

placement and description.

The Timer/Counter (TCNTn), Output Compare Registers (OCRnA/B/C), and Input Capture Reg-

ister (ICRn) are all 16-bit registers. Special procedures must be followed when accessing the 16bit registers. These procedures are described in the section

”Accessing 16-bit Registers” on page 113 . The Timer/Counter Control Registers (TCCRnA/B/C) are 8-bit registers and have no

CPU access restrictions. Interrupt requests (abbreviated to Int.Req. in the figure) signals are all visible in the Timer Interrupt Flag Register (TIFRn). All interrupts are individually masked with the Timer Interrupt Mask Register (TIMSKn). TIFRn and TIMSKn are not shown in the figure.

The Timer/Counter can be clocked internally, via the prescaler, or by an external clock source on the Tn pin. The Clock Select logic block controls which clock source and edge the Timer/Counter uses to increment (or decrement) its value. The Timer/Counter is inactive when no clock source is selected. The output from the Clock Select logic is referred to as the timer clock (clk

T n

).

The double buffered Output Compare Registers (OCRnA/B/C) are compared with the

Timer/Counter value at all time. The result of the compare can be used by the Waveform Generator to generate a PWM or variable frequency output on the Output Compare pin (OCnA/B/C).

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See Section “16.7” on page 120

. The compare match event will also set the Compare Match

Flag (OCFnA/B/C) which can be used to generate an Output Compare interrupt request.

The Input Capture Register can capture the Timer/Counter value at a given external (edge triggered) event on either the Input Capture pin (ICPn) or on the Analog Comparator pins (

See

Section “22.” on page 240

) The Input Capture unit includes a digital filtering unit (Noise Canceler) for reducing the chance of capturing noise spikes.

The TOP value, or maximum Timer/Counter value, can in some modes of operation be defined by either the OCRnA Register, the ICRn Register, or by a set of fixed values. When using

OCRnA as TOP value in a PWM mode, the OCRnA Register can not be used for generating a

PWM output. However, the TOP value will in this case be double buffered allowing the TOP value to be changed in run time. If a fixed TOP value is required, the ICRn Register can be used as an alternative, freeing the OCRnA to be used as PWM output.

16.2.2

Definitions

The following definitions are used extensively throughout the section:

Table 16-1.

Definitions.

BOTTOM

MAX The counter reaches its MAXimum when it becomes 0xFFFF (decimal 65535).

TOP

The counter reaches the TOP when it becomes equal to the highest value in the count sequence. The TOP value can be assigned to be one of the fixed values: 0x00FF, 0x01FF, or 0x03FF, or to the value stored in the OCRnA or ICRn Register. The assignment is dependent of the mode of operation.

16.3

Accessing 16-bit Registers

The TCNTn, OCRnA/B/C, and ICRn are 16-bit registers that can be accessed by the AVR CPU via the 8-bit data bus. The 16-bit register must be byte accessed using two read or write operations. Each 16-bit timer has a single 8-bit register for temporary storing of the high byte of the 16bit access. The same temporary register is shared between all 16-bit registers within each 16-bit timer. Accessing the low byte triggers the 16-bit read or write operation. When the low byte of a

16-bit register is written by the CPU, the high byte stored in the temporary register, and the low byte written are both copied into the 16-bit register in the same clock cycle. When the low byte of a 16-bit register is read by the CPU, the high byte of the 16-bit register is copied into the temporary register in the same clock cycle as the low byte is read.

Not all 16-bit accesses uses the temporary register for the high byte. Reading the OCRnA/B/C

16-bit registers does not involve using the temporary register.

To do a 16-bit write, the high byte must be written before the low byte. For a 16-bit read, the low byte must be read before the high byte.

The following code examples show how to access the 16-bit Timer Registers assuming that no interrupts updates the temporary register. The same principle can be used directly for accessing the OCRnA/B/C and ICRn Registers. Note that when using “C”, the compiler handles the 16-bit access.

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Assembly Code Examples

(1)

...

; Set TCNTn to 0x01FF

ldi

r17,0x01

ldi

r16,0xFF

out

TCNTnH,r17

out

TCNTnL,r16

; Read TCNTn into r17:r16

in

r16,TCNTnL

in

r17,TCNTnH

...

C Code Examples

(1)

unsigned int

i;

...

/* Set TCNTn to 0x01FF */

TCNTn = 0x1FF;

/* Read TCNTn into i */ i = TCNTn;

...

Note: 1. The example code assumes that the part specific header file is included.

For I/O Registers located in extended I/O map, “IN”, “OUT”, “SBIS”, “SBIC”, “CBI”, and “SBI” instructions must be replaced with instructions that allow access to extended I/O. Typically

“LDS” and “STS” combined with “SBRS”, “SBRC”, “SBR”, and “CBR”.

The assembly code example returns the TCNTn value in the r17:r16 register pair.

It is important to notice that accessing 16-bit registers are atomic operations. If an interrupt occurs between the two instructions accessing the 16-bit register, and the interrupt code updates the temporary register by accessing the same or any other of the 16-bit Timer Registers, then the result of the access outside the interrupt will be corrupted. Therefore, when both the main code and the interrupt code update the temporary register, the main code must disable the interrupts during the 16-bit access.

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The following code examples show how to do an atomic read of the TCNTn Register contents.

Reading any of the OCRnA/B/C or ICRn Registers can be done by using the same principle.

Assembly Code Example

(1)

TIM16_ReadTCNTn:

; Save global interrupt flag

in

r18,SREG

; Disable interrupts

cli

; Read TCNTn into r17:r16

in

r16,TCNTnL

in

r17,TCNTnH

; Restore global interrupt flag

out

SREG,r18

ret

C Code Example

(1)

unsigned int

TIM16_ReadTCNTn( void )

{

unsigned char

sreg;

unsigned int

i;

/* Save global interrupt flag */ sreg = SREG;

/* Disable interrupts */

_CLI();

/* Read TCNTn into i */ i = TCNTn;

/* Restore global interrupt flag */

SREG = sreg;

return

i;

}

Note: 1. The example code assumes that the part specific header file is included.

For I/O Registers located in extended I/O map, “IN”, “OUT”, “SBIS”, “SBIC”, “CBI”, and “SBI” instructions must be replaced with instructions that allow access to extended I/O. Typically

“LDS” and “STS” combined with “SBRS”, “SBRC”, “SBR”, and “CBR”.

The assembly code example returns the TCNTn value in the r17:r16 register pair.

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The following code examples show how to do an atomic write of the TCNTn Register contents.

Writing any of the OCRnA/B/C or ICRn Registers can be done by using the same principle.

Assembly Code Example

(1)

TIM16_WriteTCNTn:

; Save global interrupt flag

in

r18,SREG

; Disable interrupts

cli

; Set TCNTn to r17:r16

out

TCNTnH,r17

out

TCNTnL,r16

; Restore global interrupt flag

out

SREG,r18

ret

C Code Example

(1)

void

TIM16_WriteTCNTn( unsigned int i )

{

unsigned char

sreg;

unsigned int

i;

/* Save global interrupt flag */ sreg = SREG;

/* Disable interrupts */

_CLI();

/* Set TCNTn to i */

TCNTn = i;

/* Restore global interrupt flag */

SREG = sreg;

}

Note: 1. The example code assumes that the part specific header file is included.

For I/O Registers located in extended I/O map, “IN”, “OUT”, “SBIS”, “SBIC”, “CBI”, and “SBI” instructions must be replaced with instructions that allow access to extended I/O. Typically

“LDS” and “STS” combined with “SBRS”, “SBRC”, “SBR”, and “CBR”.

The assembly code example requires that the r17:r16 register pair contains the value to be written to TCNTn.

Reusing the Temporary High Byte Register 16.3.1

If writing to more than one 16-bit register where the high byte is the same for all registers written, then the high byte only needs to be written once. However, note that the same rule of atomic operation described previously also applies in this case.

16.4

Timer/Counter Clock Sources

The Timer/Counter can be clocked by an internal or an external clock source. The clock source is selected by the Clock Select logic which is controlled by the Clock Select (CSn2:0) bits located in the Timer/Counter control Register B (TCCRnB). For details on clock sources and prescaler, see

”Timer/Counter Prescaler” on page 155 .

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16.5

Counter Unit

The main part of the 16-bit Timer/Counter is the programmable 16-bit bi-directional counter unit.

Figure 16-2

shows a block diagram of the counter and its surroundings.

Figure 16-2.

Counter unit block diagram.

DATA BUS

(8-bit)

TOVn

(Int.Req.)

TEMP (8-bit)

Clock Select

Edge

Detector

Tn

TCNTnH

(8-bit)

TCNTnL

TCNTn

(16-bit Counter)

(8-bit)

Count

Clear

Direction

Control Logic clk

Tn

( From Prescaler )

TOP BOTTOM

Signal description (internal signals):

Count

Increment or decrement TCNTn by 1.

Direction

Select between increment and decrement.

Clear TCNTn (set all bits to zero).

Clear clk

T n

TOP

Timer/Counter clock.

Signalize that TCNTn has reached maximum value.

BOTTOM

Signalize that TCNTn has reached minimum value (zero).

The 16-bit counter is mapped into two 8-bit I/O memory locations: Counter High (TCNTnH) containing the upper eight bits of the counter, and Counter Low (TCNTnL) containing the lower eight bits. The TCNTnH Register can only be indirectly accessed by the CPU. When the CPU does an access to the TCNTnH I/O location, the CPU accesses the high byte temporary register (TEMP).

The temporary register is updated with the TCNTnH value when the TCNTnL is read, and

TCNTnH is updated with the temporary register value when TCNTnL is written. This allows the

CPU to read or write the entire 16-bit counter value within one clock cycle via the 8-bit data bus.

It is important to notice that there are special cases of writing to the TCNTn Register when the counter is counting that will give unpredictable results. The special cases are described in the sections where they are of importance.

Depending on the mode of operation used, the counter is cleared, incremented, or decremented at each timer clock (clk

T n

). The clk

T n

can be generated from an external or internal clock source, selected by the Clock Select bits (CSn2:0). When no clock source is selected (CSn2:0 = 0) the timer is stopped. However, the TCNTn value can be accessed by the CPU, independent of whether clk

T n

is present or not. A CPU write overrides (has priority over) all counter clear or count operations.

The counting sequence is determined by the setting of the Waveform Generation mode bits

(WGMn3:0) located in the Timer/Counter Control Registers A and B (TCCRnA and TCCRnB).

There are close connections between how the counter behaves (counts) and how waveforms are generated on the Output Compare outputs OCnx. For more details about advanced counting

sequences and waveform generation, see ”Modes of Operation” on page 123

.

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The Timer/Counter Overflow Flag (TOVn) is set according to the mode of operation selected by the WGMn3:0 bits. TOVn can be used for generating a CPU interrupt.

16.6

Input Capture Unit

The Timer/Counter incorporates an Input Capture unit that can capture external events and give them a time-stamp indicating time of occurrence. The external signal indicating an event, or multiple events, can be applied via the ICPn pin or alternatively, via the analog-comparator unit. The time-stamps can then be used to calculate frequency, duty-cycle, and other features of the signal applied. Alternatively the time-stamps can be used for creating a log of the events.

The Input Capture unit is illustrated by the block diagram shown in

Figure 16-3

. The elements of the block diagram that are not directly a part of the Input Capture unit are gray shaded. The small “n” in register and bit names indicates the Timer/Counter number.

Figure 16-3.

Input Capture unit block diagram.

DATA BUS

(8-bit)

TEMP (8-bit)

ICRnH

(8-bit)

WRITE

ICRnL

ICRn

(16-bit Register)

(8-bit)

TCNTnH

(8-bit)

TCNTnL

TCNTn

(16-bit Counter)

(8-bit)

ACO*

Analog

Comparator

ACIC* ICNC

Noise

Canceler

ICES

Edge

Detector

ICFn

(Int.Req.)

ICPn

When a change of the logic level (an event) occurs on the Input Capture pin (ICPn), alternatively on the Analog Comparator output (ACO), and this change confirms to the setting of the edge detector, a capture will be triggered. When a capture is triggered, the 16-bit value of the counter

(TCNTn) is written to the Input Capture Register (ICRn). The Input Capture Flag (ICFn) is set at the same system clock as the TCNTn value is copied into ICRn Register. If enabled (ICIEn = 1), the Input Capture Flag generates an Input Capture interrupt. The ICFn Flag is automatically cleared when the interrupt is executed. Alternatively the ICFn Flag can be cleared by software by writing a logical one to its I/O bit location.

Reading the 16-bit value in the Input Capture Register (ICRn) is done by first reading the low byte (ICRnL) and then the high byte (ICRnH). When the low byte is read the high byte is copied into the high byte temporary register (TEMP). When the CPU reads the ICRnH I/O location it will access the TEMP Register.

The ICRn Register can only be written when using a Waveform Generation mode that utilizes the ICRn Register for defining the counter’s TOP value. In these cases the Waveform Genera-

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16.6.1

16.6.2

16.6.3

tion mode (WGMn3:0) bits must be set before the TOP value can be written to the ICRn

Register. When writing the ICRn Register the high byte must be written to the ICRnH I/O location before the low byte is written to ICRnL.

For more information on how to access the 16-bit registers refer to

”Accessing 16-bit Registers” on page 113 .

Input Capture Trigger Source

The main trigger source for the Input Capture unit is the Input Capture pin (ICPn).

Timer/Counter1 can alternatively use the Analog Comparator output as trigger source for the

Input Capture unit. The Analog Comparator is selected as trigger source by setting the Analog

Comparator Input Capture

(ACIC) bit in the Analog Comparator Control and Status Register

(ACSR). Be aware that changing trigger source can trigger a capture. The Input Capture Flag must therefore be cleared after the change.

Both the Input Capture pin (ICPn) and the Analog Comparator output (ACO) inputs are sampled

using the same technique as for the Tn pin ( Figure 16-1 on page 112

). The edge detector is also identical. However, when the noise canceler is enabled, additional logic is inserted before the edge detector, which increases the delay by four system clock cycles. Note that the input of the noise canceler and edge detector is always enabled unless the Timer/Counter is set in a Waveform Generation mode that uses ICRn to define TOP.

Noise Canceler

An Input Capture can be triggered by software by controlling the port of the ICPn pin.

The noise canceler improves noise immunity by using a simple digital filtering scheme. The noise canceler input is monitored over four samples, and all four must be equal for changing the output that in turn is used by the edge detector.

The noise canceler is enabled by setting the Input Capture Noise Canceler (ICNCn) bit in

Timer/Counter Control Register B (TCCRnB). When enabled the noise canceler introduces additional four system clock cycles of delay from a change applied to the input, to the update of the

ICRn Register. The noise canceler uses the system clock and is therefore not affected by the prescaler.

Using the Input Capture unit

The main challenge when using the Input Capture unit is to assign enough processor capacity for handling the incoming events. The time between two events is critical. If the processor has not read the captured value in the ICRn Register before the next event occurs, the ICRn will be overwritten with a new value. In this case the result of the capture will be incorrect.

When using the Input Capture interrupt, the ICRn Register should be read as early in the interrupt handler routine as possible. Even though the Input Capture interrupt has relatively high priority, the maximum interrupt response time is dependent on the maximum number of clock cycles it takes to handle any of the other interrupt requests.

Using the Input Capture unit in any mode of operation when the TOP value (resolution) is actively changed during operation, is not recommended.

Measurement of an external signal’s duty cycle requires that the trigger edge is changed after each capture. Changing the edge sensing must be done as early as possible after the ICRn

Register has been read. After a change of the edge, the Input Capture Flag (ICFn) must be

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cleared by software (writing a logical one to the I/O bit location). For measuring frequency only, the clearing of the ICFn Flag is not required (if an interrupt handler is used).

16.7

Output Compare units

The 16-bit comparator continuously compares TCNTn with the Output Compare Register

(OCRnx). If TCNT equals OCRnx the comparator signals a match. A match will set the Output

Compare Flag (OCFnx) at the next timer clock cycle. If enabled (OCIEnx = 1), the Output Compare Flag generates an Output Compare interrupt. The OCFnx Flag is automatically cleared when the interrupt is executed. Alternatively the OCFnx Flag can be cleared by software by writing a logical one to its I/O bit location. The Waveform Generator uses the match signal to generate an output according to operating mode set by the Waveform Generation mode

(WGMn3:0) bits and Compare Output mode (COMnx1:0) bits. The TOP and BOTTOM signals are used by the Waveform Generator for handling the special cases of the extreme values in

some modes of operation (See “Modes of Operation” on page 123).

A special feature of Output Compare unit A allows it to define the Timer/Counter TOP value (i.e., counter resolution). In addition to the counter resolution, the TOP value defines the period time for waveforms generated by the Waveform Generator.

Figure 16-4 shows a block diagram of the Output Compare unit. The small “n” in the register and

bit names indicates the device number (n = n for Timer/Counter n), and the “x” indicates Output

Compare unit (A/B/C). The elements of the block diagram that are not directly a part of the Output Compare unit are gray shaded.

Figure 16-4.

Output Compare unit, block diagram.

DATA BUS

(8-bit)

TEMP (8-bit)

OCRnxH

Buf. (8-bit)

OCRnxL

Buf. (8-bit)

OCRnx

Buffer (16-bit Register)

TCNTnH

(8-bit)

TCNTnL

TCNTn

(16-bit Counter)

(8-bit)

OCRnxH

(8-bit)

OCRnxL

OCRnx

(16-bit Register)

(8-bit)

TOP

BOTTOM

=

(16-bit Comparator )

OCFnx

(Int.Req.)

Waveform Generator

WGMn3:0 COMnx1:0

OCnx

The OCRnx Register is double buffered when using any of the twelve Pulse Width Modulation

(PWM) modes. For the Normal and Clear Timer on Compare (CTC) modes of operation, the double buffering is disabled. The double buffering synchronizes the update of the OCRnx Compare Register to either TOP or BOTTOM of the counting sequence. The synchronization

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16.7.1

16.7.2

16.7.3

prevents the occurrence of odd-length, non-symmetrical PWM pulses, thereby making the output glitch-free.

The OCRnx Register access may seem complex, but this is not case. When the double buffering is enabled, the CPU has access to the OCRnx Buffer Register, and if double buffering is disabled the CPU will access the OCRnx directly. The content of the OCR1x (Buffer or Compare)

Register is only changed by a write operation (the Timer/Counter does not update this register automatically as the TCNT1 and ICR1 Register). Therefore OCR1x is not read via the high byte temporary register (TEMP). However, it is a good practice to read the low byte first as when accessing other 16-bit registers. Writing the OCRnx Registers must be done via the TEMP Register since the compare of all 16 bits is done continuously. The high byte (OCRnxH) has to be written first. When the high byte I/O location is written by the CPU, the TEMP Register will be updated by the value written. Then when the low byte (OCRnxL) is written to the lower eight bits, the high byte will be copied into the upper 8-bits of either the OCRnx buffer or OCRnx Compare

Register in the same system clock cycle.

For more information of how to access the 16-bit registers refer to ”Accessing 16-bit Registers” on page 113 .

Force Output Compare

In non-PWM Waveform Generation modes, the match output of the comparator can be forced by writing a one to the Force Output Compare (FOCnx) bit. Forcing compare match will not set the

OCFnx Flag or reload/clear the timer, but the OCnx pin will be updated as if a real compare match had occurred (the COMn1:0 bits settings define whether the OCnx pin is set, cleared or toggled).

Compare Match Blocking by TCNTn Write

All CPU writes to the TCNTn Register will block any compare match that occurs in the next timer clock cycle, even when the timer is stopped. This feature allows OCRnx to be initialized to the same value as TCNTn without triggering an interrupt when the Timer/Counter clock is enabled.

Using the Output Compare Unit

Since writing TCNTn in any mode of operation will block all compare matches for one timer clock cycle, there are risks involved when changing TCNTn when using any of the Output Compare channels, independent of whether the Timer/Counter is running or not. If the value written to

TCNTn equals the OCRnx value, the compare match will be missed, resulting in incorrect waveform generation. Do not write the TCNTn equal to TOP in PWM modes with variable TOP values. The compare match for the TOP will be ignored and the counter will continue to 0xFFFF.

Similarly, do not write the TCNTn value equal to BOTTOM when the counter is downcounting.

The setup of the OCnx should be performed before setting the Data Direction Register for the port pin to output. The easiest way of setting the OCnx value is to use the Force Output Compare (FOCnx) strobe bits in Normal mode. The OCnx Register keeps its value even when changing between Waveform Generation modes.

Be aware that the COMnx1:0 bits are not double buffered together with the compare value.

Changing the COMnx1:0 bits will take effect immediately.

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16.8

Compare Match Output unit

The Compare Output mode (COMnx1:0) bits have two functions. The Waveform Generator uses the COMnx1:0 bits for defining the Output Compare (OCnx) state at the next compare match.

Secondly the COMnx1:0 bits control the OCnx pin output source. Figure 16-5 shows a simplified

schematic of the logic affected by the COMnx1:0 bit setting. The I/O Registers, I/O bits, and I/O pins in the figure are shown in bold. Only the parts of the general I/O Port Control Registers

(DDR and PORT) that are affected by the COMnx1:0 bits are shown. When referring to the

OCnx state, the reference is for the internal OCnx Register, not the OCnx pin. If a system reset occur, the OCnx Register is reset to “0”.

Figure 16-5.

Compare Match Output unit, schematic.

COMnx1

COMnx0

FOCnx

Waveform

Generator

D Q

OCnx

D Q

PORT

D Q

1

0

OCnx

Pin

DDR

clk

I/O

The general I/O port function is overridden by the Output Compare (OCnx) from the Waveform

Generator if either of the COMnx1:0 bits are set. However, the OCnx pin direction (input or output) is still controlled by the Data Direction Register (DDR) for the port pin. The Data Direction

Register bit for the OCnx pin (DDR_OCnx) must be set as output before the OCnx value is visible on the pin. The port override function is generally independent of the Waveform Generation mode, but there are some exceptions. Refer to

Table 16-2 ,

Table 16-3

and

Table 16-4

for details.

The design of the Output Compare pin logic allows initialization of the OCnx state before the output is enabled. Note that some COMnx1:0 bit settings are reserved for certain modes of

operation. See “Register description” on page 132.

The COMnx1:0 bits have no effect on the Input Capture unit.

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16.8.1

Compare Output Mode and Waveform Generation

The Waveform Generator uses the COMnx1:0 bits differently in normal, CTC, and PWM modes.

For all modes, setting the COMnx1:0 = 0 tells the Waveform Generator that no action on the

OCnx Register is to be performed on the next compare match. For compare output actions in the non-PWM modes refer to

Table 16-2 on page 132

. For fast PWM mode refer to

Table 16-3 on page 133 , and for phase correct and phase and frequency correct PWM refer to Table 16-4 on page 133

.

A change of the COMnx1:0 bits state will have effect at the first compare match after the bits are written. For non-PWM modes, the action can be forced to have immediate effect by using the

FOCnx strobe bits.

16.9

Modes of Operation

16.9.1

16.9.2

The mode of operation, that is, the behavior of the Timer/Counter and the Output Compare pins, is defined by the combination of the Waveform Generation mode (WGMn3:0) and Compare Out-

put mode (COMnx1:0) bits. The Compare Output mode bits do not affect the counting sequence, while the Waveform Generation mode bits do. The COMnx1:0 bits control whether the PWM output generated should be inverted or not (inverted or non-inverted PWM). For non-PWM modes the COMnx1:0 bits control whether the output should be set, cleared or toggle at a compare

match ( See “Compare Match Output unit” on page 122

).

For detailed timing information refer to

”Timer/Counter Timing diagrams” on page 130

.

Normal mode

The simplest mode of operation is the Normal mode (WGMn3:0 = 0). In this mode the counting direction is always up (incrementing), and no counter clear is performed. The counter simply overruns when it passes its maximum 16-bit value (MAX = 0xFFFF) and then restarts from the

BOTTOM (0x0000). In normal operation the Timer/Counter Overflow Flag (TOVn) will be set in the same timer clock cycle as the TCNTn becomes zero. The TOVn Flag in this case behaves like a 17th bit, except that it is only set, not cleared. However, combined with the timer overflow interrupt that automatically clears the TOVn Flag, the timer resolution can be increased by software. There are no special cases to consider in the Normal mode, a new counter value can be written anytime.

The Input Capture unit is easy to use in Normal mode. However, observe that the maximum interval between the external events must not exceed the resolution of the counter. If the interval between events are too long, the timer overflow interrupt or the prescaler must be used to extend the resolution for the capture unit.

The Output Compare units can be used to generate interrupts at some given time. Using the

Output Compare to generate waveforms in Normal mode is not recommended, since this will occupy too much of the CPU time.

Clear Timer on Compare Match (CTC) mode

In Clear Timer on Compare or CTC mode (WGMn3:0 = 4 or 12), the OCRnA or ICRn Register are used to manipulate the counter resolution. In CTC mode the counter is cleared to zero when the counter value (TCNTn) matches either the OCRnA (WGMn3:0 = 4) or the ICRn (WGMn3:0 =

12). The OCRnA or ICRn define the top value for the counter, hence also its resolution. This mode allows greater control of the compare match output frequency. It also simplifies the operation of counting external events.

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The timing diagram for the CTC mode is shown in

Figure 16-6 . The counter value (TCNTn)

increases until a compare match occurs with either OCRnA or ICRn, and then counter (TCNTn) is cleared.

Figure 16-6.

CTC mode, timing diagram.

OCnA Interrupt Flag Set or ICFn Interrupt Flag Set

(Interrupt on TOP)

TCNTn

16.9.3

OCnA

(Toggle)

Period

1 2 3 4

(COMnA1:0 = 1)

An interrupt can be generated at each time the counter value reaches the TOP value by either using the OCFnA or ICFn Flag according to the register used to define the TOP value. If the interrupt is enabled, the interrupt handler routine can be used for updating the TOP value. However, changing the TOP to a value close to BOTTOM when the counter is running with none or a low prescaler value must be done with care since the CTC mode does not have the double buffering feature. If the new value written to OCRnA or ICRn is lower than the current value of

TCNTn, the counter will miss the compare match. The counter will then have to count to its maximum value (0xFFFF) and wrap around starting at 0x0000 before the compare match can occur.

In many cases this feature is not desirable. An alternative will then be to use the fast PWM mode using OCRnA for defining TOP (WGMn3:0 = 15) since the OCRnA then will be double buffered.

For generating a waveform output in CTC mode, the OCnA output can be set to toggle its logical level on each compare match by setting the Compare Output mode bits to toggle mode

(COMnA1:0 = 1). The OCnA value will not be visible on the port pin unless the data direction for the pin is set to output (DDR_OCnA = 1). The waveform generated will have a maximum frequency of f

OC n A

= f clk_I/O

/2 when OCRnA is set to zero (0x0000). The waveform frequency is defined by the following equation:

f

OCnA

=

⋅ ⋅ (

f

clk_I/O

1

+

OCRnA

)

The N variable represents the prescaler factor (1, 8, 64, 256, or 1024).

As for the Normal mode of operation, the TOVn Flag is set in the same timer clock cycle that the counter counts from MAX to 0x0000.

Fast PWM mode

The fast Pulse Width Modulation or fast PWM mode (WGMn3:0 = 5, 6, 7, 14, or 15) provides a high frequency PWM waveform generation option. The fast PWM differs from the other PWM options by its single-slope operation. The counter counts from BOTTOM to TOP then restarts from BOTTOM. In non-inverting Compare Output mode, the Output Compare (OCnx) is cleared on the compare match between TCNTn and OCRnx, and set at BOTTOM. In inverting Compare

Output mode output is set on compare match and cleared at BOTTOM. Due to the single-slope operation, the operating frequency of the fast PWM mode can be twice as high as the phase cor-

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rect and phase and frequency correct PWM modes that use dual-slope operation. This high frequency makes the fast PWM mode well suited for power regulation, rectification, and DAC applications. High frequency allows physically small sized external components (coils, capacitors), hence reduces total system cost.

The PWM resolution for fast PWM can be fixed to 8-, 9-, or 10-bit, or defined by either ICRn or

OCRnA. The minimum resolution allowed is 2-bit (ICRn or OCRnA set to 0x0003), and the maximum resolution is 16-bit (ICRn or OCRnA set to MAX). The PWM resolution in bits can be calculated by using the following equation:

R

FPWM

= log

(

TOP

log

( )

+

1

)

-----------------------------------

In fast PWM mode the counter is incremented until the counter value matches either one of the fixed values 0x00FF, 0x01FF, or 0x03FF (WGMn3:0 = 5, 6, or 7), the value in ICRn (WGMn3:0 =

14), or the value in OCRnA (WGMn3:0 = 15). The counter is then cleared at the following timer

clock cycle. The timing diagram for the fast PWM mode is shown in Figure 16-7 . The figure

shows fast PWM mode when OCRnA or ICRn is used to define TOP. The TCNTn value is in the timing diagram shown as a histogram for illustrating the single-slope operation. The diagram includes non-inverted and inverted PWM outputs. The small horizontal line marks on the TCNTn slopes represent compare matches between OCRnx and TCNTn. The OCnx Interrupt Flag will be set when a compare match occurs.

Figure 16-7.

Fast PWM mode, timing diagram.

OCRnx/TOP Update and

TOVn Interrupt Flag Set and

OCnA Interrupt Flag Set or ICFn Interrupt Flag Set

(Interrupt on TOP)

TCNTn

OCnx

OCnx

(COMnx1:0 = 2)

(COMnx1:0 = 3)

Period

1 2 3 4 5 6 7 8

The Timer/Counter Overflow Flag (TOVn) is set each time the counter reaches TOP. In addition the OCnA or ICFn Flag is set at the same timer clock cycle as TOVn is set when either OCRnA or ICRn is used for defining the TOP value. If one of the interrupts are enabled, the interrupt handler routine can be used for updating the TOP and compare values.

When changing the TOP value the program must ensure that the new TOP value is higher or equal to the value of all of the Compare Registers. If the TOP value is lower than any of the

Compare Registers, a compare match will never occur between the TCNTn and the OCRnx.

Note that when using fixed TOP values the unused bits are masked to zero when any of the

OCRnx Registers are written.

The procedure for updating ICRn differs from updating OCRnA when used for defining the TOP value. The ICRn Register is not double buffered. This means that if ICRn is changed to a low

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16.9.4

value when the counter is running with none or a low prescaler value, there is a risk that the new

ICRn value written is lower than the current value of TCNTn. The result will then be that the counter will miss the compare match at the TOP value. The counter will then have to count to the

MAX value (0xFFFF) and wrap around starting at 0x0000 before the compare match can occur.

The OCRnA Register however, is double buffered. This feature allows the OCRnA I/O location to be written anytime. When the OCRnA I/O location is written the value written will be put into the OCRnA Buffer Register. The OCRnA Compare Register will then be updated with the value in the Buffer Register at the next timer clock cycle the TCNTn matches TOP. The update is done at the same timer clock cycle as the TCNTn is cleared and the TOVn Flag is set.

Using the ICRn Register for defining TOP works well when using fixed TOP values. By using

ICRn, the OCRnA Register is free to be used for generating a PWM output on OCnA. However, if the base PWM frequency is actively changed (by changing the TOP value), using the OCRnA as TOP is clearly a better choice due to its double buffer feature.

In fast PWM mode, the compare units allow generation of PWM waveforms on the OCnx pins.

Setting the COMnx1:0 bits to two will produce a non-inverted PWM and an inverted PWM output can be generated by setting the COMnx1:0 to three (see

Table on page 133

). The actual OCnx value will only be visible on the port pin if the data direction for the port pin is set as output

(DDR_OCnx). The PWM waveform is generated by setting (or clearing) the OCnx Register at the compare match between OCRnx and TCNTn, and clearing (or setting) the OCnx Register at the timer clock cycle the counter is cleared (changes from TOP to BOTTOM).

The PWM frequency for the output can be calculated by the following equation:

f

OCnxPWM

=

N

⋅ (

f

clk_I/O

1

+

TOP

)

The N variable represents the prescaler divider (1, 8, 64, 256, or 1024).

The extreme values for the OCRnx Register represents special cases when generating a PWM waveform output in the fast PWM mode. If the OCRnx is set equal to BOTTOM (0x0000) the output will be a narrow spike for each TOP+1 timer clock cycle. Setting the OCRnx equal to TOP will result in a constant high or low output (depending on the polarity of the output set by the

COMnx1:0 bits.)

A frequency (with 50% duty cycle) waveform output in fast PWM mode can be achieved by setting OCnA to toggle its logical level on each compare match (COMnA1:0 = 1). This applies only if OCR1A is used to define the TOP value (WGM13:0 = 15). The waveform generated will have a maximum frequency of f

OC n

A

= f clk_I/O

/2 when OCRnA is set to zero (0x0000). This feature is similar to the OCnA toggle in CTC mode, except the double buffer feature of the Output Compare unit is enabled in the fast PWM mode.

Phase Correct PWM mode

The phase correct Pulse Width Modulation or phase correct PWM mode (WGMn3:0 = 1, 2, 3,

10, or 11) provides a high resolution phase correct PWM waveform generation option. The phase correct PWM mode is, like the phase and frequency correct PWM mode, based on a dualslope operation. The counter counts repeatedly from BOTTOM (0x0000) to TOP and then from

TOP to BOTTOM. In non-inverting Compare Output mode, the Output Compare (OCnx) is cleared on the compare match between TCNTn and OCRnx while upcounting, and set on the compare match while downcounting. In inverting Output Compare mode, the operation is inverted. The dual-slope operation has lower maximum operation frequency than single slope

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operation. However, due to the symmetric feature of the dual-slope PWM modes, these modes are preferred for motor control applications.

The PWM resolution for the phase correct PWM mode can be fixed to 8-, 9-, or 10-bit, or defined by either ICRn or OCRnA. The minimum resolution allowed is 2-bit (ICRn or OCRnA set to

0x0003), and the maximum resolution is 16-bit (ICRn or OCRnA set to MAX). The PWM resolution in bits can be calculated by using the following equation:

R

PCPWM

= log

(

TOP

log

( )

+

1

)

-----------------------------------

In phase correct PWM mode the counter is incremented until the counter value matches either one of the fixed values 0x00FF, 0x01FF, or 0x03FF (WGMn3:0 = 1, 2, or 3), the value in ICRn

(WGMn3:0 = 10), or the value in OCRnA (WGMn3:0 = 11). The counter has then reached the

TOP and changes the count direction. The TCNTn value will be equal to TOP for one timer clock cycle. The timing diagram for the phase correct PWM mode is shown on

Figure 16-8

. The figure shows phase correct PWM mode when OCRnA or ICRn is used to define TOP. The TCNTn value is in the timing diagram shown as a histogram for illustrating the dual-slope operation. The diagram includes non-inverted and inverted PWM outputs. The small horizontal line marks on the TCNTn slopes represent compare matches between OCRnx and TCNTn. The OCnx Interrupt Flag will be set when a compare match occurs.

Figure 16-8.

Phase Correct PWM mode, timing diagram.

OCRnx/TOP Update and

OCnA Interrupt Flag Set or ICFn Interrupt Flag Set

(Interrupt on TOP)

TOVn Interrupt Flag Set

(Interrupt on Bottom)

TCNTn

OCnx

OCnx

(COMnx1:0 = 2)

(COMnx1:0 = 3)

Period

1 2 3 4

The Timer/Counter Overflow Flag (TOVn) is set each time the counter reaches BOTTOM. When either OCRnA or ICRn is used for defining the TOP value, the OCnA or ICFn Flag is set accordingly at the same timer clock cycle as the OCRnx Registers are updated with the double buffer value (at TOP). The Interrupt Flags can be used to generate an interrupt each time the counter reaches the TOP or BOTTOM value.

When changing the TOP value the program must ensure that the new TOP value is higher or equal to the value of all of the Compare Registers. If the TOP value is lower than any of the

Compare Registers, a compare match will never occur between the TCNTn and the OCRnx.

Note that when using fixed TOP values, the unused bits are masked to zero when any of the

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OCRnx Registers are written. As the third period shown in Figure 16-8

illustrates, changing the

TOP actively while the Timer/Counter is running in the phase correct mode can result in an unsymmetrical output. The reason for this can be found in the time of update of the OCRnx Register. Since the OCRnx update occurs at TOP, the PWM period starts and ends at TOP. This implies that the length of the falling slope is determined by the previous TOP value, while the length of the rising slope is determined by the new TOP value. When these two values differ the two slopes of the period will differ in length. The difference in length gives the unsymmetrical result on the output.

It is recommended to use the phase and frequency correct mode instead of the phase correct mode when changing the TOP value while the Timer/Counter is running. When using a static

TOP value there are practically no differences between the two modes of operation.

In phase correct PWM mode, the compare units allow generation of PWM waveforms on the

OCnx pins. Setting the COMnx1:0 bits to two will produce a non-inverted PWM and an inverted

PWM output can be generated by setting the COMnx1:0 to three (See Table on page 133 ). The

actual OCnx value will only be visible on the port pin if the data direction for the port pin is set as output (DDR_OCnx). The PWM waveform is generated by setting (or clearing) the OCnx Register at the compare match between OCRnx and TCNTn when the counter increments, and clearing (or setting) the OCnx Register at compare match between OCRnx and TCNTn when the counter decrements. The PWM frequency for the output when using phase correct PWM can be calculated by the following equation:

f

OCnxPCPWM

=

f

clk_I/O

----------------------------

16.9.5

The N variable represents the prescaler divider (1, 8, 64, 256, or 1024).

The extreme values for the OCRnx Register represent special cases when generating a PWM waveform output in the phase correct PWM mode. If the OCRnx is set equal to BOTTOM the output will be continuously low and if set equal to TOP the output will be continuously high for non-inverted PWM mode. For inverted PWM the output will have the opposite logic values. If

OCR1A is used to define the TOP value (WGM13:0 = 11) and COM1A1:0 = 1, the OC1A output will toggle with a 50% duty cycle.

Phase and Frequency Correct PWM mode

The phase and frequency correct Pulse Width Modulation, or phase and frequency correct PWM mode (WGMn3:0 = 8 or 9) provides a high resolution phase and frequency correct PWM waveform generation option. The phase and frequency correct PWM mode is, like the phase correct

PWM mode, based on a dual-slope operation. The counter counts repeatedly from BOTTOM

(0x0000) to TOP and then from TOP to BOTTOM. In non-inverting Compare Output mode, the

Output Compare (OCnx) is cleared on the compare match between TCNTn and OCRnx while upcounting, and set on the compare match while downcounting. In inverting Compare Output mode, the operation is inverted. The dual-slope operation gives a lower maximum operation frequency compared to the single-slope operation. However, due to the symmetric feature of the dual-slope PWM modes, these modes are preferred for motor control applications.

The main difference between the phase correct, and the phase and frequency correct PWM mode is the time the OCRnx Register is updated by the OCRnx Buffer Register, (see

Figure 16-

8

and Figure 16-9 ).

The PWM resolution for the phase and frequency correct PWM mode can be defined by either

ICRn or OCRnA. The minimum resolution allowed is 2-bit (ICRn or OCRnA set to 0x0003), and

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the maximum resolution is 16-bit (ICRn or OCRnA set to MAX). The PWM resolution in bits can be calculated using the following equation:

R

PFCPWM

= log

(

TOP

log

( )

+

1

)

-----------------------------------

In phase and frequency correct PWM mode the counter is incremented until the counter value matches either the value in ICRn (WGMn3:0 = 8), or the value in OCRnA (WGMn3:0 = 9). The counter has then reached the TOP and changes the count direction. The TCNTn value will be equal to TOP for one timer clock cycle. The timing diagram for the phase correct and frequency

correct PWM mode is shown on Figure 16-9 . The figure shows phase and frequency correct

PWM mode when OCRnA or ICRn is used to define TOP. The TCNTn value is in the timing diagram shown as a histogram for illustrating the dual-slope operation. The diagram includes noninverted and inverted PWM outputs. The small horizontal line marks on the TCNTn slopes represent compare matches between OCRnx and TCNTn. The OCnx Interrupt Flag will be set when a compare match occurs.

Figure 16-9.

Phase and Frequency Correct PWM mode, timing diagram.

OCnA Interrupt Flag Set or ICFn Interrupt Flag Set

(Interrupt on TOP)

OCRnx/TOP Updateand

TOVn Interrupt Flag Set

(Interrupt on Bottom)

TCNTn

OCnx

OCnx

(COMnx1:0 = 2)

(COMnx1:0 = 3)

Period

1 2 3 4

The Timer/Counter Overflow Flag (TOVn) is set at the same timer clock cycle as the OCRnx

Registers are updated with the double buffer value (at BOTTOM). When either OCRnA or ICRn is used for defining the TOP value, the OCnA or ICFn Flag set when TCNTn has reached TOP.

The Interrupt Flags can then be used to generate an interrupt each time the counter reaches the

TOP or BOTTOM value.

When changing the TOP value the program must ensure that the new TOP value is higher or equal to the value of all of the Compare Registers. If the TOP value is lower than any of the

Compare Registers, a compare match will never occur between the TCNTn and the OCRnx.

As Figure 16-9

shows the output generated is, in contrast to the phase correct mode, symmetrical in all periods. Since the OCRnx Registers are updated at BOTTOM, the length of the rising and the falling slopes will always be equal. This gives symmetrical output pulses and is therefore frequency correct.

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Using the ICRn Register for defining TOP works well when using fixed TOP values. By using

ICRn, the OCRnA Register is free to be used for generating a PWM output on OCnA. However, if the base PWM frequency is actively changed by changing the TOP value, using the OCRnA as

TOP is clearly a better choice due to its double buffer feature.

In phase and frequency correct PWM mode, the compare units allow generation of PWM waveforms on the OCnx pins. Setting the COMnx1:0 bits to two will produce a non-inverted PWM and

an inverted PWM output can be generated by setting the COMnx1:0 to three (See Table 16-4 on page 133

). The actual OCnx value will only be visible on the port pin if the data direction for the port pin is set as output (DDR_OCnx). The PWM waveform is generated by setting (or clearing) the OCnx Register at the compare match between OCRnx and TCNTn when the counter increments, and clearing (or setting) the OCnx Register at compare match between OCRnx and

TCNTn when the counter decrements. The PWM frequency for the output when using phase and frequency correct PWM can be calculated by the following equation:

f

OCnxPFCPWM

=

f

clk_I/O

----------------------------

The N variable represents the prescaler divider (1, 8, 64, 256, or 1024).

The extreme values for the OCRnx Register represents special cases when generating a PWM waveform output in the phase correct PWM mode. If the OCRnx is set equal to BOTTOM the output will be continuously low and if set equal to TOP the output will be set to high for noninverted PWM mode. For inverted PWM the output will have the opposite logic values. If OCR1A is used to define the TOP value (WGM13:0 = 9) and COM1A1:0 = 1, the OC1A output will toggle with a 50% duty cycle.

16.10 Timer/Counter Timing diagrams

The Timer/Counter is a synchronous design and the timer clock (clk

Tn

) is therefore shown as a clock enable signal in the following figures. The figures include information on when Interrupt

Flags are set, and when the OCRnx Register is updated with the OCRnx buffer value (only for modes utilizing double buffering).

Figure 16-10

shows a timing diagram for the setting of OCFnx.

Figure 16-10.

Timer/Counter Timing diagram, setting of OCFnx, no prescaling.

clk

I/O clk

(clk

I/O

Tn

/1)

TCNTn

OCRnx

OCRnx - 1 OCRnx

OCRnx Value

OCRnx + 1 OCRnx + 2

OCFnx

Figure 16-11

shows the same timing data, but with the prescaler enabled.

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Figure 16-11.

Timer/Counter Timing diagram, setting of OCFnx, with prescaler (f clk_I/O

/8).

clk

I/O clk

(clk

I/O

Tn

/8)

TCNTn OCRnx - 1 OCRnx OCRnx + 1 OCRnx + 2

OCRnx Value OCRnx

OCFnx

Figure 16-12

shows the count sequence close to TOP in various modes. When using phase and frequency correct PWM mode the OCRnx Register is updated at BOTTOM. The timing diagrams will be the same, but TOP should be replaced by BOTTOM, TOP-1 by BOTTOM+1 and so on.

The same renaming applies for modes that set the TOVn Flag at BOTTOM.

Figure 16-12.

Timer/Counter Timing diagram, no prescaling.

clk

I/O clk

(clk

I/O

Tn

/1)

TCNTn

(CTC and FPWM)

TCNTn

(PC and PFC PWM)

TOVn

(FPWM) and ICFn

(if used as TOP)

OCRnx

(Update at TOP)

TOP - 1

TOP - 1

Old OCRnx Value

TOP

TOP

BOTTOM

TOP - 1

BOTTOM + 1

TOP - 2

New OCRnx Value

Figure 16-13

shows the same timing data, but with the prescaler enabled.

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Figure 16-13.

Timer/Counter Timing diagram, with prescaler (f clk_I/O

/8).

clk

I/O clk

Tn

I/O

/8)

TCNTn

(CTC and FPWM)

TCNTn

(PC and PFC PWM)

TOVn

(FPWM) and ICF n

(if used as TOP)

OCRnx

(Update at TOP)

TOP - 1

TOP - 1

Old OCRnx Value

TOP

TOP

BOTTOM

TOP - 1

BOTTOM + 1

TOP - 2

New OCRnx Value

16.11 Register description

16.11.1

TCCRnA – Timer/Counter n Control Register A

Bit

(0x80)

Read/Write

Initial Value

7

COMnA1

R/W

0

6

COMnA0

R/W

0

5

COMnB1

R/W

0

4

COMnB0

R/W

0

R

0

3

R

0

2

1

WGMn1

R/W

0

0

WGMn0

R/W

0

TCCRnA

• Bit 7:6 – COMnA1:0: Compare Output Mode for Channel A

• Bit 5:4 – COMnB1:0: Compare Output Mode for Channel B

The COMnA1:0 and COMnB1:0 control the Output Compare pins (OCnA and OCnB respectively) behavior. If one or both of the COMnA1:0 bits are written to one, the OCnA output overrides the normal port functionality of the I/O pin it is connected to. If one or both of the

COMnB1:0 bit are written to one, the OCnB output overrides the normal port functionality of the

I/O pin it is connected to. However, note that the Data Direction Register (DDR) bit corresponding to the OCnA or OCnB pin must be set in order to enable the output driver.

When the OCnA or OCnB is connected to the pin, the function of the COMnx1:0 bits is depen-

dent of the WGMn3:0 bits setting. Table 16-2 on page 132 shows the COMnx1:0 bit functionality

when the WGMn3:0 bits are set to a Normal or a CTC mode (non-PWM).

Table 16-2.

Compare Output mode, non-PWM.

COMnA1/COMnB1

0

0

1

1

COMnA0/COMnB0 Description

0 Normal port operation, OCnA/OCnB disconnected.

1 Toggle OCnA/OCnB on Compare Match.

0

1

Clear OCnA/OCnB on Compare Match (Set output to low level).

Set OCnA/OCnB on Compare Match (Set output to high level).

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Table 16-3 on page 133

shows the COMnx1:0 bit functionality when the WGMn3:0 bits are set to the fast PWM mode.

Table 16-3.

Compare Output mode, fast PWM

(1)

.

COMnA1/COMnB1 COMnA0/COMnB0 Description

0

0

1

1

0

1

0

1

Normal port operation, OCnA/OCnB disconnected.

WGMn3:0 = 14 or 15: Toggle OC1A on Compare

Match, OC1B disconnected (normal port operation).

For all other WGM1 settings, normal port operation,

OC1A/OC1B disconnected.

Clear OCnA/OCnB on Compare Match, set

OCnA/OCnB at BOTTOM (non-inverting mode)

Set OCnA/OCnB on Compare Match, clear

OCnA/OCnB at BOTTOM (inverting mode)

Note: 1. A special case occurs when OCRnA/OCRnB equals TOP and COMnA1/COMnB1 is set. In this case the compare match is ignored, but the set or clear is done at BOTTOM.

See Section

“16.9.3” on page 124

for more details.

Table 16-4 on page 133

shows the COMnx1:0 bit functionality when the WGMn3:0 bits are set to the phase correct or the phase and frequency correct, PWM mode.

Table 16-4.

Compare Output mode, phase correct and phase and frequency correct PWM

(1)

.

COMnA1/COMnB1

0

0

1

1

COMnA0/COMnB0 Description

0 Normal port operation, OCnA/OCnB disconnected.

1

0

WGMn3:0 = 9 or 11: Toggle OCnA on Compare

Match, OCnB disconnected (normal port operation).

For all other WGM1 settings, normal port operation,

OC1A/OC1B disconnected.

Clear OCnA/OCnB on Compare Match when upcounting. Set OCnA/OCnB on Compare Match when downcounting.

1

Set OCnA/OCnB on Compare Match when upcounting. Clear OCnA/OCnB on Compare Match when downcounting.

Note:

1. A special case occurs when OCRnA/OCRnB equals TOP and COMnA1/COMnB1 is set. See

Section “16.9.4” on page 126 for more details.

• Bit 1:0 – WGMn1:0: Waveform Generation Mode

Combined with the WGMn3:2 bits found in the TCCRnB Register, these bits control the counting sequence of the counter, the source for maximum (TOP) counter value, and what type of waveform generation to be used, see

Table 16-5 on page 134 . Modes of operation supported by the

Timer/Counter unit are: Normal mode (counter), Clear Timer on Compare match (CTC) mode,

and three types of Pulse Width Modulation (PWM) modes. ( See Section “16.9” on page 123

).

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Table 16-5.

Waveform Generation mode bit description

(1)

.

8

9

10

11

12

13

Mode WGMn3

0 0

1 0

4

5

2

3

6

7

0

0

0

0

0

0

1

1

1

1

1

1

WGMn2

(CTCn)

0

0

1

1

0

0

1

1

0

0

1

1

0

0

WGMn1

(PWMn1)

0

0

0

0

1

1

1

1

0

0

0

0

1

1

WGMn0

(PWMn0)

0

1

0

1

0

1

0

1

0

1

0

1

0

1

Timer/Counter mode of operation

Normal

PWM, Phase Correct, 8-bit

PWM, Phase Correct, 9-bit

PWM, Phase Correct, 10-bit

CTC

Fast PWM, 8-bit

Fast PWM, 9-bit

Fast PWM, 10-bit

PWM, Phase and Frequency

Correct

PWM, Phase and Frequency

Correct

PWM, Phase Correct

PWM, Phase Correct

CTC

(Reserved)

TOP

0xFFFF

0x00FF

0x01FF

0x03FF

OCRnA

0x00FF

0x01FF

0x03FF

ICRn

OCRnA

ICRn

OCRnA

ICRn

Update of

OCRn x

at

TOVn flag set on

Immediate MAX

TOP BOTTOM

TOP

TOP

BOTTOM

BOTTOM

Immediate MAX

BOTTOM TOP

BOTTOM

BOTTOM

TOP

TOP

BOTTOM

BOTTOM

BOTTOM

BOTTOM

TOP

TOP

BOTTOM

BOTTOM

Immediate MAX

– –

14 1 1 1 0 Fast PWM ICRn BOTTOM TOP

15 1 1 1 1 Fast PWM OCRnA BOTTOM TOP

Note: 1. The CTCn and PWMn1:0 bit definition names are obsolete. Use the

WGM n2:0 definitions. However, the functionality and location of these bits are compatible with previous versions of the timer.

16.11.2

TCCRnB – Timer/Counter n Control Register B

Bit

(0x81)

Read/Write

Initial Value

7

ICNCn

R/W

0

6

ICESn

R/W

0

R

0

5

4

WGMn3

R/W

0

3

WGMn2

R/W

0

2

CSn2

R/W

0

1

CSn1

R/W

0

0

CSn0

R/W

0

TCCRnB

• Bit 7 – ICNCn: Input Capture Noise Canceler

Setting this bit (to one) activates the Input Capture Noise Canceler. When the noise canceler is activated, the input from the Input Capture pin (ICPn) is filtered. The filter function requires four successive equal valued samples of the ICPn pin for changing its output. The Input Capture is therefore delayed by four Oscillator cycles when the noise canceler is enabled.

• Bit 6 – ICESn: Input Capture Edge Select

This bit selects which edge on the Input Capture pin (ICPn) that is used to trigger a capture event. When the ICESn bit is written to zero, a falling (negative) edge is used as trigger, and when the ICESn bit is written to one, a rising (positive) edge will trigger the capture.

When a capture is triggered according to the ICESn setting, the counter value is copied into the

Input Capture Register (ICRn). The event will also set the Input Capture Flag (ICFn), and this can be used to cause an Input Capture Interrupt, if this interrupt is enabled.

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When the ICRn is used as TOP value (see description of the WGMn3:0 bits located in the

TCCRnA and the TCCRnB Register), the ICPn is disconnected and consequently the Input Capture function is disabled.

• Bit 5 – Reserved

This bit is reserved for future use. For ensuring compatibility with future devices, this bit must be written to zero when TCCRnB is written.

• Bit 4:3 – WGMn3:2: Waveform Generation Mode

See “TCCRnA – Timer/Counter n Control Register A description on page 132

.

• Bit 2:0 – CSn2:0: Clock Select

The three Clock Select bits select the clock source to be used by the Timer/Counter, see

Figure

16-10

and Figure 16-11

.

Table 16-6.

Clock Select bit description.

CSn2

0

0

1

1

0

0

1

1

CSn1

0

0

0

0

1

1

1

1

CSn0

0

1

0

1

0

1

0

1

Description

No clock source (Timer/Counter stopped).

clk

I/O

/1 (No prescaling) clk

I/O

/8 (From prescaler) clk

I/O

/64 (From prescaler) clk

I/O

/256 (From prescaler) clk

I/O

/1024 (From prescaler)

External clock source on Tn pin. Clock on falling edge.

External clock source on Tn pin. Clock on rising edge.

If external pin modes are used for the Timer/Countern, transitions on the Tn pin will clock the counter even if the pin is configured as an output. This feature allows software control of the counting.

16.11.3

TCCRnC – Timer/Counter n Control Register C

Bit

(0x82)

Read/Write

Initial Value

7

FOCnA

R/W

0

6

FOCnB

R/W

0

5

R

0

4

R

0

3

R

0

2

R

0

1

R

0

0

R

0

TCCRnC

• Bit 7 – FOCnA: Force Output Compare for Channel A

• Bit 6 – FOCnB: Force Output Compare for Channel B

The FOCnA/FOCnB bits are only active when the WGMn3:0 bits specifies a non-PWM mode.

However, for ensuring compatibility with future devices, these bits must be set to zero when

TCCRnA is written when operating in a PWM mode. When writing a logical one to the

FOCnA/FOCnB bit, an immediate compare match is forced on the Waveform Generation unit.

The OCnA/OCnB output is changed according to its COMnx1:0 bits setting. Note that the

FOCnA/FOCnB bits are implemented as strobes. Therefore it is the value present in the

COMnx1:0 bits that determine the effect of the forced compare.

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A FOCnA/FOCnB strobe will not generate any interrupt nor will it clear the timer in Clear Timer on Compare match (CTC) mode using OCRnA as TOP.

The FOCnA/FOCnB bits are always read as zero.

16.11.4

TCNT1H and TCNT1L –Timer/Counter1

Bit

(0x85)

(0x84)

Read/Write

Initial Value

7

R/W

0

6

R/W

0

5

R/W

0

4 3

TCNT1[15:8]

TCNT1[7:0]

R/W R/W

0 0

2

R/W

0

1

R/W

0

0

R/W

0

TCNT1H

TCNT1L

The two Timer/Counter I/O locations (TCNT1H and TCNT1L, combined TCNT1) give direct access, both for read and for write operations, to the Timer/Counter unit 16-bit counter. To ensure that both the high and low bytes are read and written simultaneously when the CPU accesses these registers, the access is performed using an 8-bit temporary High Byte Register

(TEMP). This temporary register is shared by all the other 16-bit registers.

See “Accessing 16-bit

Registers” on page 113

.

Modifying the counter (TCNT1) while the counter is running introduces a risk of missing a compare match between TCNT1 and one of the OCRnx Registers.

Writing to the TCNT1 Register blocks (removes) the compare match on the following timer clock for all compare units.

16.11.5

TCNT3H and TCNT3L –Timer/Counter3

Bit

(0x95)

(0x94)

Read/Write

Initial Value

7

R/W

0

6

R/W

0

5

R/W

0

4 3

TCNT3[15:8]

TCNT3[7:0]

R/W R/W

0 0

2

R/W

0

1

R/W

0

0

R/W

0

TCNT3H

TCNT3L

The two Timer/Counter I/O locations (TCNT3H and TCNT3L, combined TCNT3) give direct access, both for read and for write operations, to the Timer/Counter unit 16-bit counter. To ensure that both the high and low bytes are read and written simultaneously when the CPU accesses these registers, the access is performed using an 8-bit temporary High Byte Register

(TEMP). This temporary register is shared by all the other 16-bit registers.

See “Accessing 16-bit

Registers” on page 113

.

Modifying the counter (TCNT3) while the counter is running introduces a risk of missing a compare match between TCNT3 and one of the OCRnx Registers.

Writing to the TCNT3 Register blocks (removes) the compare match on the following timer clock for all compare units.

16.11.6

OCR1AH and OCR1AL – Output Compare Register1 A

Bit

(0x89)

(0x88)

Read/Write

Initial Value

7

R/W

0

6

R/W

0

5

R/W

0

4 3

OCR1A[15:8]

OCR1A[7:0]

R/W R/W

0 0

2

R/W

0

1

R/W

0

0

R/W

0

OCR1AH

OCR1AL

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16.11.7

OCR1BH and OCR1BL – Output Compare Register1 B

Bit

(0x8B)

(0x8A)

Read/Write

Initial Value

7

R/W

0

6

R/W

0

5

R/W

0

4 3

OCR1B[15:8]

OCR1B[7:0]

R/W R/W

0 0

2

R/W

0

1

R/W

0

0

R/W

0

OCR1BH

OCR1BL

The Output Compare Registers contain a 16-bit value that is continuously compared with the counter value (TCNT1). A match can be used to generate an Output Compare interrupt, or to generate a waveform output on the OCnx pin.

The Output Compare Registers are 16-bit in size. To ensure that both the high and low bytes are written simultaneously when the CPU writes to these registers, the access is performed using an

8-bit temporary High Byte Register (TEMP). This temporary register is shared by all the other

16-bit registers.

See “Accessing 16-bit Registers” on page 113 .

16.11.8

OCR3AH and OCR3AL – Output Compare Register3 A

Bit

(0x99)

(0x98)

Read/Write

Initial Value

7

R/W

0

6

R/W

0

5

R/W

0

16.11.9

OCR3BH and OCR3BL – Output Compare Register3 B

4 3

OCR3A[15:8]

OCR3A[7:0]

R/W R/W

0 0

2

R/W

0

1

R/W

0

0

R/W

0

OCR3AH

OCR3AL

Bit

(0x9B)

(0x9A)

Read/Write

Initial Value

7

R/W

0

6

R/W

0

5

R/W

0

4 3

OCR3B[15:8]

OCR3B[7:0]

R/W R/W

0 0

2

R/W

0

1

R/W

0

0

R/W

0

OCR3BH

OCR3BL

The Output Compare Registers contain a 16-bit value that is continuously compared with the counter value (TCNT3). A match can be used to generate an Output Compare interrupt, or to generate a waveform output on the OCnx pin.

The Output Compare Registers are 16-bit in size. To ensure that both the high and low bytes are written simultaneously when the CPU writes to these registers, the access is performed using an

8-bit temporary High Byte Register (TEMP). This temporary register is shared by all the other

16-bit registers.

See “Accessing 16-bit Registers” on page 113 .

16.11.10 ICR1H and ICR1L – Input Capture Register 1

Bit

(0x87)

(0x86)

Read/Write

Initial Value

7

R/W

0

6

R/W

0

5

R/W

0

4 3

ICR1[15:8]

R/W

ICR1[7:0]

R/W

0 0

2

R/W

0

1

R/W

0

0

R/W

0

ICR1H

ICR1L

The Input Capture is updated with the counter (TCNT1) value each time an event occurs on the

ICPn pin (or optionally on the Analog Comparator output for Timer/Counter1). The Input Capture can be used for defining the counter TOP value.

The Input Capture Register is 16-bit in size. To ensure that both the high and low bytes are read simultaneously when the CPU accesses these registers, the access is performed using an 8-bit

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temporary High Byte Register (TEMP). This temporary register is shared by all the other 16-bit

registers. See “Accessing 16-bit Registers” on page 113

.

16.11.11 ICR3H and ICR3L – Input Capture Register 3

Bit

(0x97)

(0x96)

Read/Write

Initial Value

7

R/W

0

6

R/W

0

5

R/W

0

4 3

ICR3[15:8]

R/W

ICR3[7:0]

R/W

0 0

2

R/W

0

1

R/W

0

0

R/W

0

ICR3H

ICR3L

The Input Capture is updated with the counter (TCNT3) value each time an event occurs on the

ICPn pin (or optionally on the Analog Comparator output for Timer/Counter3). The Input Capture can be used for defining the counter TOP value.

The Input Capture Register is 16-bit in size. To ensure that both the high and low bytes are read simultaneously when the CPU accesses these registers, the access is performed using an 8-bit temporary High Byte Register (TEMP). This temporary register is shared by all the other 16-bit

registers. See “Accessing 16-bit Registers” on page 113

.

16.11.12 TIMSK1 – Timer/Counter1 Interrupt Mask Register

Bit

(0x6F)

Read/Write

Initial Value

R

0

7

R

0

6

5

ICIE1

R/W

0

R

0

4

R

0

3

2

OCIE1B

R/W

0

1

OCIE1A

R/W

0

0

TOIE1

R/W

0

TIMSK1

• Bit 7:6 – Reserved

These bits are unused and will always read as zero.

• Bit 5 – ICIE1: Timer/Counter1, Input Capture Interrupt Enable

When this bit is written to one, and the I-flag in the Status Register is set (interrupts globally enabled), the Timer/Counter1 Input Capture interrupt is enabled. The corresponding Interrupt

Vector (

see “Interrupts” on page 61 ) is executed when the ICF1 Flag, located in TIFR1, is set.

• Bit 4:3 – Reserved

These bits are unused and will always read as zero.

• Bit 2 – OCIE1B: Timer/Counter1, Output Compare B Match Interrupt Enable

When this bit is written to one, and the I-flag in the Status Register is set (interrupts globally enabled), the Timer/Counter1 Output Compare B Match interrupt is enabled. The corresponding

Interrupt Vector (

see “Interrupts” on page 61 ) is executed when the OCF1B Flag, located in

TIFR1, is set.

• Bit 1 – OCIE1A: Timer/Counter1, Output Compare A Match Interrupt Enable

When this bit is written to one, and the I-flag in the Status Register is set (interrupts globally enabled), the Timer/Counter1 Output Compare A Match interrupt is enabled. The corresponding

Interrupt Vector (

see “Interrupts” on page 61 ) is executed when the OCF1A Flag, located in

TIFR1, is set.

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• Bit 0 – TOIE1: Timer/Counter1, Overflow Interrupt Enable

When this bit is written to one, and the I-flag in the Status Register is set (interrupts globally enabled), the Timer/Counter1 Overflow interrupt is enabled. The corresponding Interrupt Vector

( See Section “11.3” on page 55 ) is executed when the TOV1 Flag, located in TIFR1, is set.

16.11.13 TIMSK3 – Timer/Counter3 Interrupt Mask Register

Bit

(0x71)

Read/Write

Initial Value

R

0

7

R

0

6

5

ICIE3

R/W

0

R

0

4

R

0

3

2

OCIE3B

R/W

0

1

OCIE3A

R/W

0

0

TOIE3

R/W

0

TIMSK3

• Bit 7:6 – Reserved

These bits are unused and will always read as zero.

• Bit 5 – ICIE3: Timer/Counter3, Input Capture Interrupt Enable

When this bit is written to one, and the I-flag in the Status Register is set (interrupts globally enabled), the Timer/Counter1 Input Capture interrupt is enabled. The corresponding Interrupt

Vector (

See “Interrupts” on page 61

) is executed when the ICF3 Flag, located in TIFR3, is set.

• Bit 4:3 – Reserved

These bits are unused and will always read as zero.

• Bit 2 – OCIE3B: Timer/Counter3, Output Compare B Match Interrupt Enable

When this bit is written to one, and the I-flag in the Status Register is set (interrupts globally enabled), the Timer/Counter3 Output Compare B Match interrupt is enabled. The corresponding

Interrupt Vector ( See “Interrupts” on page 61

) is executed when the OCF3B Flag, located in

TIFR3, is set.

• Bit 1 – OCIE3A: Timer/Counter3, Output Compare A Match Interrupt Enable

When this bit is written to one, and the I-flag in the Status Register is set (interrupts globally enabled), the Timer/Counter3 Output Compare A Match interrupt is enabled. The corresponding

Interrupt Vector ( See “Interrupts” on page 61

) is executed when the OCF3A Flag, located in

TIFR3, is set.

• Bit 0 – TOIE3: Timer/Counter3, Overflow Interrupt Enable

When this bit is written to one, and the I-flag in the Status Register is set (interrupts globally enabled), the Timer/Counter3 Overflow interrupt is enabled. The corresponding Interrupt Vector

( See “Watchdog Timer” on page 55

) is executed when the TOV3 Flag, located in TIFR3, is set.

16.11.14 TIFR1 – Timer/Counter1 Interrupt Flag Register

Bit

0x16 (0x36)

Read/Write

Initial Value

R

0

7

R

0

6

5

ICF1

R/W

0

R

0

4

• Bit 7:6 – Reserved

These bits are unused and will always read as zero.

R

0

3

2

OCF1B

R/W

0

1

OCF1A

R/W

0

0

TOV1

R/W

0

TIFR1

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• Bit 5 – ICF1: Timer/Counter1, Input Capture Flag

This flag is set when a capture event occurs on the ICP1 pin. When the Input Capture Register

(ICR1) is set by the WGMn3:0 to be used as the TOP value, the ICF1 Flag is set when the counter reaches the TOP value.

ICF1 is automatically cleared when the Input Capture Interrupt Vector is executed. Alternatively,

ICF1 can be cleared by writing a logic one to its bit location.

• Bit 4:3 – Reserved

These bits are unused and will always read as zero.

• Bit 2 – OCF1B: Timer/Counter1, Output Compare B Match Flag

This flag is set in the timer clock cycle after the counter (TCNT1) value matches the Output

Compare Register B (OCR1B).

Note that a Forced Output Compare (FOC1B) strobe will not set the OCF1B Flag.

OCF1B is automatically cleared when the Output Compare Match B Interrupt Vector is executed. Alternatively, OCF1B can be cleared by writing a logic one to its bit location.

• Bit 1 – OCF1A: Timer/Counter1, Output Compare A Match Flag

This flag is set in the timer clock cycle after the counter (TCNT1) value matches the Output

Compare Register A (OCR1A).

Note that a Forced Output Compare (FOC1A) strobe will not set the OCF1A Flag.

OCF1A is automatically cleared when the Output Compare Match A Interrupt Vector is executed. Alternatively, OCF1A can be cleared by writing a logic one to its bit location.

• Bit 0 – TOV1: Timer/Counter1, Overflow Flag

The setting of this flag is dependent of the WGMn3:0 bits setting. In Normal and CTC modes, the TOV1 Flag is set when the timer overflows. Refer to

Table 16-5 on page 134 for the TOV1

Flag behavior when using another WGMn3:0 bit setting.

TOV1 is automatically cleared when the Timer/Counter1 Overflow Interrupt Vector is executed.

Alternatively, TOV1 can be cleared by writing a logic one to its bit location.

16.11.15 TIFR3 – Timer/Counter3 Interrupt Flag Register

Bit

0x18 (0x38)

Read/Write

Initial Value

R

0

7

R

0

6

5

ICF3

R/W

0

R

0

4

R

0

3

2

OCF3B

R/W

0

1

OCF3A

R/W

0

0

TOV3

R/W

0

TIFR3

• Bit 7:6 – Reserved

These bits are unused and will always read as zero.

• Bit 5 – ICF3: Timer/Counter3, Input Capture Flag

This flag is set when a capture event occurs on the ICP3 pin. When the Input Capture Register

(ICR1) is set by the WGMn3:0 to be used as the TOP value, the ICF3 Flag is set when the counter reaches the TOP value.

ICF3 is automatically cleared when the Input Capture Interrupt Vector is executed. Alternatively,

ICF3 can be cleared by writing a logic one to its bit location.

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• Bit 4:3 – Reserved

These bits are unused and will always read as zero.

• Bit 2 – OCF3B: Timer/Counter3, Output Compare B Match Flag

This flag is set in the timer clock cycle after the counter (TCNT3) value matches the Output

Compare Register B (OCR3B).

Note that a Forced Output Compare (FOC3B) strobe will not set the OCF3B Flag.

OCF3B is automatically cleared when the Output Compare Match B Interrupt Vector is executed. Alternatively, OCF3B can be cleared by writing a logic one to its bit location.

• Bit 1 – OCF3A: Timer/Counter3, Output Compare A Match Flag

This flag is set in the timer clock cycle after the counter (TCNT3) value matches the Output

Compare Register A (OCR3A).

Note that a Forced Output Compare (FOC3A) strobe will not set the OCF3A Flag.

OCF3A is automatically cleared when the Output Compare Match A Interrupt Vector is executed. Alternatively, OCF3A can be cleared by writing a logic one to its bit location.

• Bit 0 – TOV3: Timer/Counter1, Overflow Flag

The setting of this flag is dependent of the WGMn3:0 bits setting. In Normal and CTC modes, the TOV3 Flag is set when the timer overflows. Refer to

Table 16-5 on page 134 for the TOV3

Flag behavior when using another WGMn3:0 bit setting.

TOV3 is automatically cleared when the Timer/Counter3 Overflow Interrupt Vector is executed.

Alternatively, TOV3 can be cleared by writing a logic one to its bit location.

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17. 8-bit Timer/Counter2 with PWM and asynchronous operation

17.1

Features

Single channel counter

Clear Timer on Compare Match (Auto Reload)

Glitch-free, phase correct Pulse Width Modulator (PWM)

Frequency generator

10-bit clock prescaler

Overflow and Compare Match Interrupt Sources (TOV2, OCF2A and OCF2B)

Allows clocking from external 32kHz watch crystal independent of the I/O clock

17.2

Overview

Timer/Counter2 is a general purpose, single channel, 8-bit Timer/Counter module.

A simplified block diagram of the 8-bit Timer/Counter is shown in

Figure 16-12.

. For the actual

placement of I/O pins, see ”Pin configurations” on page 2 . CPU accessible I/O Registers, includ-

ing I/O bits and I/O pins, are shown in bold. The device-specific I/O Register and bit locations

are listed in the ”Register description” on page 156

.

The Power Reduction Timer/Counter2 bit, PRTIM2, in

”PRR0 – Power Reduction Register 0” on page 48 must be written to zero to enable Timer/Counter2 module.

Figure 17-1.

8-bit Timer/Counter block diagram.

Count

Clear

Direction

Control Logic clk

Tn

TOP BOTTOM

Prescaler

Timer/Counter

TCNTn

Status flags

=

OCRnA

=

OCRnB

= =

0

OCnA

(Int.Req.)

Waveform

Generation

Fixed

TOP

Value

OCnB

(Int.Req.)

Waveform

Generation

Synchronized Status flags asynchronous mode

select (ASn)

ASSRn

Synchronization Unit

TOVn

(Int.Req.)

T/C

Oscillator clk

I/O

TOSC1

TOSC2

OCnA

OCnB

clk

I/O clk

ASY

TCCRnA TCCRnB

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17.2.1

Registers

The Timer/Counter (TCNT2) and Output Compare Register (OCR2A and OCR2B) are 8-bit registers. Interrupt request (abbreviated to Int.Req.) signals are all visible in the Timer Interrupt Flag

Register (TIFR2). All interrupts are individually masked with the Timer Interrupt Mask Register

(TIMSK2). TIFR2 and TIMSK2 are not shown in the figure.

The Timer/Counter can be clocked internally, via the prescaler, or asynchronously clocked from the TOSC1/2 pins, as detailed later in this section. The asynchronous operation is controlled by the Asynchronous Status Register (ASSR). The Clock Select logic block controls which clock source the Timer/Counter uses to increment (or decrement) its value. The Timer/Counter is inactive when no clock source is selected. The output from the Clock Select logic is referred to as the timer clock (clk

T2

).

The double buffered Output Compare Register (OCR2A and OCR2B) are compared with the

Timer/Counter value at all times. The result of the compare can be used by the Waveform Generator to generate a PWM or variable frequency output on the Output Compare pins (OC2A and

OC2B).

See “Output Compare unit” on page 144

for details. The compare match event will also set the Compare Flag (OCF2A or OCF2B) which can be used to generate an Output Compare interrupt request.

17.2.2

Definitions

Many register and bit references in this document are written in general form. A lower case “n” replaces the Timer/Counter number, in this case 2. However, when using the register or bit defines in a program, the precise form must be used, that is, TCNT2 for accessing

Timer/Counter2 counter value and so on.

The definitions in Table 17-1 are also used extensively throughout the section.

Table 17-1.

Definitions.

BOTTOM The counter reaches the BOTTOM when it becomes zero (0x00).

MAX

TOP

The counter reaches its MAXimum when it becomes 0xFF (decimal 255).

The counter reaches the TOP when it becomes equal to the highest value in the count sequence. The TOP value can be assigned to be the fixed value 0xFF

(MAX) or the value stored in the OCR2A Register. The assignment is dependent on the mode of operation.

17.3

Timer/Counter clock sources

The Timer/Counter can be clocked by an internal synchronous or an external asynchronous clock source. The clock source clk

T2

is by default equal to the MCU clock, clk

I/O

. When the AS2 bit in the ASSR Register is written to logic one, the clock source is taken from the Timer/Counter

Oscillator connected to TOSC1 and TOSC2. For details on asynchronous operation, see ”ASSR

– Asynchronous Status Register” on page 160 . For details on clock sources and prescaler, see

”Timer/Counter Prescaler” on page 155

.

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17.4

Counter unit

The main part of the 8-bit Timer/Counter is the programmable bi-directional counter unit.

Figure

17-2

shows a block diagram of the counter and its surrounding environment.

Figure 17-2.

Counter Unit block diagram.

DATA BUS

TOVn

(Int.Req.)

TOSC1

TCNTn

count clear direction

Control Logic clk

Tn

Prescaler

T/C

Oscillator

TOSC2

bottom top clk

I/O

Signal description (internal signals):

count direction

Increment or decrement TCNT2 by 1.

Selects between increment and decrement.

clear clk top

Tn

Clear TCNT2 (set all bits to zero).

Timer/Counter clock, referred to as clk

T2 in the following.

Signalizes that TCNT2 has reached maximum value.

Signalizes that TCNT2 has reached minimum value (zero).

bottom

Depending on the mode of operation used, the counter is cleared, incremented, or decremented at each timer clock (clk

T2

). clk

T2

can be generated from an external or internal clock source, selected by the Clock Select bits (CS22:0). When no clock source is selected (CS22:0 = 0) the timer is stopped. However, the TCNT2 value can be accessed by the CPU, regardless of whether clk

T2

is present or not. A CPU write overrides (has priority over) all counter clear or count operations.

The counting sequence is determined by the setting of the WGM21 and WGM20 bits located in the Timer/Counter Control Register (TCCR2A) and the WGM22 located in the Timer/Counter

Control Register B (TCCR2B). There are close connections between how the counter behaves

(counts) and how waveforms are generated on the Output Compare outputs OC2A and OC2B.

For more details about advanced counting sequences and waveform generation, see ”Modes of operation” on page 147

.

The Timer/Counter Overflow Flag (TOV2) is set according to the mode of operation selected by the WGM22:0 bits. TOV2 can be used for generating a CPU interrupt.

17.5

Output Compare unit

The 8-bit comparator continuously compares TCNT2 with the Output Compare Register

(OCR2A and OCR2B). Whenever TCNT2 equals OCR2A or OCR2B, the comparator signals a match. A match will set the Output Compare Flag (OCF2A or OCF2B) at the next timer clock cycle. If the corresponding interrupt is enabled, the Output Compare Flag generates an Output

Compare interrupt. The Output Compare Flag is automatically cleared when the interrupt is executed. Alternatively, the Output Compare Flag can be cleared by software by writing a logical one to its I/O bit location. The Waveform Generator uses the match signal to generate an output

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according to operating mode set by the WGM22:0 bits and Compare Output mode (COM2x1:0) bits. The max and bottom signals are used by the Waveform Generator for handling the special cases of the extreme values in some modes of operation (see

”Modes of operation” on page

147 ).

Figure 16-10 on page 130

shows a block diagram of the Output Compare unit.

Figure 17-3.

Output Compare unit, block diagram.

DATA BUS

OCRnx TCNTn

=

(8-bit Comparator )

OCFn

x (Int.Req.) top bottom

FOCn

Waveform Generator

OCnx

17.5.1

17.5.2

WGMn1:0 COMnX1:0

The OCR2x Register is double buffered when using any of the Pulse Width Modulation (PWM) modes. For the Normal and Clear Timer on Compare (CTC) modes of operation, the double buffering is disabled. The double buffering synchronizes the update of the OCR2x Compare

Register to either top or bottom of the counting sequence. The synchronization prevents the occurrence of odd-length, non-symmetrical PWM pulses, thereby making the output glitch-free.

The OCR2x Register access may seem complex, but this is not case. When the double buffering is enabled, the CPU has access to the OCR2x Buffer Register, and if double buffering is disabled the CPU will access the OCR2x directly.

Force Output Compare

In non-PWM waveform generation modes, the match output of the comparator can be forced by writing a one to the Force Output Compare (FOC2x) bit. Forcing compare match will not set the

OCF2x Flag or reload/clear the timer, but the OC2x pin will be updated as if a real compare match had occurred (the COM2x1:0 bits settings define whether the OC2x pin is set, cleared or toggled).

Compare Match Blocking by TCNT2 Write

All CPU write operations to the TCNT2 Register will block any compare match that occurs in the next timer clock cycle, even when the timer is stopped. This feature allows OCR2x to be initialized to the same value as TCNT2 without triggering an interrupt when the Timer/Counter clock is enabled.

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17.5.3

Using the Output Compare Unit

Since writing TCNT2 in any mode of operation will block all compare matches for one timer clock cycle, there are risks involved when changing TCNT2 when using the Output Compare channel, independently of whether the Timer/Counter is running or not. If the value written to TCNT2 equals the OCR2x value, the compare match will be missed, resulting in incorrect waveform generation. Similarly, do not write the TCNT2 value equal to BOTTOM when the counter is downcounting.

The setup of the OC2x should be performed before setting the Data Direction Register for the port pin to output. The easiest way of setting the OC2x value is to use the Force Output Compare (FOC2x) strobe bit in Normal mode. The OC2x Register keeps its value even when changing between Waveform Generation modes.

Be aware that the COM2x1:0 bits are not double buffered together with the compare value.

Changing the COM2x1:0 bits will take effect immediately.

17.6

Compare Match Output unit

The Compare Output mode (COM2x1:0) bits have two functions. The Waveform Generator uses the COM2x1:0 bits for defining the Output Compare (OC2x) state at the next compare match.

Also, the COM2x1:0 bits control the OC2x pin output source. Figure 17-4 shows a simplified

schematic of the logic affected by the COM2x1:0 bit setting. The I/O Registers, I/O bits, and I/O pins in the figure are shown in bold. Only the parts of the general I/O Port Control Registers

(DDR and PORT) that are affected by the COM2x1:0 bits are shown. When referring to the

OC2x state, the reference is for the internal OC2x Register, not the OC2x pin.

Figure 17-4.

Compare Match Output unit, schematic.

COMnx1

COMnx0

FOCnx

Waveform

Generator

D Q

OCnx

D Q

1

0

OCnx

Pin

PORT

D Q

DDR

clk

I/O

The general I/O port function is overridden by the Output Compare (OC2x) from the Waveform

Generator if either of the COM2x1:0 bits are set. However, the OC2x pin direction (input or output) is still controlled by the Data Direction Register (DDR) for the port pin. The Data Direction

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17.6.1

Register bit for the OC2x pin (DDR_OC2x) must be set as output before the OC2x value is visible on the pin. The port override function is independent of the Waveform Generation mode.

The design of the Output Compare pin logic allows initialization of the OC2x state before the output is enabled. Note that some COM2x1:0 bit settings are reserved for certain modes of

operation. See ”Register description” on page 156

.

Compare Output Mode and Waveform Generation

The Waveform Generator uses the COM2x1:0 bits differently in normal, CTC, and PWM modes.

For all modes, setting the COM2x1:0 = 0 tells the Waveform Generator that no action on the

OC2x Register is to be performed on the next compare match. For compare output actions in the

non-PWM modes refer to Table 17-5 on page 157 . For fast PWM mode, refer to Table 17-6 on page 157

, and for phase correct PWM refer to

Table 17-7 on page 158 .

A change of the COM2x1:0 bits state will have effect at the first compare match after the bits are written. For non-PWM modes, the action can be forced to have immediate effect by using the

FOC2x strobe bits.

17.7

Modes of operation

17.7.1

17.7.2

The mode of operation, that is, the behavior of the Timer/Counter and the Output Compare pins, is defined by the combination of the Waveform Generation mode (WGM22:0) and Compare Output mode (COM2x1:0) bits. The Compare Output mode bits do not affect the counting sequence, while the Waveform Generation mode bits do. The COM2x1:0 bits control whether the PWM output generated should be inverted or not (inverted or non-inverted PWM). For non-PWM modes the COM2x1:0 bits control whether the output should be set, cleared, or toggled at a compare

match ( See “Compare Match Output unit” on page 146

).

For detailed timing information refer to

”Timer/Counter Timing diagrams” on page 151

.

Normal Mode

The simplest mode of operation is the Normal mode (WGM22:0 = 0). In this mode the counting direction is always up (incrementing), and no counter clear is performed. The counter simply overruns when it passes its maximum 8-bit value (TOP = 0xFF) and then restarts from the bottom (0x00). In normal operation the Timer/Counter Overflow Flag (TOV2) will be set in the same timer clock cycle as the TCNT2 becomes zero. The TOV2 Flag in this case behaves like a ninth bit, except that it is only set, not cleared. However, combined with the timer overflow interrupt that automatically clears the TOV2 Flag, the timer resolution can be increased by software.

There are no special cases to consider in the Normal mode, a new counter value can be written anytime.

The Output Compare unit can be used to generate interrupts at some given time. Using the Output Compare to generate waveforms in Normal mode is not recommended, since this will occupy too much of the CPU time.

Clear Timer on Compare Match (CTC) Mode

In Clear Timer on Compare or CTC mode (WGM22:0 = 2), the OCR2A Register is used to manipulate the counter resolution. In CTC mode the counter is cleared to zero when the counter value (TCNT2) matches the OCR2A. The OCR2A defines the top value for the counter, hence also its resolution. This mode allows greater control of the compare match output frequency. It also simplifies the operation of counting external events.

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The timing diagram for the CTC mode is shown in

Table 17-5 on page 148

. The counter value

(TCNT2) increases until a compare match occurs between TCNT2 and OCR2A, and then counter (TCNT2) is cleared.

Figure 17-5.

CTC mode, timing diagram.

OCnx Interrupt Flag Set

TCNTn

OCnx

(Toggle)

Period

1 2 3 4

(COMnx1:0 = 1)

17.7.3

An interrupt can be generated each time the counter value reaches the TOP value by using the

OCF2A Flag. If the interrupt is enabled, the interrupt handler routine can be used for updating the TOP value. However, changing TOP to a value close to BOTTOM when the counter is running with none or a low prescaler value must be done with care since the CTC mode does not have the double buffering feature. If the new value written to OCR2A is lower than the current value of TCNT2, the counter will miss the compare match. The counter will then have to count to its maximum value (0xFF) and wrap around starting at 0x00 before the compare match can occur.

For generating a waveform output in CTC mode, the OC2A output can be set to toggle its logical level on each compare match by setting the Compare Output mode bits to toggle mode

(COM2A1:0 = 1). The OC2A value will not be visible on the port pin unless the data direction for the pin is set to output. The waveform generated will have a maximum frequency of f

OC2A

= f clk_I/O

/2 when OCR2A is set to zero (0x00). The waveform frequency is defined by the following equation:

f

OCnx

=

⋅ ⋅

f

( clk_I/O

1

+

OCRnx

)

The N variable represents the prescale factor (1, 8, 32, 64, 128, 256, or 1024).

As for the Normal mode of operation, the

TOV2

Flag is set in the same timer clock cycle that the counter counts from MAX to 0x00.

Fast PWM mode

The fast Pulse Width Modulation or fast PWM mode (WGM22:0 = 3 or 7) provides a high frequency PWM waveform generation option. The fast PWM differs from the other PWM option by its single-slope operation. The counter counts from BOTTOM to TOP then restarts from BOT-

TOM. TOP is defined as 0xFF when WGM22:0 = 3, and OCR2A when MGM22:0 = 7. In noninverting Compare Output mode, the Output Compare (OC2x) is cleared on the compare match between TCNT2 and OCR2x, and set at BOTTOM. In inverting Compare Output mode, the output is set on compare match and cleared at BOTTOM. Due to the single-slope operation, the operating frequency of the fast PWM mode can be twice as high as the phase correct PWM mode that uses dual-slope operation. This high frequency makes the fast PWM mode well suited

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for power regulation, rectification, and DAC applications. High frequency allows physically small sized external components (coils, capacitors), and therefore reduces total system cost.

In fast PWM mode, the counter is incremented until the counter value matches the TOP value.

The counter is then cleared at the following timer clock cycle. The timing diagram for the fast

PWM mode is shown in

Figure 17-6 on page 149 . The TCNT2 value is in the timing diagram

shown as a histogram for illustrating the single-slope operation. The diagram includes noninverted and inverted PWM outputs. The small horizontal line marks on the TCNT2 slopes represent compare matches between OCR2x and TCNT2.

Figure 17-6.

Fast PWM mode, timing diagram.

OCRnx Interrupt Flag Set

OCRnx Update and

TOVn Interrupt Flag Set

TCNTn

OCnx

OCnx

Period

1 2 3 4 5 6 7

(COMnx1:0 = 2)

(COMnx1:0 = 3)

The Timer/Counter Overflow Flag (TOV2) is set each time the counter reaches TOP. If the interrupt is enabled, the interrupt handler routine can be used for updating the compare value.

In fast PWM mode, the compare unit allows generation of PWM waveforms on the OC2x pin.

Setting the COM2x1:0 bits to two will produce a non-inverted PWM and an inverted PWM output can be generated by setting the COM2x1:0 to three. TOP is defined as 0xFF when WGM2:0 = 3,

and OCR2A when WGM2:0 = 7 (See Table 17-3 on page 156

). The actual OC2x value will only be visible on the port pin if the data direction for the port pin is set as output. The PWM waveform is generated by setting (or clearing) the OC2x Register at the compare match between

OCR2x and TCNT2, and clearing (or setting) the OC2x Register at the timer clock cycle the counter is cleared (changes from TOP to BOTTOM).

The PWM frequency for the output can be calculated by the following equation:

f

OCnxPWM

=

f

clk_I/O

------------------

The N variable represents the prescale factor (1, 8, 32, 64, 128, 256, or 1024).

The extreme values for the OCR2A Register represent special cases when generating a PWM waveform output in the fast PWM mode. If the OCR2A is set equal to BOTTOM, the output will be a narrow spike for each MAX+1 timer clock cycle. Setting the OCR2A equal to MAX will result in a constantly high or low output (depending on the polarity of the output set by the COM2A1:0 bits.)

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17.7.4

A frequency (with 50% duty cycle) waveform output in fast PWM mode can be achieved by setting OC2x to toggle its logical level on each compare match (COM2x1:0 = 1). The waveform generated will have a maximum frequency of f oc2

= f clk_I/O

/2 when OCR2A is set to zero. This feature is similar to the OC2A toggle in CTC mode, except the double buffer feature of the Output

Compare unit is enabled in the fast PWM mode.

Phase Correct PWM mode

The phase correct PWM mode (WGM22:0 = 1 or 5) provides a high resolution phase correct

PWM waveform generation option. The phase correct PWM mode is based on a dual-slope operation. The counter counts repeatedly from BOTTOM to TOP and then from TOP to BOT-

TOM. TOP is defined as 0xFF when WGM22:0 = 1, and OCR2A when MGM22:0 = 5. In noninverting Compare Output mode, the Output Compare (OC2x) is cleared on the compare match between TCNT2 and OCR2x while upcounting, and set on the compare match while downcounting. In inverting Output Compare mode, the operation is inverted. The dual-slope operation has lower maximum operation frequency than single slope operation. However, due to the symmetric feature of the dual-slope PWM modes, these modes are preferred for motor control applications.

In phase correct PWM mode the counter is incremented until the counter value matches TOP.

When the counter reaches TOP, it changes the count direction. The TCNT2 value will be equal to TOP for one timer clock cycle. The timing diagram for the phase correct PWM mode is shown on

Figure 17-7

. The TCNT2 value is in the timing diagram shown as a histogram for illustrating the dual-slope operation. The diagram includes non-inverted and inverted PWM outputs. The small horizontal line marks on the TCNT2 slopes represent compare matches between OCR2x and TCNT2.

Figure 17-7.

Phase Correct PWM mode, timing diagram.

OCnx Interrupt Flag Set

OCRnx Update

TOVn Interrupt Flag Set

TCNTn

OCnx

OCnx

Period

1 2 3

(COMnx1:0 = 2)

(COMnx1:0 = 3)

The Timer/Counter Overflow Flag (TOV2) is set each time the counter reaches BOTTOM. The

Interrupt Flag can be used to generate an interrupt each time the counter reaches the BOTTOM value.

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In phase correct PWM mode, the compare unit allows generation of PWM waveforms on the

OC2x pin. Setting the COM2x1:0 bits to two will produce a non-inverted PWM. An inverted PWM output can be generated by setting the COM2x1:0 to three. TOP is defined as 0xFF when

WGM2:0 = 3, and OCR2A when MGM2:0 = 7 (See Table 17-4 on page 157 ). The actual OC2x

value will only be visible on the port pin if the data direction for the port pin is set as output. The

PWM waveform is generated by clearing (or setting) the OC2x Register at the compare match between OCR2x and TCNT2 when the counter increments, and setting (or clearing) the OC2x

Register at compare match between OCR2x and TCNT2 when the counter decrements. The

PWM frequency for the output when using phase correct PWM can be calculated by the following equation:

f

OCnxPCPWM

=

f

clk_I/O

------------------

The N variable represents the prescale factor (1, 8, 32, 64, 128, 256, or 1024).

The extreme values for the OCR2A Register represent special cases when generating a PWM waveform output in the phase correct PWM mode. If the OCR2A is set equal to BOTTOM, the output will be continuously low and if set equal to MAX the output will be continuously high for non-inverted PWM mode. For inverted PWM the output will have the opposite logic values.

At the very start of period 2 in Figure 17-7 on page 150 OCnx has a transition from high to low

even though there is no Compare Match. The point of this transition is to guarantee symmetry around BOTTOM. There are two cases that give a transition without Compare Match.

• OCR2A changes its value from MAX, like in Figure 17-7 on page 150

. When the OCR2A value is MAX the OCn pin value is the same as the result of a down-counting compare match. To ensure symmetry around BOTTOM the OCn value at MAX must correspond to the result of an up-counting Compare Match

• The timer starts counting from a value higher than the one in OCR2A, and for that reason misses the Compare Match and hence the OCn change that would have happened on the way up

17.8

Timer/Counter Timing diagrams

The following figures show the Timer/Counter in synchronous mode, and the timer clock (clk

T2

) is therefore shown as a clock enable signal. In asynchronous mode, clk

I/O

should be replaced by the Timer/Counter Oscillator clock. The figures include information on when Interrupt Flags are set.

Figure 17-8 on page 152

contains timing data for basic Timer/Counter operation. The figure shows the count sequence close to the MAX value in all modes other than phase correct PWM mode.

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Figure 17-8.

Timer/Counter Timing diagram, no prescaling.

clk

I/O clk

(clk

I/O

Tn

/1)

TCNTn MAX - 1 MAX BOTTOM

TOVn

BOTTOM + 1

Figure 17-9 on page 152 shows the same timing data, but with the prescaler enabled.

Figure 17-9.

Timer/Counter Timing diagram, with prescaler (f clk_I/O

/8).

clk

I/O clk

(clk

I/O

Tn

/8)

TCNTn

TOVn

MAX - 1 MAX BOTTOM BOTTOM + 1

Figure 17-10 on page 152

shows the setting of OCF2A in all modes except CTC mode.

Figure 17-10.

Timer/Counter Timing diagram, setting of OCF2A, with prescaler (f clk_I/O

/8).

clk

I/O clk

(clk

I/O

Tn

/8)

TCNTn OCRnx - 1 OCRnx OCRnx + 1 OCRnx + 2

OCRnx Value OCRnx

OCFnx

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Figure 17-11 on page 153 shows the setting of OCF2A and the clearing of TCNT2 in CTC mode.

Figure 17-11.

Timer/Counter Timing diagram, Clear Timer on Compare Match mode, with prescaler (f clk_I/O

/8).

clk

I/O clk

(clk

I/O

Tn

/8)

TCNTn

(CTC)

OCRnx

OCFnx

TOP - 1 TOP

TOP

BOTTOM BOTTOM + 1

17.9

Asynchronous Operation of Timer/Counter2

When Timer/Counter2 operates asynchronously, some considerations must be taken.

• Warning: When switching between asynchronous and synchronous clocking of

Timer/Counter2, the Timer Registers TCNT2, OCR2x, and TCCR2x might be corrupted. A safe procedure for switching clock source is: a. Disable the Timer/Counter2 interrupts by clearing OCIE2x and TOIE2.

b.

Select clock source by setting AS2 as appropriate.

c.

Write new values to TCNT2, OCR2x, and TCCR2x.

d. To switch to asynchronous operation: Wait for TCN2UB, OCR2xUB, and TCR2xUB.

e. Clear the Timer/Counter2 Interrupt Flags.

f.

Enable interrupts, if needed.

• The CPU main clock frequency must be more than four times the Oscillator frequency

• When writing to one of the registers TCNT2, OCR2x, or TCCR2x, the value is transferred to a temporary register, and latched after two positive edges on TOSC1. The user should not write a new value before the contents of the temporary register have been transferred to its destination. Each of the five mentioned registers have their individual temporary register, which means that e.g. writing to TCNT2 does not disturb an OCR2x write in progress. To detect that a transfer to the destination register has taken place, the Asynchronous Status Register – ASSR has been implemented

• When entering Power-save or ADC Noise Reduction mode after having written to TCNT2,

OCR2x, or TCCR2x, the user must wait until the written register has been updated if

Timer/Counter2 is used to wake up the device. Otherwise, the MCU will enter sleep mode before the changes are effective. This is particularly important if any of the Output Compare2 interrupt is used to wake up the device, since the Output Compare function is disabled during writing to OCR2x or TCNT2. If the write cycle is not finished, and the MCU enters sleep mode before the corresponding OCR2xUB bit returns to zero, the device will never receive a compare match interrupt, and the MCU will not wake up

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• If Timer/Counter2 is used to wake the device up from Power-save or ADC Noise Reduction mode, precautions must be taken if the user wants to re-enter one of these modes: The interrupt logic needs one TOSC1 cycle to be reset. If the time between wake-up and reentering sleep mode is less than one TOSC1 cycle, the interrupt will not occur, and the device will fail to wake up. If the user is in doubt whether the time before re-entering Power-save or

ADC Noise Reduction mode is sufficient, the following algorithm can be used to ensure that one TOSC1 cycle has elapsed: a. Write a value to TCCR2x, TCNT2, or OCR2x.

b.

Wait until the corresponding Update Busy Flag in ASSR returns to zero.

c.

Enter Power-save or ADC Noise Reduction mode.

• When the asynchronous operation is selected, the 32.768kHz Oscillator for Timer/Counter2 is always running, except in Power-down and Standby modes. After a Power-up Reset or wakeup from Power-down or Standby mode, the user should be aware of the fact that this Oscillator might take as long as one second to stabilize. The user is advised to wait for at least one second before using Timer/Counter2 after power-up or wake-up from Power-down or Standby mode. The contents of all Timer/Counter2 Registers must be considered lost after a wake-up from Power-down or Standby mode due to unstable clock signal upon start-up, no matter whether the Oscillator is in use or a clock signal is applied to the TOSC1 pin

• Description of wake up from Power-save or ADC Noise Reduction mode when the timer is clocked asynchronously: When the interrupt condition is met, the wake up process is started on the following cycle of the timer clock, that is, the timer is always advanced by at least one before the processor can read the counter value. After wake-up, the MCU is halted for four cycles, it executes the interrupt routine, and resumes execution from the instruction following

SLEEP

• Reading of the TCNT2 Register shortly after wake-up from Power-save may give an incorrect result. Since TCNT2 is clocked on the asynchronous TOSC clock, reading TCNT2 must be done through a register synchronized to the internal I/O clock domain. Synchronization takes place for every rising TOSC1 edge. When waking up from Power-save mode, and the I/O clock

(clk

I/O

) again becomes active, TCNT2 will read as the previous value (before entering sleep) until the next rising TOSC1 edge. The phase of the TOSC clock after waking up from Powersave mode is essentially unpredictable, as it depends on the wake-up time. The recommended procedure for reading TCNT2 is thus as follows: a. Write any value to either of the registers OCR2x or TCCR2x. b.

Wait for the corresponding Update Busy Flag to be cleared. c.

Read TCNT2.

• During asynchronous operation, the synchronization of the Interrupt Flags for the asynchronous timer takes 3 processor cycles plus one timer cycle. The timer is therefore advanced by at least one before the processor can read the timer value causing the setting of the Interrupt Flag. The Output Compare pin is changed on the timer clock and is not synchronized to the processor clock

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17.10 Timer/Counter Prescaler

Figure 17-12.

Prescaler for Timer/Counter2.

clk

I/O

TOSC1 clk

T2S

Clear

AS2

10-BIT T/C PRESCALER

PSRASY

0

CS20

CS21

CS22

TIMER/COUNTER2 CLOCK SOURCE clk

T2

The clock source for Timer/Counter2 is named clk

T2S

. clk

T2S

is by default connected to the main system I/O clock clk

IO

. By setting the AS2 bit in ASSR, Timer/Counter2 is asynchronously clocked from the TOSC1 pin. This enables use of Timer/Counter2 as a Real Time Counter

(RTC). When AS2 is set, pins TOSC1 and TOSC2 are disconnected from Port C. A crystal can then be connected between the TOSC1 and TOSC2 pins to serve as an independent clock source for Timer/Counter2. The Oscillator is optimized for use with a 32.768kHz crystal. By setting the EXCLK bit in the ASSR a 32kHz external clock can be applied. See

”ASSR –

Asynchronous Status Register” on page 160 for details.

For Timer/Counter2, the possible prescaled selections are: clk

T2S

/8, clk

T2S

/32, clk

T2S

/64, clk

T2S

/128, clk

T2S

/256, and clk

T2S

/1024. Additionally, clk

T2S

as well as 0 (stop) may be selected.

Setting the PSRASY bit in GTCCR resets the prescaler. This allows the user to operate with a predictable prescaler.

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17.11 Register description

17.11.1

TCCR2A – Timer/Counter Control Register A

Bit

(0xB0)

Read/Write

Initial Value

7

COM2A1

R/W

0

6

COM2A0

R/W

0

5

COM2B1

R/W

0

4

COM2B0

R/W

0

3

R

0

2

R

0

1

WGM21

R/W

0

0

WGM20

R/W

0

TCCR2A

• Bits 7:6 – COM2A1:0: Compare Match Output A Mode

These bits control the Output Compare pin (OC2A) behavior. If one or both of the COM2A1:0 bits are set, the OC2A output overrides the normal port functionality of the I/O pin it is connected to. However, note that the Data Direction Register (DDR) bit corresponding to the OC2A pin must be set in order to enable the output driver.

When OC2A is connected to the pin, the function of the COM2A1:0 bits depends on the

WGM22:0 bit setting.

Table 17-2 shows the COM2A1:0 bit functionality when the WGM22:0 bits

are set to a normal or CTC mode (non-PWM).

Table 17-2.

Compare Output mode, non-PWM mode.

COM2A1

0

0

1

1

COM2A0

0

1

0

1

Description

Normal port operation, OC0A disconnected.

Toggle OC2A on Compare Match

Clear OC2A on Compare Match

Set OC2A on Compare Match

Table 17-3 shows the COM2A1:0 bit functionality when the WGM21:0 bits are set to fast PWM

mode.

Table 17-3.

Compare Output mode, fast PWM mode

(1)

.

COM2A1

0

0

1

1

COM2A0

0

1

0

1

Description

Normal port operation, OC2A disconnected.

WGM22 = 0: Normal Port Operation, OC0A Disconnected.

WGM22 = 1: Toggle OC2A on Compare Match.

Clear OC2A on Compare Match, set OC2A at BOTTOM,

(non-inverting mode).

Set OC2A on Compare Match, clear OC2A at BOTTOM,

(inverting mode).

Note: 1. A special case occurs when OCR2A equals TOP and COM2A1 is set. In this case, the Com-

pare Match is ignored, but the set or clear is done at BOTTOM. See ”Fast PWM mode” on page 148

for more details.

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Table 17-4

shows the COM2A1:0 bit functionality when the WGM22:0 bits are set to phase correct PWM mode.

Table 17-4.

Compare Output mode, phase correct PWM mode

(1)

.

COM2A1

0

0

1

1

COM2A0

0

1

0

1

Description

Normal port operation, OC2A disconnected.

WGM22 = 0: Normal Port Operation, OC2A Disconnected.

WGM22 = 1: Toggle OC2A on Compare Match.

Clear OC2A on Compare Match when up-counting. Set OC2A on

Compare Match when down-counting.

Set OC2A on Compare Match when up-counting. Clear OC2A on

Compare Match when down-counting.

Note: 1. A special case occurs when OCR2A equals TOP and COM2A1 is set. In this case, the Com-

pare Match is ignored, but the set or clear is done at TOP. See ”Phase Correct PWM mode” on page 150

for more details.

• Bits 5:4 – COM2B1:0: Compare Match Output B Mode

These bits control the Output Compare pin (OC2B) behavior. If one or both of the COM2B1:0 bits are set, the OC2B output overrides the normal port functionality of the I/O pin it is connected to. However, note that the Data Direction Register (DDR) bit corresponding to the OC2B pin must be set in order to enable the output driver.

When OC2B is connected to the pin, the function of the COM2B1:0 bits depends on the

WGM22:0 bit setting.

Table 17-5 shows the COM2B1:0 bit functionality when the WGM22:0 bits

are set to a normal or CTC mode (non-PWM).

Table 17-5.

Compare Output mode, non-PWM mode.

COM2B1

0

0

1

1

COM2B0

0

1

0

1

Description

Normal port operation, OC2B disconnected.

Toggle OC2B on Compare Match

Clear OC2B on Compare Match

Set OC2B on Compare Match

Table 17-6 shows the COM2B1:0 bit functionality when the WGM22:0 bits are set to fast PWM

mode.

Table 17-6.

Compare Output mode, fast PWM mode

(1)

.

COM2B1

0

COM2B0

0

Description

Normal port operation, OC2B disconnected.

0

1

1

0

Reserved

Clear OC2B on Compare Match, set OC2B at BOTTOM,

(non-inverting mode).

1 1

Set OC2B on Compare Match, clear OC2B at BOTTOM,

(inverting mode).

Note: 1. A special case occurs when OCR2B equals TOP and COM2B1 is set. In this case, the Com-

pare Match is ignored, but the set or clear is done at BOTTOM. See ”Fast PWM mode” on page 148

for more details.

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Table 17-7

shows the COM2B1:0 bit functionality when the WGM22:0 bits are set to phase correct PWM mode.

Table 17-7.

Compare Output mode, phase correct PWM mode

(1)

.

COM2B1

0

0

1

1

COM2B0

0

1

0

1

Description

Normal port operation, OC2B disconnected.

Reserved

Clear OC2B on Compare Match when up-counting. Set OC2B on

Compare Match when down-counting.

Set OC2B on Compare Match when up-counting. Clear OC2B on

Compare Match when down-counting.

Note: 1. A special case occurs when OCR2B equals TOP and COM2B1 is set. In this case, the Com-

pare Match is ignored, but the set or clear is done at TOP. See ”Phase Correct PWM mode” on page 150

for more details.

• Bits 3:2 – Reserved

These bits are reserved and will always read as zero.

• Bits 1:0 – WGM21:0: Waveform Generation Mode

Combined with the WGM22 bit found in the TCCR2B Register, these bits control the counting sequence of the counter, the source for maximum (TOP) counter value, and what type of waveform generation to be used, see

Table 17-8

. Modes of operation supported by the Timer/Counter unit are: Normal mode (counter), Clear Timer on Compare Match (CTC) mode, and two types of

Pulse Width Modulation (PWM) modes (see ”Modes of operation” on page 147

).

Table 17-8.

Waveform Generation mode bit description.

Mode WGM2 WGM1 WGM0

0 0 0 0

1

2

3

4

5

6

7

0

0

0

1

1

1

1

0

1

1

0

0

1

1

1

0

1

0

1

0

1

Timer/Counter

Mode of

Operation

Normal

PWM, Phase

Correct

CTC

Fast PWM

Reserved

PWM, Phase

Correct

Reserved

Fast PWM

TOP

0xFF

0xFF

OCRA

0xFF

OCRA

OCRA

Notes: 1. MAX= 0xFF

2. BOTTOM= 0x00

Update of

OCRx at

Immediate

TOP

Immediate

BOTTOM

TOP

BOTTOM

TOV Flag

Set on

(1)(2)

MAX

BOTTOM

MAX

MAX

BOTTOM

TOP

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17.11.2

TCCR2B – Timer/Counter Control Register B

Bit

(0xB1)

Read/Write

Initial Value

7

FOC2A

W

0

6

FOC2B

W

0

5

R

0

4

R

0

3

WGM22

R/W

0

2

CS22

R/W

0

1

CS21

R/W

0

0

CS20

R/W

0

TCCR2B

• Bit 7 – FOC2A: Force Output Compare A

The FOC2A bit is only active when the WGM bits specify a non-PWM mode.

However, for ensuring compatibility with future devices, this bit must be set to zero when

TCCR2B is written when operating in PWM mode. When writing a logical one to the FOC2A bit, an immediate Compare Match is forced on the Waveform Generation unit. The OC2A output is changed according to its COM2A1:0 bits setting. Note that the FOC2A bit is implemented as a strobe. Therefore it is the value present in the COM2A1:0 bits that determines the effect of the forced compare.

A FOC2A strobe will not generate any interrupt, nor will it clear the timer in CTC mode using

OCR2A as TOP.

The FOC2A bit is always read as zero.

• Bit 6 – FOC2B: Force Output Compare B

The FOC2B bit is only active when the WGM bits specify a non-PWM mode.

However, for ensuring compatibility with future devices, this bit must be set to zero when

TCCR2B is written when operating in PWM mode. When writing a logical one to the FOC2B bit, an immediate Compare Match is forced on the Waveform Generation unit. The OC2B output is changed according to its COM2B1:0 bits setting. Note that the FOC2B bit is implemented as a strobe. Therefore it is the value present in the COM2B1:0 bits that determines the effect of the forced compare.

A FOC2B strobe will not generate any interrupt, nor will it clear the timer in CTC mode using

OCR2B as TOP.

The FOC2B bit is always read as zero.

• Bits 5:4 – Reserved

These bits are reserved and will always read as zero.

• Bit 3 – WGM22: Waveform Generation Mode

See the description in the

”TCCR2A – Timer/Counter Control Register A” on page 156

.

• Bit 2:0 – CS22:0: Clock Select

The three Clock Select bits select the clock source to be used by the Timer/Counter, see

Table

17-9 on page 159

.

Table 17-9.

Clock Select bit description.

CS22

0

0

0

CS21

0

0

1

CS20

0

1

0

Description

No clock source (Timer/Counter stopped).

clk

T2S

/(No prescaling) clk

T2S

/8 (From prescaler)

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Table 17-9.

Clock Select bit description. (Continued)

CS22

0

1

1

1

1

CS21

1

0

0

1

1

CS20

1

0

1

0

1

Description

clk

T2S

/32 (From prescaler) clk

T2S

/64 (From prescaler) clk

T2S

/128 (From prescaler) clk

T 2 S

/256 (From prescaler) clk

T

2

S

/1024 (From prescaler)

17.11.3

TCNT2 – Timer/Counter Register

Bit

(0xB2)

Read/Write

Initial Value

7

R/W

0

6

R/W

0

5

R/W

0

4

TCNT2[7:0]

3

R/W

0

R/W

0

2

R/W

0

1

R/W

0

0

R/W

0

TCNT2

The Timer/Counter Register gives direct access, both for read and write operations, to the

Timer/Counter unit 8-bit counter. Writing to the TCNT2 Register blocks (removes) the Compare

Match on the following timer clock. Modifying the counter (TCNT2) while the counter is running, introduces a risk of missing a Compare Match between TCNT2 and the OCR2x Registers.

17.11.4

OCR2A – Output Compare Register A

Bit

(0xB3)

Read/Write

Initial Value

7

R/W

0

6

R/W

0

5

R/W

0

4

OCR2A[7:0]

3

R/W

0

R/W

0

2

R/W

0

1

R/W

0

0

R/W

0

OCR2A

The Output Compare Register A contains an 8-bit value that is continuously compared with the counter value (TCNT2). A match can be used to generate an Output Compare interrupt, or to generate a waveform output on the OC2A pin.

17.11.5

OCR2B – Output Compare Register B

Bit

(0xB4)

Read/Write

Initial Value

7

R/W

0

6

R/W

0

5

R/W

0

4 3

OCR2B[7:0]

R/W R/W

0 0

2

R/W

0

1

R/W

0

0

R/W

0

OCR2B

The Output Compare Register B contains an 8-bit value that is continuously compared with the counter value (TCNT2). A match can be used to generate an Output Compare interrupt, or to generate a waveform output on the OC2B pin.

17.11.6

ASSR – Asynchronous Status Register

Bit

(0xB6)

Read/Write

Initial Value

R

0

7

6

EXCLK

R/W

0

5

AS2

R/W

0

4

TCN2UB

R

0

3

OCR2AUB

R

0

2

OCR2BUB

R

0

1

TCR2AUB

R

0

0

TCR2BUB

R

0

ASSR

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• Bit 6 – EXCLK: Enable External Clock Input

When EXCLK is written to one, and asynchronous clock is selected, the external clock input buffer is enabled and an external clock can be input on Timer Oscillator 1 (TOSC1) pin instead of a

32kHz crystal. Writing to EXCLK should be done before asynchronous operation is selected.

Note that the crystal Oscillator will only run when this bit is zero.

• Bit 5 – AS2: Asynchronous Timer/Counter2

When AS2 is written to zero, Timer/Counter2 is clocked from the I/O clock, clk

I/O

. When AS2 is written to one, Timer/Counter2 is clocked from a crystal Oscillator connected to the Timer Oscillator 1 (TOSC1) pin. When the value of AS2 is changed, the contents of TCNT2, OCR2A,

OCR2B, TCCR2A and TCCR2B might be corrupted.

• Bit 4 – TCN2UB: Timer/Counter2 Update Busy

When Timer/Counter2 operates asynchronously and TCNT2 is written, this bit becomes set.

When TCNT2 has been updated from the temporary storage register, this bit is cleared by hardware. A logical zero in this bit indicates that TCNT2 is ready to be updated with a new value.

• Bit 3 – OCR2AUB: Output Compare Register2 Update Busy

When Timer/Counter2 operates asynchronously and OCR2A is written, this bit becomes set.

When OCR2A has been updated from the temporary storage register, this bit is cleared by hardware. A logical zero in this bit indicates that OCR2A is ready to be updated with a new value.

• Bit 2 – OCR2BUB: Output Compare Register2 Update Busy

When Timer/Counter2 operates asynchronously and OCR2B is written, this bit becomes set.

When OCR2B has been updated from the temporary storage register, this bit is cleared by hardware. A logical zero in this bit indicates that OCR2B is ready to be updated with a new value.

• Bit 1 – TCR2AUB: Timer/Counter Control Register2 Update Busy

When Timer/Counter2 operates asynchronously and TCCR2A is written, this bit becomes set.

When TCCR2A has been updated from the temporary storage register, this bit is cleared by hardware. A logical zero in this bit indicates that TCCR2A is ready to be updated with a new value.

• Bit 0 – TCR2BUB: Timer/Counter Control Register2 Update Busy

When Timer/Counter2 operates asynchronously and TCCR2B is written, this bit becomes set.

When TCCR2B has been updated from the temporary storage register, this bit is cleared by hardware. A logical zero in this bit indicates that TCCR2B is ready to be updated with a new value.

If a write is performed to any of the five Timer/Counter2 Registers while its update busy flag is set, the updated value might get corrupted and cause an unintentional interrupt to occur.

The mechanisms for reading TCNT2, OCR2A, OCR2B, TCCR2A and TCCR2B are different.

When reading TCNT2, the actual timer value is read. When reading OCR2A, OCR2B, TCCR2A and TCCR2B the value in the temporary storage register is read.

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17.11.7

TIMSK2 – Timer/Counter2 Interrupt Mask Register

Bit

(0x70)

Read/Write

Initial Value

7

R

0

6

R

0

5

R

0

4

R

0

3

R

0

2

OCIE2B

R/W

0

1

OCIE2A

R/W

0

0

TOIE2

R/W

0

TIMSK2

• Bit 2 – OCIE2B: Timer/Counter2 Output Compare Match B Interrupt Enable

When the OCIE2B bit is written to one and the I-bit in the Status Register is set (one), the

Timer/Counter2 Compare Match B interrupt is enabled. The corresponding interrupt is executed if a compare match in Timer/Counter2 occurs, that is, when the OCF2B bit is set in the

Timer/Counter 2 Interrupt Flag Register – TIFR2.

• Bit 1 – OCIE2A: Timer/Counter2 Output Compare Match A Interrupt Enable

When the OCIE2A bit is written to one and the I-bit in the Status Register is set (one), the

Timer/Counter2 Compare Match A interrupt is enabled. The corresponding interrupt is executed if a compare match in Timer/Counter2 occurs, that is, when the OCF2A bit is set in the

Timer/Counter 2 Interrupt Flag Register – TIFR2.

• Bit 0 – TOIE2: Timer/Counter2 Overflow Interrupt Enable

When the TOIE2 bit is written to one and the I-bit in the Status Register is set (one), the

Timer/Counter2 Overflow interrupt is enabled. The corresponding interrupt is executed if an overflow in Timer/Counter2 occurs, that is, when the TOV2 bit is set in the Timer/Counter2 Interrupt Flag Register – TIFR2.

17.11.8

TIFR2 – Timer/Counter2 Interrupt Flag Register

Bit

0x17 (0x37)

Read/Write

Initial Value

7

R

0

6

R

0

5

R

0

4

R

0

3

R

0

2

OCF2B

R/W

0

1

OCF2A

R/W

0

0

TOV2

R/W

0

TIFR2

• Bit 2 – OCF2B: Output Compare Flag 2 B

The OCF2B bit is set (one) when a compare match occurs between the Timer/Counter2 and the data in OCR2B – Output Compare Register2. OCF2B is cleared by hardware when executing the corresponding interrupt handling vector. Alternatively, OCF2B is cleared by writing a logic one to the flag. When the I-bit in SREG, OCIE2B (Timer/Counter2 Compare match Interrupt

Enable), and OCF2B are set (one), the Timer/Counter2 Compare match Interrupt is executed.

• Bit 1 – OCF2A: Output Compare Flag 2 A

The OCF2A bit is set (one) when a compare match occurs between the Timer/Counter2 and the data in OCR2A – Output Compare Register2. OCF2A is cleared by hardware when executing the corresponding interrupt handling vector. Alternatively, OCF2A is cleared by writing a logic one to the flag. When the I-bit in SREG, OCIE2A (Timer/Counter2 Compare match Interrupt

Enable), and OCF2A are set (one), the Timer/Counter2 Compare match Interrupt is executed.

• Bit 0 – TOV2: Timer/Counter2 Overflow Flag

The TOV2 bit is set (one) when an overflow occurs in Timer/Counter2. TOV2 is cleared by hardware when executing the corresponding interrupt handling vector. Alternatively, TOV2 is cleared by writing a logic one to the flag. When the SREG I-bit, TOIE2A (Timer/Counter2 Overflow Inter-

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rupt Enable), and TOV2 are set (one), the Timer/Counter2 Overflow interrupt is executed. In

PWM mode, this bit is set when Timer/Counter2 changes counting direction at 0x00.

17.11.9

GTCCR – General Timer/Counter Control Register

Bit

0x23 (0x43)

Read/Write

Initial Value

7

TSM

R/W

0

6

R

0

5

R

0

4

R

0

3

R

0

2

R

0

1 0

PSRASY PSRSYNC GTCCR

R/W R/W

0 0

• Bit 7 – TSM: Timer/Counter Synchronization mode

Writing the TSM bit to one, activates the Timer/Counter Synchronization mode. In this mode, the value that is written to the PSRASY and PSRSYNC bits is kept, hence keepeing the corresponding prescaler reset signals asserted. This ensures that the corresponding Timer/Counters are halted and can be configured to the same value without the risk of one of them advancing during configuration. When the TSM bit is written to zero, the PSRASY and PSRSYNC bits are cleared by hardware, and the Timer/Counters start counting simultaneously.

• Bit 1 – PSRASY: Prescaler Reset Timer/Counter2

When this bit is one, the Timer/Counter2 prescaler will be reset. This bit is normally cleared immediately by hardware. If the bit is written when Timer/Counter2 is operating in asynchronous mode, the bit will remain one until the prescaler has been reset. The bit will not be cleared by hardware if the TSM bit is set. Refer to the description of the “Bit 7 – TSM: Timer/Counter Synchronization Mode” on this page for a description of the Timer/Counter Synchronization mode.

• Bit 0 – PSRSYNC: Prescaler Reset

When this bit is one, Timer/Counter1 and Timer/Counter0 prescaler will be Reset. This bit is normally cleared immediately by hardware, except ifthe TSM bit is set. Note that Timer/Counter1 and Timer/Counter0 share the same prescaler and a reset of this prescaler will affect both timers.

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18. SPI – Serial Peripheral Interface

18.1

Features

Full-duplex, three-wire synchronous data transfer

Master or Slave operation

LSB first or MSB first data transfer

Seven programmable bit rates

End of Transmission Interrupt flag

Write Collision flag protection

Wake-up from Idle mode

Double speed (CK/2) Master SPI mode

18.2

Overview

The Serial Peripheral Interface (SPI) allows high-speed synchronous data transfer between the

Atmel ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P and peripheral devices or between several AVR devices.

USART can also be used in Master SPI mode, see ”USART in SPI mode” on page 201

.

The Power Reduction SPI bit, PRSPI, in

”PRR0 – Power Reduction Register 0” on page 48 must

be written to zero to enable SPI module.

Figure 18-1.

SPI block diagram

(1)

.

DIVIDER

/2/4/8/16/32/64/128

8272D–AVR–05/12

Note:

1. Refer to Figure 1-1 on page 2

, and Table 14-6 on page 82 for SPI pin placement.

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The interconnection between Master and Slave CPUs with SPI is shown in

Figure 18-2

. The system consists of two shift Registers, and a Master clock generator. The SPI Master initiates the communication cycle when pulling low the Slave Select SS pin of the desired Slave. Master and

Slave prepare the data to be sent in their respective shift Registers, and the Master generates the required clock pulses on the SCK line to interchange data. Data is always shifted from Master to Slave on the Master Out – Slave In, MOSI, line, and from Slave to Master on the Master In

– Slave Out, MISO, line. After each data packet, the Master will synchronize the Slave by pulling high the Slave Select, SS, line.

When configured as a Master, the SPI interface has no automatic control of the SS line. This must be handled by user software before communication can start. When this is done, writing a byte to the SPI Data Register starts the SPI clock generator, and the hardware shifts the eight bits into the Slave. After shifting one byte, the SPI clock generator stops, setting the end of

Transmission Flag (SPIF). If the SPI Interrupt Enable bit (SPIE) in the SPCR Register is set, an interrupt is requested. The Master may continue to shift the next byte by writing it into SPDR, or signal the end of packet by pulling high the Slave Select, SS line. The last incoming byte will be kept in the Buffer Register for later use.

When configured as a Slave, the SPI interface will remain sleeping with MISO tri-stated as long as the SS pin is driven high. In this state, software may update the contents of the SPI Data

Register, SPDR, but the data will not be shifted out by incoming clock pulses on the SCK pin until the SS pin is driven low. As one byte has been completely shifted, the end of Transmission

Flag, SPIF is set. If the SPI Interrupt Enable bit, SPIE, in the SPCR Register is set, an interrupt is requested. The Slave may continue to place new data to be sent into SPDR before reading the incoming data. The last incoming byte will be kept in the Buffer Register for later use.

Figure 18-2.

SPI Master-slave interconnection.

8272D–AVR–05/12

SHIFT

ENABLE

The system is single buffered in the transmit direction and double buffered in the receive direction. This means that bytes to be transmitted cannot be written to the SPI Data Register before the entire shift cycle is completed. When receiving data, however, a received character must be read from the SPI Data Register before the next character has been completely shifted in. Otherwise, the first byte is lost.

In SPI Slave mode, the control logic will sample the incoming signal of the SCK pin. To ensure correct sampling of the clock signal, the minimum low and high periods should be:

Low period: longer than two CPU clock cycles.

High period: longer than two CPU clock cycles.

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When the SPI is enabled, the data direction of the MOSI, MISO, SCK, and SS pins is overridden according to

Table 18-1

. For more details on automatic port overrides, refer to

”Alternate Port

Functions” on page 77 .

Table 18-1.

SPI pin overrides

(1)

.

Pin

MOSI

MISO

SCK

SS

Direction, Master SPI

User Defined

Input

User Defined

User Defined

Direction, Slave SPI

Input

User Defined

Input

Input

Note: 1. See

”Alternate Functions of Port B” on page 82

for a detailed description of how to define the direction of the user defined SPI pins.

The following code examples show how to initialize the SPI as a Master and how to perform a simple transmission. DDR_SPI in the examples must be replaced by the actual Data Direction

Register controlling the SPI pins. DD_MOSI, DD_MISO and DD_SCK must be replaced by the actual data direction bits for these pins. For example, if MOSI is placed on pin PB5, replace

DD_MOSI with DDB5 and DDR_SPI with DDRB.

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ATmega164A/PA/324A/PA/644A/PA/1284/P

Assembly Code Example

(1)

SPI_MasterInit:

; Set MOSI and SCK output, all others input

ldi

r17,(1<<DD_MOSI)|(1<<DD_SCK)

out

DDR_SPI,r17

; Enable SPI, Master, set clock rate fck/16

ldi

r17,(1<<SPE)|(1<<MSTR)|(1<<SPR0)

out

SPCR,r17

ret

SPI_MasterTransmit:

; Start transmission of data (r16)

out

SPDR,r16

Wait_Transmit:

; Wait for transmission complete

sbis

SPSR,SPIF

rjmp

Wait_Transmit

ret

C Code Example

(1)

void

SPI_MasterInit(void)

{

/* Set MOSI and SCK output, all others input */

DDR_SPI = (1<<DD_MOSI)|(1<<DD_SCK);

/* Enable SPI, Master, set clock rate fck/16 */

SPCR = (1<<SPE)|(1<<MSTR)|(1<<SPR0);

}

void

SPI_MasterTransmit(char cData)

{

/* Start transmission */

SPDR = cData;

/* Wait for transmission complete */

while

(!(SPSR & (1<<SPIF)))

;

}

Note: 1.

See “About code examples” on page 9

.

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The following code examples show how to initialize the SPI as a Slave and how to perform a simple reception.

Assembly Code Example

(1)

SPI_SlaveInit:

; Set MISO output, all others input

ldi

r17,(1<<DD_MISO)

out

DDR_SPI,r17

; Enable SPI

ldi

r17,(1<<SPE)

out

SPCR,r17

ret

SPI_SlaveReceive:

; Wait for reception complete

sbis

SPSR,SPIF

rjmp

SPI_SlaveReceive

; Read received data and return

in

r16,SPDR

ret

C Code Example

(1)

void

SPI_SlaveInit(void)

{

/* Set MISO output, all others input */

DDR_SPI = (1<<DD_MISO);

/* Enable SPI */

SPCR = (1<<SPE);

}

char

SPI_SlaveReceive(void)

{

/* Wait for reception complete */

while

(!(SPSR & (1<<SPIF)))

;

/* Return Data Register */

return

SPDR;

}

Note: 1.

See “About code examples” on page 9

.

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ATmega164A/PA/324A/PA/644A/PA/1284/P

18.3

SS pin functionality

18.3.1

Slave mode

When the SPI is configured as a Slave, the Slave Select (SS) pin is always input. When SS is held low, the SPI is activated, and MISO becomes an output if configured so by the user. All other pins are inputs. When SS is driven high, all pins are inputs, and the SPI is passive, which means that it will not receive incoming data. Note that the SPI logic will be reset once the SS pin is driven high.

The SS pin is useful for packet/byte synchronization to keep the slave bit counter synchronous with the master clock generator. When the SS pin is driven high, the SPI slave will immediately reset the send and receive logic, and drop any partially received data in the Shift Register.

18.3.2

Master mode

When the SPI is configured as a Master (MSTR in SPCR is set), the user can determine the direction of the SS pin.

If SS is configured as an output, the pin is a general output pin which does not affect the SPI system. Typically, the pin will be driving the SS pin of the SPI Slave.

If SS is configured as an input, it must be held high to ensure Master SPI operation. If the SS pin is driven low by peripheral circuitry when the SPI is configured as a Master with the SS pin defined as an input, the SPI system interprets this as another master selecting the SPI as a slave and starting to send data to it. To avoid bus contention, the SPI system takes the following actions:

1. The MSTR bit in SPCR is cleared and the SPI system becomes a Slave. As a result of the SPI becoming a Slave, the MOSI and SCK pins become inputs.

2. The SPIF Flag in SPSR is set, and if the SPI interrupt is enabled, and the I-bit in SREG is set, the interrupt routine will be executed.

Thus, when interrupt-driven SPI transmission is used in Master mode, and there exists a possibility that SS is driven low, the interrupt should always check that the MSTR bit is still set. If the

MSTR bit has been cleared by a slave select, it must be set by the user to re-enable SPI Master mode.

18.4

Data modes

There are four combinations of SCK phase and polarity with respect to serial data, which are determined by control bits CPHA and CPOL. The SPI data transfer formats are shown in

Figure

18-3 on page 170 and Figure 18-4 on page 170

. Data bits are shifted out and latched in on opposite edges of the SCK signal, ensuring sufficient time for data signals to stabilize. This is clearly seen by summarizing

Table 18-3 on page 171 and Table 18-4 on page 171

, as done in

Table 18-2 on page 170

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Table 18-2.

SPI modes.

SPI Mode

2

3

0

1

Conditions

CPOL=0, CPHA=0

CPOL=0, CPHA=1

CPOL=1, CPHA=0

CPOL=1, CPHA=1

Figure 18-3.

SPI transfer format with CPHA = 0.

SCK (CPOL = 0) mode 0

SCK (CPOL = 1) mode 2

SAMPLE I

MOSI/MISO

CHANGE 0

MOSI PIN

CHANGE 0

MISO PIN

SS

Leading Edge

Sample (Rising)

Setup (Rising)

Sample (Falling)

Setup (Falling)

Trailing Edge

Setup (Falling)

Sample (Falling)

Setup (Rising)

Sample (Rising)

MSB first (DORD = 0)

LSB first (DORD = 1)

MSB

LSB

Bit 6

Bit 1

Bit 5

Bit 2

Figure 18-4.

SPI transfer format with CPHA = 1.

SCK (CPOL = 0) mode 1

SCK (CPOL = 1) mode 3

SAMPLE I

MOSI/MISO

CHANGE 0

MOSI PIN

CHANGE 0

MISO PIN

SS

Bit 4

Bit 3

Bit 3

Bit 4

Bit 2

Bit 5

Bit 1

Bit 6

LSB

MSB

MSB first (DORD = 0)

LSB first (DORD = 1)

MSB

LSB

Bit 6

Bit 1

Bit 5

Bit 2

Bit 4

Bit 3

Bit 3

Bit 4

Bit 2

Bit 5

Bit 1

Bit 6

LSB

MSB

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18.5

Register description

18.5.1

SPCR – SPI Control Register

Bit

0x2C (0x4C)

Read/Write

Initial Value

7

SPIE

R/W

0

6

SPE

R/W

0

5

DORD

R/W

0

4

MSTR

R/W

0

3

CPOL

R/W

0

2

CPHA

R/W

0

1

SPR1

R/W

0

0

SPR0

R/W

0

SPCR

• Bit 7 – SPIE: SPI Interrupt Enable

This bit causes the SPI interrupt to be executed if SPIF bit in the SPSR Register is set and the if the Global Interrupt Enable bit in SREG is set.

• Bit 6 – SPE: SPI Enable

When the SPE bit is written to one, the SPI is enabled. This bit must be set to enable any SPI operations.

• Bit 5 – DORD: Data Order

When the DORD bit is written to one, the LSB of the data word is transmitted first.

When the DORD bit is written to zero, the MSB of the data word is transmitted first.

• Bit 4 – MSTR: Master/Slave Select

This bit selects Master SPI mode when written to one, and Slave SPI mode when written logic zero. If SS is configured as an input and is driven low while MSTR is set, MSTR will be cleared, and SPIF in SPSR will become set. The user will then have to set MSTR to re-enable SPI Master mode.

• Bit 3 – CPOL: Clock Polarity

When this bit is written to one, SCK is high when idle. When CPOL is written to zero, SCK is low when idle. Refer to

Figure 18-3

and

Figure 18-4

for an example. The CPOL functionality is summarized below:

Table 18-3.

CPOL functionality.

CPOL

0

1

Leading Edge

Rising

Falling

Trailing Edge

Falling

Rising

• Bit 2 – CPHA: Clock Phase

The settings of the Clock Phase bit (CPHA) determine if data is sampled on the leading (first) or trailing (last) edge of SCK. Refer to

Figure 18-3 and Figure 18-4 for an example. The CPOL

functionality is summarized below:

Table 18-4.

CPHA functionality.

CPHA

0

1

Leading Edge

Sample

Setup

Trailing Edge

Setup

Sample

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18.5.2

• Bits 1:0 – SPR1, SPR0: SPI Clock Rate Select 1 and 0

These two bits control the SCK rate of the device configured as a Master. SPR1 and SPR0 have no effect on the Slave. The relationship between SCK and the Oscillator Clock frequency f osc is shown in the following table:

Table 18-5.

Relationship between SCK and the oscillator frequency.

SPI2X

1

1

1

1

0

0

0

0

SPSR – SPI Status Register

SPR1

1

1

0

0

1

1

0

0

SPR0

0

1

0

1

0

1

0

1

SCK Frequency

f osc

/

4 f osc

/

16 f osc

/

64 f osc

/

128 f osc

/

2 f osc

/

8 f osc

/

32 f osc

/

64

Bit

0x2D (0x4D)

Read/Write

Initial Value

7

SPIF

R

0

6

WCOL

R

0

R

0

5

R

0

4

R

0

3

R

0

2

R

0

1

0

SPI2X

R/W

0

SPSR

• Bit 7 – SPIF: SPI Interrupt Flag

When a serial transfer is complete, the SPIF Flag is set. An interrupt is generated if SPIE in

SPCR is set and global interrupts are enabled. If SS is an input and is driven low when the SPI is in Master mode, this will also set the SPIF Flag. SPIF is cleared by hardware when executing the corresponding interrupt handling vector. Alternatively, the SPIF bit is cleared by first reading the

SPI Status Register with SPIF set, then accessing the SPI Data Register (SPDR).

• Bit 6 – WCOL: Write COLlision Flag

The WCOL bit is set if the SPI Data Register (SPDR) is written during a data transfer. The

WCOL bit (and the SPIF bit) are cleared by first reading the SPI Status Register with WCOL set, and then accessing the SPI Data Register.

• Bit 5:1 – Reserved

These bits are reserved and will always read as zero.

• Bit 0 – SPI2X: Double SPI Speed Bit

When this bit is written logic one the SPI speed (SCK Frequency) will be doubled when the SPI

is in Master mode (see Table 18-5

). This means that the minimum SCK period will be two CPU clock periods. When the SPI is configured as Slave, the SPI is only guaranteed to work at f osc

/4 or lower.

The SPI interface on the Atmel ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P is also used for program memory and EEPROM downloading or uploading. See

page 312

for serial programming and verification.

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18.5.3

SPDR – SPI Data Register

Bit

0x2E (0x4E)

Read/Write

Initial Value

7

MSB

R/W

X

6

R/W

X

5

R/W

X

4

R/W

X

3

R/W

X

2

R/W

X

1

R/W

X

0

LSB

R/W

X

SPDR

Undefined

The SPI Data Register is a read/write register used for data transfer between the Register File and the SPI Shift Register. Writing to the register initiates data transmission. Reading the register causes the Shift Register Receive buffer to be read.

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19. USART

19.1

Features

Full duplex operation (independent serial receive and transmit registers)

Asynchronous or synchronous operation

Master or Slave clocked synchronous operation

High resolution baud rate generator

Supports Serial Frames with 5, 6, 7, 8, or 9 data bits and 1 or 2 stop bits

Odd or even parity generation and parity check supported by hardware

Data OverRun detection

Framing Error detection

Noise filtering includes False Start bit detection and Digital Low Pass Filter

Three separate interrupts on TX complete, TX Data Register Empty and RX Complete

Multi-processor Communication mode

Double Speed Asynchronous Communication mode

19.2

USART1 and USART0

The Atmel ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P has two USART’s,

USART0 and USART1.

The functionality for all USART’s is described below, most register and bit references in this section are written in general form. A lower case “n” replaces the USART number.

USART0 and USART1 have different I/O registers as shown in

”Register summary” on page

553 .

19.3

Overview

The Universal Synchronous and Asynchronous serial Receiver and Transmitter (USART) is a highly flexible serial communication device.

A simplified block diagram of the USART Transmitter is shown in

Figure 19-1 on page 175

. CPU accessible I/O Registers and I/O pins are shown in bold.

The Power Reducion USART0 bit, PRUSART0, in

”PRR0 – Power Reduction Register 0” on page 48 must be disabled by writing a logical zero to it.

The Power Reducion USART1 bit, PRUSART1, in

”PRR1 – Power Reduction Register 1” on page 49 must be disabled by writing a logical zero to it.

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Figure 19-1.

USART block diagram

(1)

.

Clock Generator

UBRR[H:L]

BAUD RATE GENERATOR

OSC

SYNC LOGIC

UDR (Transmit)

TRANSMIT SHIFT REGISTER

RECEIVE SHIFT REGISTER

UDR (Receive)

PARITY

GENERATOR

CLOCK

RECOVERY

DATA

RECOVERY

PARITY

CHECKER

PIN

CONTROL

Transmitter

TX

CONTROL

XCK

PIN

CONTROL

Receiver

RX

CONTROL

TxD

PIN

CONTROL

RxD

UCSRA UCSRB UCSRC

Note: 1. See

Figure 1-1 on page 2 and

”Alternate Port Functions” on page 77 for USART pin

placement.

The dashed boxes in the block diagram separate the three main parts of the USART (listed from the top): Clock Generator, Transmitter and Receiver. Control Registers are shared by all units.

The Clock Generation logic consists of synchronization logic for external clock input used by synchronous slave operation, and the baud rate generator. The XCKn (Transfer Clock) pin is only used by synchronous transfer mode. The Transmitter consists of a single write buffer, a serial Shift Register, Parity Generator and Control logic for handling different serial frame formats. The write buffer allows a continuous transfer of data without any delay between frames.

The Receiver is the most complex part of the USART module due to its clock and data recovery units. The recovery units are used for asynchronous data reception. In addition to the recovery units, the Receiver includes a Parity Checker, Control logic, a Shift Register and a two level receive buffer (UDRn). The Receiver supports the same frame formats as the Transmitter, and can detect Frame Error, Data OverRun and Parity Errors.

19.4

Clock Generation

The Clock Generation logic generates the base clock for the Transmitter and Receiver. The

USARTn supports four modes of clock operation: Normal asynchronous, Double Speed asynchronous, Master synchronous and Slave synchronous mode. The UMSELn bit in USART

Control and Status Register C (UCSRnC) selects between asynchronous and synchronous operation. Double Speed (asynchronous mode only) is controlled by the U2Xn found in the

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UCSRnA Register. When using synchronous mode (UMSELn = 1), the Data Direction Register for the XCKn pin (DDR_XCKn) controls whether the clock source is internal (Master mode) or external (Slave mode). The XCKn pin is only active when using synchronous mode.

Figure 19-2

shows a block diagram of the clock generation logic.

Figure 19-2.

Clock Generation Logic, block diagram.

UBRR fosc

UBRR+1

Prescaling

Down-Counter

/2 /4 /2

U2X

0

1

OSC

0

1 txclk

DDR_XCK

Sync

Register

Edge

Detector

XCK

Pin xcki xcko

0

1

UMSEL

DDR_XCK UCPOL 1

0 rxclk

19.4.1

Signal description:

txclk

Transmitter clock (Internal Signal).

rxclk xcki

Receiver base clock (Internal Signal).

Input from XCK pin (internal Signal). Used for synchronous slave operation.

xcko

Clock output to XCK pin (Internal Signal). Used for synchronous master operation.

f

OSC

XTAL pin frequency (System Clock).

Internal Clock Generation – The Baud Rate Generator

Internal clock generation is used for the asynchronous and the synchronous master modes of

operation. The description in this section refers to Figure 19-2 on page 176

.

The USART Baud Rate Register (UBRRn) and the down-counter connected to it function as a programmable prescaler or baud rate generator. The down-counter, running at system clock

(f osc

), is loaded with the UBRRn value each time the counter has counted down to zero or when the UBRRnL Register is written. A clock is generated each time the counter reaches zero. This clock is the baud rate generator clock output (= f osc

/(UBRRn+1)). The Transmitter divides the baud rate generator clock output by 2, 8, or 16 depending on mode. The baud rate generator output is used directly by the Receiver’s clock and data recovery units. However, the recovery units use a state machine that uses 2, 8, or 16 states depending on mode set by the state of the

UMSELn, U2Xn and DDR_XCKn bits.

Table 19-1 on page 177 contains equations for calculating the baud rate (in bits per second) and

for calculating the UBRRn value for each mode of operation using an internally generated clock source.

Note: 1. The baud rate is defined to be the transfer rate in bit per second (bps)

BAUD

Baud rate (in bits per second, bps).

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Table 19-1.

Equations for calculating baud rate register setting.

Operating mode

Equation for calculating baud

rate

(1)

Equation for calculating UBRR value

UBRR

n

=

f

OSC

16BAUD

1

Asynchronous Normal mode (U2Xn = 0)

BAUD

=

f

OSC

16 UBRRn

+

1

)

UBRR

n

=

f

OSC

1

Asynchronous Double

Speed mode (U2Xn = 1)

BAUD

=

f

OSC

8 UBRRn

+

1

)

UBRR

n

=

f

OSC

1

Synchronous Master mode

BAUD

=

f

OSC

2 UBRRn

+

1

)

19.4.2

19.4.3

f

OSC

UBRRn

System Oscillator clock frequency.

Contents of the UBRRnH and UBRRnL Registers, (0-4095).

Some examples of UBRRn values for some system clock frequencies are found in Table 19-9 on page 197

.

Double Speed Operation (U2Xn)

External Clock

The transfer rate can be doubled by setting the U2Xn bit in UCSRnA. Setting this bit only has effect for the asynchronous operation. Set this bit to zero when using synchronous operation.

Setting this bit will reduce the divisor of the baud rate divider from 16 to 8, effectively doubling the transfer rate for asynchronous communication. Note however that the Receiver will in this case only use half the number of samples (reduced from 16 to 8) for data sampling and clock recovery, and therefore a more accurate baud rate setting and system clock are required when this mode is used. For the Transmitter, there are no downsides.

External clocking is used by the synchronous slave modes of operation. The description in this

section refers to Figure 19-2 on page 176 for details.

External clock input from the XCKn pin is sampled by a synchronization register to minimize the chance of meta-stability. The output from the synchronization register must then pass through an edge detector before it can be used by the Transmitter and Receiver. This process intro-

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19.4.4

duces a two CPU clock period delay and therefore the maximum external XCKn clock frequency is limited by the following equation:

f

XCK

<

f

OSC

4

Note that f osc

depends on the stability of the system clock source. It is therefore recommended to add some margin to avoid possible loss of data due to frequency variations.

Synchronous Clock Operation

When synchronous mode is used (UMSELn = 1), the XCKn pin will be used as either clock input

(Slave) or clock output (Master). The dependency between the clock edges and data sampling or data change is the same. The basic principle is that data input (on RxDn) is sampled at the opposite XCKn clock edge of the edge the data output (TxDn) is changed.

Figure 19-3.

Synchronous mode XCKn timing.

UCPOL = 1 XCK

RxD / TxD

Sample

UCPOL = 0 XCK

RxD / TxD

Sample

19.5

Frame formats

The UCPOLn bit UCRSC selects which XCKn clock edge is used for data sampling and which is used for data change. As

Figure 19-3 on page 178

shows, when UCPOLn is zero the data will be changed at rising XCKn edge and sampled at falling XCKn edge. If UCPOLn is set, the data will be changed at falling XCKn edge and sampled at rising XCKn edge.

A serial frame is defined to be one character of data bits with synchronization bits (start and stop bits), and optionally a parity bit for error checking. The USART accepts all 30 combinations of the following as valid frame formats:

• One start bit

• 5, 6, 7, 8, or 9 data bits

• No, even, or odd parity bit

• One or two stop bits

A frame starts with the start bit followed by the least significant data bit. Then the next data bits, up to a total of nine, are succeeding, ending with the most significant bit. If enabled, the parity bit is inserted after the data bits, before the stop bits. When a complete frame is transmitted, it can be directly followed by a new frame, or the communication line can be set to an idle (high) state.

Figure 19-4 on page 179 illustrates the possible combinations of the frame formats. Bits inside

brackets are optional.

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Figure 19-4.

Frame formats.

FRAME

(IDLE) St 0 1 2 3 4 [5] [6] [7] [8] [P] Sp1 [Sp2] (St / IDLE)

19.5.1

St

(n)

P

Sp

IDLE

Start bit, always low.

Data bits (0 to 8).

Parity bit. Can be odd or even.

Stop bit, always high.

No transfers on the communication line (RxDn or TxDn). An IDLE line must be high.

The frame format used by the USART is set by the UCSZn2:0, UPMn1:0 and USBSn bits in

UCSRnB and UCSRnC. The Receiver and Transmitter use the same setting. Note that changing the setting of any of these bits will corrupt all ongoing communication for both the Receiver and

Transmitter.

The USART Character SiZe (UCSZn2:0) bits select the number of data bits in the frame. The

USART Parity mode (UPMn1:0) bits enable and set the type of parity bit. The selection between one or two stop bits is done by the USART Stop Bit Select (USBSn) bit. The Receiver ignores the second stop bit. An FE (Frame Error) will therefore only be detected in the cases where the first stop bit is zero.

Parity Bit Calculation

The parity bit is calculated by doing an exclusive-or of all the data bits. If odd parity is used, the result of the exclusive or is inverted. The relation between the parity bit and data bits is as follows::

P even

P odd

=

=

d d n

1

n

1

⊕ … ⊕

d

d

⊕ ⊕

d

⊕ … ⊕

d

3

3

d

2

2

d d

1

1

d

0

0

0

1

P even

P odd

Parity bit using even parity.

Parity bit using odd parity.

d n

Data bit n of the character.

If used, the parity bit is located between the last data bit and first stop bit of a serial frame.

19.6

USART Initialization

The USART has to be initialized before any communication can take place. The initialization process normally consists of setting the baud rate, setting frame format and enabling the

Transmitter or the Receiver depending on the usage. For interrupt driven USART operation, the

Global Interrupt Flag should be cleared and the USART interrupts should be disabled.

Before doing a re-initialization with changed baud rate or frame format, be sure that there are no ongoing transmissions during the period the registers are changed. The TXCn Flag can be used to check that the Transmitter has completed all transfers, and the RXC Flag can be used to

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check that there are no unread data in the receive buffer. Note that the TXCn Flag must be cleared before each transmission (before UDRn is written) if it is used for this purpose.

The following simple USART initialization code examples show one assembly and one C function that are equal in functionality. The examples assume asynchronous operation using polling

(no interrupts enabled) and a fixed frame format. The baud rate is given as a function parameter.

For the assembly code, the baud rate parameter is assumed to be stored in the r17:r16

Registers.

Assembly Code Example

(1)

USART_Init:

; Set baud rate

out

UBRRnH, r17

out

UBRRnL, r16

; Enable receiver and transmitter

ldi

r16, (1<<RXENn)|(1<<TXENn)

out

UCSRnB,r16

; Set frame format: 8data, 2stop bit

ldi

r16, (1<<USBSn)|(3<<UCSZn0)

out

UCSRnC,r16

ret

C Code Example

(1)

void

USART_Init( unsigned int baud )

{

/* Set baud rate */

UBRRnH = (unsigned char)(baud>>8);

UBRRnL = (unsigned char)baud;

/* Enable receiver and transmitter */

UCSRnB = (1<<RXENn)|(1<<TXENn);

/* Set frame format: 8data, 2stop bit */

UCSRnC = (1<<USBSn)|(3<<UCSZn0);

}

Note: 1.

See “About code examples” on page 9

.

More advanced initialization routines can be made that include frame format as parameters, disable interrupts and so on. However, many applications use a fixed setting of the baud and control registers, and for these types of applications the initialization code can be placed directly in the main routine, or be combined with initialization code for other I/O modules.

19.7

Data Transmission – The USART Transmitter

The USART Transmitter is enabled by setting the Transmit Enable (TXEN) bit in the UCSRnB

Register. When the Transmitter is enabled, the normal port operation of the TxDn pin is overridden by the USART and given the function as the Transmitter’s serial output. The baud rate, mode of operation and frame format must be set up once before doing any transmissions. If synchronous operation is used, the clock on the XCKn pin will be overridden and used as transmission clock.

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19.7.1

19.7.2

Sending Frames with 5 to 8 Data Bit

A data transmission is initiated by loading the transmit buffer with the data to be transmitted. The

CPU can load the transmit buffer by writing to the UDRn I/O location. The buffered data in the transmit buffer will be moved to the Shift Register when the Shift Register is ready to send a new frame. The Shift Register is loaded with new data if it is in idle state (no ongoing transmission) or immediately after the last stop bit of the previous frame is transmitted. When the Shift Register is loaded with new data, it will transfer one complete frame at the rate given by the Baud Register,

U2Xn bit or by XCKn depending on mode of operation.

The following code examples show a simple USART transmit function based on polling of the

Data Register Empty (UDREn) Flag. When using frames with less than eight bits, the most significant bits written to the UDRn are ignored. The USART has to be initialized before the function can be used. For the assembly code, the data to be sent is assumed to be stored in Register

R16

.

Assembly Code Example

(1)

USART_Transmit:

; Wait for empty transmit buffer

sbis

UCSRnA,UDREn

rjmp

USART_Transmit

; Put data (r16) into buffer, sends the data

out

UDRn,r16

ret

C Code Example

(1)

void

USART_Transmit( unsigned char data )

{

/* Wait for empty transmit buffer */

while

( !( UCSRnA & (1<<UDREn)) )

;

/* Put data into buffer, sends the data */

UDRn = data;

}

Note: 1.

See “About code examples” on page 9

.

The function simply waits for the transmit buffer to be empty by checking the UDREn Flag, before loading it with new data to be transmitted. If the Data Register Empty interrupt is utilized, the interrupt routine writes the data into the buffer.

Sending Frames with 9 Data Bit

If 9-bit characters are used (UCSZn = 7), the ninth bit must be written to the TXB8 bit in

UCSRnB before the low byte of the character is written to UDRn. The following code examples show a transmit function that handles 9-bit characters. For the assembly code, the data to be sent is assumed to be stored in registers R17:R16.

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19.7.3

Assembly Code Example

(1)(2)

USART_Transmit:

; Wait for empty transmit buffer

sbis

UCSRnA,UDREn

rjmp

USART_Transmit

; Copy 9th bit from r17 to TXB8

cbi

UCSRnB,TXB8

sbrc

r17,0

sbi

UCSRnB,TXB8

; Put LSB data (r16) into buffer, sends the data

out

UDRn,r16

ret

C Code Example

(1)(2)

void

USART_Transmit( unsigned int data )

{

/* Wait for empty transmit buffer */

while

( !( UCSRnA & (1<<UDREn))) )

;

/* Copy 9th bit to TXB8 */

UCSRnB &= ~(1<<TXB8); if ( data & 0x0100 )

UCSRnB |= (1<<TXB8);

/* Put data into buffer, sends the data */

UDRn = data;

}

Notes: 1. These transmit functions are written to be general functions. They can be optimized if the contents of the UCSRnB is static. For example, only the TXB8 bit of the UCSRnB Register is used after initialization.

2.

See “About code examples” on page 9

.

The ninth bit can be used for indicating an address frame when using multi processor communication mode or for other protocol handling as for example synchronization.

Transmitter Flags and Interrupts

The USART Transmitter has two flags that indicate its state: USART Data Register Empty

(UDREn) and Transmit Complete (TXCn). Both flags can be used for generating interrupts.

The Data Register Empty (UDREn) Flag indicates whether the transmit buffer is ready to receive new data. This bit is set when the transmit buffer is empty, and cleared when the transmit buffer contains data to be transmitted that has not yet been moved into the Shift Register. For compatibility with future devices, always write this bit to zero when writing the UCSRnA Register.

When the Data Register Empty Interrupt Enable (UDRIEn) bit in UCSRnB is written to one, the

USART Data Register Empty Interrupt will be executed as long as UDREn is set (provided that global interrupts are enabled). UDREn is cleared by writing UDRn. When interrupt-driven data transmission is used, the Data Register Empty interrupt routine must either write new data to

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19.7.4

UDRn in order to clear UDREn or disable the Data Register Empty interrupt, otherwise a new interrupt will occur once the interrupt routine terminates.

The Transmit Complete (TXCn) Flag bit is set one when the entire frame in the Transmit Shift

Register has been shifted out and there are no new data currently present in the transmit buffer.

The TXCn Flag bit is automatically cleared when a transmit complete interrupt is executed, or it can be cleared by writing a one to its bit location. The TXCn Flag is useful in half-duplex communication interfaces (like the RS-485 standard), where a transmitting application must enter receive mode and free the communication bus immediately after completing the transmission.

When the Transmit Compete Interrupt Enable (TXCIEn) bit in UCSRnB is set, the USART

Transmit Complete Interrupt will be executed when the TXCn Flag becomes set (provided that global interrupts are enabled). When the transmit complete interrupt is used, the interrupt handling routine does not have to clear the TXCn Flag, this is done automatically when the interrupt is executed.

Parity Generator

19.7.5

The Parity Generator calculates the parity bit for the serial frame data. When parity bit is enabled

(UPMn1 = 1), the transmitter control logic inserts the parity bit between the last data bit and the first stop bit of the frame that is sent.

Disabling the Transmitter

The disabling of the Transmitter (setting the TXEN to zero) will not become effective until ongoing and pending transmissions are completed, that is, when the Transmit Shift Register and

Transmit Buffer Register do not contain data to be transmitted. When disabled, the Transmitter will no longer override the TxDn pin.

19.8

Data Reception – The USART Receiver

19.8.1

The USART Receiver is enabled by writing the Receive Enable (RXENn) bit in the

UCSRnB Register to one. When the Receiver is enabled, the normal pin operation of the RxDn pin is overridden by the USART and given the function as the Receiver’s serial input. The baud rate, mode of operation and frame format must be set up once before any serial reception can be done. If synchronous operation is used, the clock on the XCKn pin will be used as transfer clock.

Receiving Frames with 5 to 8 Data Bits

The Receiver starts data reception when it detects a valid start bit. Each bit that follows the start bit will be sampled at the baud rate or XCKn clock, and shifted into the Receive Shift Register until the first stop bit of a frame is received. A second stop bit will be ignored by the Receiver.

When the first stop bit is received, that is, a complete serial frame is present in the Receive Shift

Register, the contents of the Shift Register will be moved into the receive buffer. The receive buffer can then be read by reading the UDRn I/O location.

The following code example shows a simple USART receive function based on polling of the

Receive Complete (RXCn) Flag. When using frames with less than eight bits the most significant bits of the data read from the UDRn will be masked to zero. The USART has to be initialized before the function can be used.

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19.8.2

Assembly Code Example

(1)

USART_Receive:

; Wait for data to be received

sbis

UCSRnA, RXCn

rjmp

USART_Receive

; Get and return received data from buffer

in

r16, UDRn

ret

C Code Example

(1)

unsigned char

USART_Receive( void )

{

/* Wait for data to be received */

while

( !(UCSRnA & (1<<RXCn)) )

;

/* Get and return received data from buffer */

return

UDRn;

}

Note: 1.

See “About code examples” on page 9

.

The function simply waits for data to be present in the receive buffer by checking the RXCn Flag, before reading the buffer and returning the value.

Receiving Frames with 9 Data Bits

If 9-bit characters are used (UCSZn=7) the ninth bit must be read from the RXB8n bit in

UCSRnB before reading the low bits from the UDRn. This rule applies to the FEn, DORn and

UPEn Status Flags as well. Read status from UCSRnA, then data from UDRn. Reading the

UDRn I/O location will change the state of the receive buffer FIFO and consequently the TXB8n,

FEn, DORn and UPEn bits, which all are stored in the FIFO, will change.

The following code example shows a simple USART receive function that handles both nine bit characters and the status bits.

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Assembly Code Example

(1)

USART_Receive:

; Wait for data to be received

sbis

UCSRnA, RXCn

rjmp

USART_Receive

; Get status and 9th bit, then data from buffer

in

r18, UCSRnA

in

r17, UCSRnB

in

r16, UDRn

; If error, return -1

andi

r18,(1<<FEn)|(1<<DORn)|(1<<UPEn)

breq

USART_ReceiveNoError

ldi

r17, HIGH(-1)

ldi

r16, LOW(-1)

USART_ReceiveNoError:

; Filter the 9th bit, then return

lsr

r17

andi

r17, 0x01

ret

C Code Example

(1)

unsigned int

USART_Receive( void )

{

unsigned char

status, resh, resl;

/* Wait for data to be received */

while

( !(UCSRnA & (1<<RXCn)) )

;

/* Get status and 9th bit, then data */

/* from buffer */ status = UCSRnA; resh = UCSRnB; resl = UDRn;

/* If error, return -1 */

if

( status & (1<<FEn)|(1<<DORn)|(1<<UPEn) )

return

-1;

/* Filter the 9th bit, then return */ resh = (resh >> 1) & 0x01;

return

((resh << 8) | resl);

}

Note: 1.

See “About code examples” on page 9

.

The receive function example reads all the I/O Registers into the Register File before any computation is done. This gives an optimal receive buffer utilization since the buffer location read will be free to accept new data as early as possible.

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19.8.3

19.8.4

19.8.5

Receive Compete Flag and Interrupt

The USART Receiver has one flag that indicates the Receiver state.

The Receive Complete (RXCn) Flag indicates if there are unread data present in the receive buffer. This flag is one when unread data exist in the receive buffer, and zero when the receive buffer is empty (i.e., does not contain any unread data). If the Receiver is disabled (RXENn = 0), the receive buffer will be flushed and consequently the RXCn bit will become zero.

When the Receive Complete Interrupt Enable (RXCIEn) in UCSRnB is set, the USART Receive

Complete interrupt will be executed as long as the RXCn Flag is set (provided that global interrupts are enabled). When interrupt-driven data reception is used, the receive complete routine must read the received data from UDRn in order to clear the RXCn Flag, otherwise a new interrupt will occur once the interrupt routine terminates.

Receiver Error Flags

Parity Checker

The USART Receiver has three Error Flags: Frame Error (FEn), Data OverRun (DORn) and

Parity Error (UPEn). All can be accessed by reading UCSRnA. Common for the Error Flags is that they are located in the receive buffer together with the frame for which they indicate the error status. Due to the buffering of the Error Flags, the UCSRnA must be read before the receive buffer (UDRn), since reading the UDRn I/O location changes the buffer read location.

Another equality for the Error Flags is that they can not be altered by software doing a write to the flag location. However, all flags must be set to zero when the UCSRnA is written for upward compatibility of future USART implementations. None of the Error Flags can generate interrupts.

The Frame Error (FEn) Flag indicates the state of the first stop bit of the next readable frame stored in the receive buffer. The FEn Flag is zero when the stop bit was correctly read (as one), and the FEn Flag will be one when the stop bit was incorrect (zero). This flag can be used for detecting out-of-sync conditions, detecting break conditions and protocol handling. The FEn

Flag is not affected by the setting of the USBSn bit in UCSRnC since the Receiver ignores all, except for the first, stop bits. For compatibility with future devices, always set this bit to zero when writing to UCSRnA.

The Data OverRun (DORn) Flag indicates data loss due to a receiver buffer full condition. A

Data OverRun occurs when the receive buffer is full (two characters), it is a new character waiting in the Receive Shift Register, and a new start bit is detected. If the DORn Flag is set there was one or more serial frame lost between the frame last read from UDRn, and the next frame read from UDRn. For compatibility with future devices, always write this bit to zero when writing to UCSRnA. The DORn Flag is cleared when the frame received was successfully moved from the Shift Register to the receive buffer.

The Parity Error (UPEn) Flag indicates that the next frame in the receive buffer had a Parity

Error when received. If Parity Check is not enabled the UPEn bit will always be read zero. For compatibility with future devices, always set this bit to zero when writing to UCSRnA. For more

details see ”Parity Bit Calculation” on page 179

and ”Parity Checker” on page 186

.

The Parity Checker is active when the high USART Parity mode (UPMn1) bit is set. Type of Parity Check to be performed (odd or even) is selected by the UPMn0 bit. When enabled, the Parity

Checker calculates the parity of the data bits in incoming frames and compares the result with the parity bit from the serial frame. The result of the check is stored in the receive buffer together

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19.8.6

19.8.7

with the received data and stop bits. The Parity Error (UPEn) Flag can then be read by software to check if the frame had a Parity Error.

The UPEn bit is set if the next character that can be read from the receive buffer had a Parity

Error when received and the Parity Checking was enabled at that point (UPMn1 = 1). This bit is valid until the receive buffer (UDRn) is read.

Disabling the Receiver

In contrast to the Transmitter, disabling of the Receiver will be immediate. Data from ongoing receptions will therefore be lost. When disabled (that is, the RXENn is set to zero) the Receiver will no longer override the normal function of the RxDn port pin. The Receiver buffer FIFO will be flushed when the Receiver is disabled. Remaining data in the buffer will be lost

Flushing the Receive Buffer

The receiver buffer FIFO will be flushed when the Receiver is disabled, that is, the buffer will be emptied of its contents. Unread data will be lost. If the buffer has to be flushed during normal operation, due to for instance an error condition, read the UDRn I/O location until the RXCn Flag is cleared. The following code example shows how to flush the receive buffer.

Assembly Code Example

(1)

USART_Flush:

sbis

UCSRnA, RXCn

ret in

r16, UDRn

rjmp

USART_Flush

C Code Example

(1)

void

USART_Flush( void )

{

unsigned char

dummy;

while

( UCSRnA & (1<<RXCn) ) dummy = UDRn;

}

Note: 1.

See “About code examples” on page 9

.

19.9

Asynchronous Data Reception

19.9.1

The USART includes a clock recovery and a data recovery unit for handling asynchronous data reception. The clock recovery logic is used for synchronizing the internally generated baud rate clock to the incoming asynchronous serial frames at the RxDn pin. The data recovery logic samples and low pass filters each incoming bit, thereby improving the noise immunity of the

Receiver. The asynchronous reception operational range depends on the accuracy of the internal baud rate clock, the rate of the incoming frames, and the frame size in number of bits.

Asynchronous Clock Recovery

The clock recovery logic synchronizes internal clock to the incoming serial frames.

Figure 19-5

illustrates the sampling process of the start bit of an incoming frame. The sample rate is 16 times the baud rate for Normal mode, and eight times the baud rate for Double Speed mode. The horizontal arrows illustrate the synchronization variation due to the sampling process. Note the

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larger time variation when using the Double Speed mode (U2Xn = 1) of operation. Samples denoted zero are samples done when the RxDn line is idle (that is, no communication activity).

Figure 19-5.

Start bit sampling.

RxD IDLE START BIT 0

Sample

(U2X = 0)

Sample

(U2X = 1)

0 0 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 1 2 3

0 1 2 3 4 5 6 7 8 1 2

19.9.2

When the clock recovery logic detects a high (idle) to low (start) transition on the RxDn line, the start bit detection sequence is initiated. Let sample 1 denote the first zero-sample as shown in the figure. The clock recovery logic then uses samples 8, 9, and 10 for Normal mode, and samples 4, 5, and 6 for Double Speed mode (indicated with sample numbers inside boxes on the figure), to decide if a valid start bit is received. If two or more of these three samples have logical high levels (the majority wins), the start bit is rejected as a noise spike and the Receiver starts looking for the next high to low-transition. If however, a valid start bit is detected, the clock recovery logic is synchronized and the data recovery can begin. The synchronization process is repeated for each start bit.

Asynchronous Data Recovery

When the receiver clock is synchronized to the start bit, the data recovery can begin. The data recovery unit uses a state machine that has 16 states for each bit in Normal mode and eight

states for each bit in Double Speed mode. Figure 19-6

shows the sampling of the data bits and the parity bit. Each of the samples is given a number that is equal to the state of the recovery unit.

Figure 19-6.

Sampling of Data and Parity bit.

RxD BIT n

Sample

(U2X = 0)

Sample

(U2X = 1)

1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 1

1 2 3 4 5 6 7 8 1

The decision of the logic level of the received bit is taken by doing a majority voting of the logic value to the three samples in the center of the received bit. The center samples are emphasized on the figure by having the sample number inside boxes. The majority voting process is done as follows: If two or all three samples have high levels, the received bit is registered to be a logic 1.

If two or all three samples have low levels, the received bit is registered to be a logic 0. This majority voting process acts as a low pass filter for the incoming signal on the RxDn pin. The recovery process is then repeated until a complete frame is received. Including the first stop bit.

Note that the Receiver only uses the first stop bit of a frame.

Figure 19-7 on page 189

shows the sampling of the stop bit and the earliest possible beginning of the start bit of the next frame.

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Figure 19-7.

Stop Bit Sampling and Next Start Bit Sampling.

RxD STOP 1 (A) (B)

Sample

(U2X = 0)

Sample

(U2X = 1)

1 2 3 4 5 6 7 8 9 10 0/1 0/1 0/1

1 2 3 4 5 6 0/1

(C)

19.9.3

The same majority voting is done to the stop bit as done for the other bits in the frame. If the stop bit is registered to have a logic 0 value, the Frame Error (FEn) Flag will be set.

A new high to low transition indicating the start bit of a new frame can come right after the last of the bits used for majority voting. For Normal Speed mode, the first low level sample can be at

point marked (A) in Figure 19-7 on page 189

. For Double Speed mode the first low level must be delayed to (B). (C) marks a stop bit of full length. The early start bit detection influences the operational range of the Receiver.

Asynchronous Operational Range

The operational range of the Receiver is dependent on the mismatch between the received bit rate and the internally generated baud rate. If the Transmitter is sending frames at too fast or too slow bit rates, or the internally generated baud rate of the Receiver does not have a similar (see

Table 19-2 on page 190

) base frequency, the Receiver will not be able to synchronize the frames to the start bit.

The following equations can be used to calculate the ratio of the incoming data rate and internal receiver baud rate.

R slow

=

S

1

(

D

+

+

1

)S

D S

+

S

F

R fast

=

(

D

(

D

+

1

+

2

)S

+

M

D

S

S

F

Sum of character size and parity size (D = 5 to 10 bit).

Samples per bit. S = 16 for Normal Speed mode and S = 8 for Double Speed mode.

First sample number used for majority voting. S

F

= 8 for normal speed and S

F

= 4 for Double Speed mode.

S

R

M slow

Middle sample number used for majority voting. S

M

= 9 for normal speed and

S

M

= 5 for Double Speed mode.

is the ratio of the slowest incoming data rate that can be accepted in relation to the receiver baud rate. R fast

is the ratio of the fastest incoming data rate that can be accepted in relation to the receiver baud rate.

Table 19-2 on page 190 and Table 19-3 on page 190

list the maximum receiver baud rate error that can be tolerated. Note that Normal Speed mode has higher toleration of baud rate variations.

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Table 19-2.

Recommended Maximum Receiver Baud Rate Error for Normal Speed Mode

(U2Xn = 0).

D

# (Data+Parity Bit)

5

6

9

10

7

8

R slow

[%]

93.20

94.12

94.81

95.36

95.81

96.17

R fast

[%]

106.67

105.79

105.11

104.58

104.14

103.78

Maximum total error

[%]

+6.67/-6.8

+5.79/-5.88

+5.11/-5.19

+4.58/-4.54

+4.14/-4.19

+3.78/-3.83

Recommended max. receiver error [%]

±3.0

±2.5

±2.0

±2.0

±1.5

±1.5

Table 19-3.

Recommended Maximum Receiver Baud Rate Error for Double Speed Mode

(U2Xn = 1).

D

# (Data+Parity Bit)

5

8

9

6

7

10

R slow

[%]

94.12

94.92

95.52

96.00

96.39

96.70

R fast

[%]

105.66

104.92

104,35

103.90

103.53

103.23

Maximum total error

[%]

+5.66/-5.88

+4.92/-5.08

+4.35/-4.48

+3.90/-4.00

+3.53/-3.61

+3.23/-3.30

Recommended max. receiver error [%]

±2.5

±2.0

±1.5

±1.5

±1.5

±1.0

The recommendations of the maximum receiver baud rate error was made under the assumption that the Receiver and Transmitter equally divides the maximum total error.

There are two possible sources for the receivers baud rate error. The Receiver’s system clock

(XTAL) will always have some minor instability over the supply voltage range and the temperature range. When using a crystal to generate the system clock, this is rarely a problem, but for a resonator the system clock may differ more than 2% depending of the resonators tolerance. The second source for the error is more controllable. The baud rate generator can not always do an exact division of the system frequency to get the baud rate wanted. In this case an UBRR value that gives an acceptable low error can be used if possible.

19.10 Multi-processor Communication mode

Setting the Multi-processor Communication mode (MPCMn) bit in UCSRnA enables a filtering function of incoming frames received by the USART Receiver. Frames that do not contain address information will be ignored and not put into the receive buffer. This effectively reduces the number of incoming frames that has to be handled by the CPU, in a system with multiple

MCUs that communicate via the same serial bus. The Transmitter is unaffected by the MPCMn setting, but has to be used differently when it is a part of a system utilizing the Multi-processor

Communication mode.

If the Receiver is set up to receive frames that contain 5 to 8 data bits, then the first stop bit indicates if the frame contains data or address information. If the Receiver is set up for frames with nine data bits, then the ninth bit (RXB8n) is used for identifying address and data frames. When

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19.10.1

Using MPCMn

the frame type bit (the first stop or the ninth bit) is one, the frame contains an address. When the frame type bit is zero the frame is a data frame.

The Multi-processor Communication mode enables several slave MCUs to receive data from a master MCU. This is done by first decoding an address frame to find out which MCU has been addressed. If a particular slave MCU has been addressed, it will receive the following data frames as normal, while the other slave MCUs will ignore the received frames until another address frame is received.

For an MCU to act as a master MCU, it can use a 9-bit character frame format (UCSZn = 7). The ninth bit (TXB8n) must be set when an address frame (TXB8n = 1) or cleared when a data frame

(TXB = 0) is being transmitted. The slave MCUs must in this case be set to use a 9-bit character frame format.

The following procedure should be used to exchange data in Multi-processor Communication mode:

1. All Slave MCUs are in Multi-processor Communication mode (MPCMn in UCSRnA is set).

2. The Master MCU sends an address frame, and all slaves receive and read this frame. In the Slave MCUs, the RXCn Flag in UCSRnA will be set as normal.

3. Each Slave MCU reads the UDRn Register and determines if it has been selected. If so, it clears the MPCMn bit in UCSRnA, otherwise it waits for the next address byte and keeps the MPCMn setting.

4. The addressed MCU will receive all data frames until a new address frame is received.

The other Slave MCUs, which still have the MPCMn bit set, will ignore the data frames.

5. When the last data frame is received by the addressed MCU, the addressed MCU sets the MPCMn bit and waits for a new address frame from master. The process then repeats from 2.

Using any of the 5- to 8-bit character frame formats is possible, but impractical since the

Receiver must change between using n and n+1 character frame formats. This makes fullduplex operation difficult since the Transmitter and Receiver uses the same character size setting. If 5- to 8-bit character frames are used, the Transmitter must be set to use two stop bit

(USBSn = 1) since the first stop bit is used for indicating the frame type.

Do not use Read-Modify-Write instructions (SBI and CBI) to set or clear the MPCMn bit. The

MPCMn bit shares the same I/O location as the TXCn Flag and this might accidentally be cleared when using SBI or CBI instructions.

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19.11 Register description

19.11.1

UDRn – USART I/O Data Register n

Bit

Read/Write

Initial Value

7

R/W

0

6

R/W

0

5

R/W

0

4 3

RXB[7:0]

R/W

TXB[7:0]

R/W

0 0

2

R/W

0

1

R/W

0

0

R/W

0

UDRn (Read)

UDRn (Write)

The USART Transmit Data Buffer Register and USART Receive Data Buffer Registers share the same I/O address referred to as USART Data Register or UDRn. The Transmit Data Buffer Register (TXB) will be the destination for data written to the UDRn Register location. Reading the

UDRn Register location will return the contents of the Receive Data Buffer Register (RXB).

For 5-, 6-, or 7-bit characters the upper unused bits will be ignored by the Transmitter and set to zero by the Receiver.

The transmit buffer can only be written when the UDREn Flag in the UCSRnA Register is set.

Data written to UDRn when the UDREn Flag is not set, will be ignored by the USART Transmitter. When data is written to the transmit buffer, and the Transmitter is enabled, the Transmitter will load the data into the Transmit Shift Register when the Shift Register is empty. Then the data will be serially transmitted on the TxDn pin.

The receive buffer consists of a two level FIFO. The FIFO will change its state whenever the receive buffer is accessed. Due to this behavior of the receive buffer, do not use Read-Modify-

Write instructions (SBI and CBI) on this location. Be careful when using bit test instructions

(SBIC and SBIS), since these also will change the state of the FIFO.

19.11.2

UCSRnA – USART Control and Status Register A

Bit

Read/Write

Initial Value

7

RXCn

R

0

6

TXCn

R/W

0

5

UDREn

R

1

4

FEn

R

0

3

DORn

R

0

2

UPEn

R

0

1

U2Xn

R/W

0

0

MPCMn

R/W

0

UCSRnA

• Bit 7 – RXCn: USART Receive Complete

This flag bit is set when there are unread data in the receive buffer and cleared when the receive buffer is empty (that is, does not contain any unread data). If the Receiver is disabled, the receive buffer will be flushed and consequently the RXCn bit will become zero. The RXCn Flag can be used to generate a Receive Complete interrupt (see description of the RXCIEn bit).

• Bit 6 – TXCn: USART Transmit Complete

This flag bit is set when the entire frame in the Transmit Shift Register has been shifted out and there are no new data currently present in the transmit buffer (UDRn). The TXCn Flag bit is automatically cleared when a transmit complete interrupt is executed, or it can be cleared by writing a one to its bit location. The TXCn Flag can generate a Transmit Complete interrupt (see description of the TXCIEn bit).

• Bit 5 – UDREn: USART Data Register Empty

The UDREn Flag indicates if the transmit buffer (UDRn) is ready to receive new data. If UDREn is one, the buffer is empty, and therefore ready to be written. The UDREn Flag can generate a

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Data Register Empty interrupt (see description of the UDRIEn bit).UDREn is set after a reset to indicate that the Transmitter is ready.

• Bit 4 – FEn: Frame Error

This bit is set if the next character in the receive buffer had a Frame Error when received. I.e., when the first stop bit of the next character in the receive buffer is zero. This bit is valid until the receive buffer (UDRn) is read. The FEn bit is zero when the stop bit of received data is one.

Always set this bit to zero when writing to UCSRnA.

• Bit 3 – DORn: Data OverRun

This bit is set if a Data OverRun condition is detected. A Data OverRun occurs when the receive buffer is full (two characters), it is a new character waiting in the Receive Shift Register, and a new start bit is detected. This bit is valid until the receive buffer (UDRn) is read. Always set this bit to zero when writing to UCSRnA.

• Bit 2 – UPEn: USART Parity Error

This bit is set if the next character in the receive buffer had a Parity Error when received and the

Parity Checking was enabled at that point (UPMn1 = 1). This bit is valid until the receive buffer

(UDRn) is read. Always set this bit to zero when writing to UCSRnA.

• Bit 1 – U2Xn: Double the USART Transmission Speed

This bit only has effect for the asynchronous operation. Write this bit to zero when using synchronous operation.

Writing this bit to one will reduce the divisor of the baud rate divider from 16 to 8 effectively doubling the transfer rate for asynchronous communication.

• Bit 0 – MPCMn: Multi-processor Communication Mode

This bit enables the Multi-processor Communication mode. When the MPCMn bit is written to one, all the incoming frames received by the USART Receiver that do not contain address information will be ignored. The Transmitter is unaffected by the MPCMn setting. For more detailed

information see ”Multi-processor Communication mode” on page 190

.

19.11.3

UCSRnB – USART Control and Status Register n B

Bit

Read/Write

Initial Value

7

RXCIEn

R/W

0

6

TXCIEn

R/W

0

5

UDRIEn

R/W

0

4

RXENn

R/W

0

3

TXENn

R/W

0

2

UCSZn2

R/W

0

1

RXB8n

R

0

0

TXB8n

R/W

0

UCSRnB

• Bit 7 – RXCIEn: RX Complete Interrupt Enable n

Writing this bit to one enables interrupt on the RXCn Flag. A USART Receive Complete interrupt will be generated only if the RXCIEn bit is written to one, the Global Interrupt Flag in SREG is written to one and the RXCn bit in UCSRnA is set.

• Bit 6 – TXCIEn: TX Complete Interrupt Enable n

Writing this bit to one enables interrupt on the TXCn Flag. A USART Transmit Complete interrupt will be generated only if the TXCIEn bit is written to one, the Global Interrupt Flag in SREG is written to one and the TXCn bit in UCSRnA is set.

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• Bit 5 – UDRIEn: USART Data Register Empty Interrupt Enable n

Writing this bit to one enables interrupt on the UDREn Flag. A Data Register Empty interrupt will be generated only if the UDRIEn bit is written to one, the Global Interrupt Flag in SREG is written to one and the UDREn bit in UCSRnA is set.

• Bit 4 – RXENn: Receiver Enable n

Writing this bit to one enables the USART Receiver. The Receiver will override normal port operation for the RxDn pin when enabled. Disabling the Receiver will flush the receive buffer invalidating the FEn, DORn, and UPEn Flags.

• Bit 3 – TXENn: Transmitter Enable n

Writing this bit to one enables the USART Transmitter. The Transmitter will override normal port operation for the TxDn pin when enabled. The disabling of the Transmitter (writing TXENn to zero) will not become effective until ongoing and pending transmissions are completed, i.e., when the Transmit Shift Register and Transmit Buffer Register do not contain data to be transmitted. When disabled, the Transmitter will no longer override the TxDn port.

• Bit 2 – UCSZn2: Character Size n

The UCSZn2 bits combined with the UCSZn1:0 bit in UCSRnC sets the number of data bits

(Character SiZe) in a frame the Receiver and Transmitter use.

• Bit 1 – RXB8n: Receive Data Bit 8 n

RXB8n is the ninth data bit of the received character when operating with serial frames with nine data bits. Must be read before reading the low bits from UDRn.

• Bit 0 – TXB8n: Transmit Data Bit 8 n

TXB8n is the ninth data bit in the character to be transmitted when operating with serial frames with nine data bits. Must be written before writing the low bits to UDRn.

19.11.4

UCSRnC – USART Control and Status Register n C

Bit

Read/Write

Initial Value

7

UMSELn1

R/W

0

6

UMSELn0

R/W

0

5

UPMn1

R/W

0

4

UPMn0

R/W

0

3

USBSn

R/W

0

2

UCSZn1

R/W

1

1

UCSZn0

R/W

1

0

UCPOLn

R/W

0

UCSRnC

• Bits 7:6 – UMSELn1:0 USART Mode Select

These bits select the mode of operation of the USARTn as shown in Table 19-4

..

Table 19-4.

UMSELn bits settings.

UMSELn1

0

0

1

1

UMSELn0

0

1

0

1

Mode

Asynchronous USART

Synchronous USART

(Reserved)

Master SPI (MSPIM)

(1)

Note: 1. See

”USART in SPI mode” on page 201

for full description of the Master SPI Mode (MSPIM) operation

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• Bits 5:4 – UPMn1:0: Parity Mode

These bits enable and set type of parity generation and check. If enabled, the Transmitter will automatically generate and send the parity of the transmitted data bits within each frame. The

Receiver will generate a parity value for the incoming data and compare it to the UPMn setting.

If a mismatch is detected, the UPEn Flag in UCSRnA will be set.

Table 19-5.

UPMn bits settings.

UPMn1

0

0

1

1

UPMn0

0

1

0

1

Parity Mode

Disabled

Reserved

Enabled, Even Parity

Enabled, Odd Parity

• Bit 3 – USBSn: Stop Bit Select

This bit selects the number of stop bits to be inserted by the Transmitter. The Receiver ignores this setting.

Table 19-6.

USBS bit settings.

USBSn

0

1

Stop bit(s)

1-bit

2-bit

• Bit 2:1 – UCSZn1:0: Character Size

The UCSZn1:0 bits combined with the UCSZn2 bit in UCSRnB sets the number of data bits

(Character SiZe) in a frame the Receiver and Transmitter use.

Table 19-7.

UCSZn bits settings.

UCSZn2

0

0

1

1

0

0

1

1

UCSZn1

0

0

0

0

1

1

1

1

UCSZn0

0

1

0

1

0

1

0

1

Character Size

5-bit

6-bit

7-bit

8-bit

Reserved

Reserved

Reserved

9-bit

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• Bit 0 – UCPOLn: Clock Polarity

This bit is used for synchronous mode only. Write this bit to zero when asynchronous mode is used. The UCPOLn bit sets the relationship between data output change and data input sample, and the synchronous clock (XCKn).

Table 19-8.

UCPOLn bit settings.

UCPOLn

0

1

Transmitted data changed (output of

TxDn pin)

Rising XCKn Edge

Falling XCKn Edge

Received data sampled (input on RxDn pin)

Falling XCKn Edge

Rising XCKn Edge

19.11.5

UBRRnL and UBRRnH – USART Baud Rate Registers

Bit

Read/Write

Initial Value

15

7

R

R/W

0

0

14

6

R

R/W

0

0

13

5

R

R/W

0

0

12 11

R

R/W

0

0

4

UBRR[7:0]

3

R/W

R/W

0

0

10

UBRR[11:8]

9

2

R/W

R/W

0

0

1

R/W

R/W

0

0

8

0

R/W

R/W

0

0

UBRRnH

UBRRnL

• Bit 15:12 – Reserved

These bits are reserved for future use. For compatibility with future devices, these bit must be written to zero when UBRRH is written.

• Bit 11:0 – UBRR11:0: USART Baud Rate Register

This is a 12-bit register which contains the USART baud rate. The UBRRH contains the four most significant bits, and the UBRRL contains the eight least significant bits of the USART baud rate. Ongoing transmissions by the Transmitter and Receiver will be corrupted if the baud rate is changed. Writing UBRRL will trigger an immediate update of the baud rate prescaler.

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19.12 Examples of Baud Rate Setting

For standard crystal and resonator frequencies, the most commonly used baud rates for asyn-

chronous operation can be generated by using the UBRR settings in Table 19-9 to

Table 19-12 .

UBRR values which yield an actual baud rate differing less than 0.5% from the target baud rate, are bold in the table. Higher error ratings are acceptable, but the Receiver will have less noise

resistance when the error ratings are high, especially for large serial frames (see ”Asynchronous

Operational Range” on page 189 ). The error values are calculated using the following equation:

Error[%]

=

BaudRate

Closest Match

1

Table 19-9.

Examples of UBRRn settings for commonly used oscillator frequencies.

Baud rate

[bps]

2400

f osc

= 1.0000MHz

U2Xn = 0 U2Xn = 1

UBRR

25

Error

0.2%

UBRR

51

Error

0.2%

f osc

= 1.8432MHz

U2Xn = 0 U2Xn = 1

UBRR Error

47 0.0%

UBRR

95

Error

0.0%

f osc

= 2.0000MHz

U2Xn = 0 U2Xn = 1

UBRR Error

51 0.2%

UBRR

103

Error

0.2%

4800

9600

14.4k

19.2k

28.8k

38.4k

57.6k

76.8k

115.2k

230.4k

250k

Max.

(1)

0

1

1

12

6

3

2

62.5kbps

0.2%

-7.0%

8.5%

8.5%

8.5%

-18.6%

8.5%

1

1

3

2

8

6

25

12

0

8.5%

125kbps

0.2%

0.2%

-3.5%

-7.0%

8.5%

8.5%

8.5%

-18.6%

1

1

3

2

23

11

7

5

0

0.0%

115.2kbps

0.0%

0.0%

0.0%

0.0%

0.0%

0.0%

0.0%

-25.0%

3

2

7

5

47

23

15

11

1

0

0.0%

0.0%

230.4kbps

0.0%

0.0%

0.0%

0.0%

0.0%

0.0%

0.0%

0.0%

1

1

3

2

25

12

8

6

0

8.5%

125kbps

0.2%

0.2%

-3.5%

-7.0%

8.5%

8.5%

8.5%

-18.6%

3

2

8

6

51

25

16

12

1

8.5%

0 0.0%

250kbps

0.2%

0.2%

2.1%

0.2%

-3.5%

-7.0%

8.5%

8.5%

1.

UBRR = 0, Error = 0.0%.

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Table 19-10.

Examples of UBRRn settings for commonly used oscillator frequencies. (Continued)

28.8k

38.4k

57.6k

76.8k

115.2k

230.4k

250k

0.5M

1M

Max.

(1)

Baud rate

[bps]

2400

4800

9600

14.4k

19.2k

f osc

= 3.6864MHz

U2Xn = 0

UBRR Error

U2Xn = 1

UBRR Error

95 0.0% 191 0.0%

47

23

15

11

0.0%

0.0%

0.0%

0.0%

95

47

31

23

0.0%

0.0%

0.0%

0.0%

0

1

0

3

2

7

5

230.4kbps

0.0%

0.0%

0.0%

0.0%

0.0%

0.0%

-7.8%

15

11

7

5

3

1

1

0

0.0%

0.0%

0.0%

0.0%

0.0%

0.0%

-7.8%

-7.8%

460.8kbps

f osc

= 4.0000MHz

U2Xn = 0

UBRR Error

U2Xn = 1

UBRR Error

103 0.2% 207 0.2%

51

25

16

12

0.2%

0.2%

2.1%

0.2%

103

51

34

25

0.2%

0.2%

-0.8%

0.2%

0

1

0

3

2

8

6

250kbps

-3.5%

-7.0%

8.5%

8.5%

8.5%

8.5%

0.0%

16

12

8

6

3

1

1

0

2.1%

0.2%

-3.5%

-7.0%

8.5%

8.5%

0.0%

0.0%

0.5Mbps

f osc

= 7.3728MHz

U2Xn = 0

UBRR Error

U2Xn = 1

UBRR Error

191 0.0% 383 0.0%

95

47

31

23

0.0%

0.0%

0.0%

0.0%

191

95

63

47

0.0%

0.0%

0.0%

0.0%

1

0

3

1

15

11

7

5

460.8kbps

0.0%

0.0%

0.0%

0.0%

0.0%

0.0%

-7.8%

-7.8%

31

23

15

11

3

1

7

3

0.0%

0.0%

0.0%

0.0%

0.0%

0.0%

-7.8%

-7.8%

0 -7.8%

921.6kbps

1.

UBRR = 0, Error = 0.0%.

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Table 19-11.

Examples of UBRRn settings for commonly used oscillator frequencies. (Continued)

28.8k

38.4k

57.6k

76.8k

115.2k

230.4k

250k

0.5M

1M

Max.

(1)

Baud rate

[bps]

2400

4800

9600

14.4k

19.2k

f osc

= 8.0000MHz

U2Xn = 0 U2Xn = 1

UBRR

207

Error

0.2%

UBRR

416

Error

-0.1%

103

51

34

25

0.2%

0.2%

-0.8%

0.2%

207

103

68

51

0.2%

0.2%

0.6%

0.2%

1

0

3

1

16

12

8

6

0.5Mbps

2.1%

0.2%

-3.5%

-7.0%

8.5%

8.5%

0.0%

0.0%

3

1

8

3

34

25

16

12

-0.8%

0.2%

2.1%

0.2%

-3.5%

8.5%

0.0%

0.0%

0

1Mbps

0.0%

f osc

= 11.0592MHz

U2Xn = 0 U2Xn = 1

UBRR Error

287 0.0%

UBRR

575

Error

0.0%

143

71

47

35

0.0%

0.0%

0.0%

0.0%

287

143

95

71

0.0%

0.0%

0.0%

0.0%

2

5

2

23

17

11

8

691.2kbps

0.0%

0.0%

0.0%

0.0%

0.0%

0.0%

-7.8%

47

35

23

17

11

5

5

2

0.0%

0.0%

0.0%

0.0%

0.0%

0.0%

-7.8%

-7.8%

1.3824Mbps

f osc

= 14.7456MHz

U2Xn = 0 U2Xn = 1

UBRR Error

383 0.0%

UBRR

767

Error

0.0%

191

95

63

47

0.0%

0.0%

0.0%

0.0%

383

191

127

95

0.0%

0.0%

0.0%

0.0%

3

1

7

3

31

23

15

11

0.0%

0.0%

0.0%

0.0%

0.0%

0.0%

-7.8%

-7.8%

0 -7.8%

921.6kbps

63

47

31

23

15

7

6

3

0.0%

0.0%

0.0%

0.0%

0.0%

0.0%

5.3%

-7.8%

1 -7.8%

1.8432Mbps

1.

UBRR = 0, Error = 0.0%.

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Table 19-12.

Examples of UBRRn settings for commonly used oscillator frequencies. (Continued)

28.8k

38.4k

57.6k

76.8k

115.2k

230.4k

250k

0.5M

1M

Max.

(1)

Baud rate

[bps]

2400

4800

9600

14.4k

19.2k

f osc

= 16.0000MHz

U2Xn = 0 U2Xn = 1

UBRR

416

Error

-0.1%

UBRR

832

Error

0.0%

207

103

68

51

0.2%

0.2%

0.6%

0.2%

416

207

138

103

-0.1%

0.2%

-0.1%

0.2%

3

1

8

3

34

25

16

12

-0.8%

0.2%

2.1%

0.2%

-3.5%

8.5%

0.0%

0.0%

0

1Mbps

0.0%

7

3

68

51

34

25

16

8

0.6%

0.2%

-0.8%

0.2%

2.1%

-3.5%

0.0%

0.0%

1

2Mbps

0.0%

f osc

= 18.4320MHz

U2Xn = 0 U2Xn = 1

UBRR Error

479 0.0%

UBRR

959

Error

0.0%

239

119

79

59

0.0%

0.0%

0.0%

0.0%

479

239

159

119

0.0%

0.0%

0.0%

0.0%

4

9

4

39

29

19

14

– –

1.152Mbps

0.0%

0.0%

0.0%

0.0%

0.0%

0.0%

-7.8%

79

59

39

29

19

9

8

4

0.0%

0.0%

0.0%

0.0%

0.0%

0.0%

2.4%

-7.8%

2.304Mbps

f osc

= 20.0000MHz

U2Xn = 0 U2Xn = 1

UBRR Error

520 0.0%

UBRR

1041

Error

0.0%

259

129

86

64

0.2%

0.2%

-0.2%

0.2%

520

259

173

129

0.0%

0.2%

-0.2%

0.2%

10

4

4

42

32

21

15

1.25Mbps

0.9%

-1.4%

-1.4%

1.7%

-1.4%

8.5%

0.0%

86

64

42

32

21

10

9

4

-0.2%

0.2%

0.9%

-1.4%

-1.4%

-1.4%

0.0%

0.0%

2.5Mbps

1.

UBRR = 0, Error = 0.0%.

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20. USART in SPI mode

20.1

Features

Full duplex, three-wire synchronous data transfer

Master Operation

Supports all four SPI modes of operation (Mode 0, 1, 2, and 3)

LSB first or MSB first data transfer (configurable data order)

Queued operation (double buffered)

High resolution baud rate generator

High speed operation (fXCKmax = fCK/2)

Flexible interrupt generation

20.2

Overview

The Universal Synchronous and Asynchronous serial Receiver and Transmitter (USART) can be set to a master SPI compliant mode of operation.

Setting both UMSELn1:0 bits to one enables the USART in MSPIM logic. In this mode of operation the SPI master control logic takes direct control over the USART resources. These resources include the transmitter and receiver shift register and buffers, and the baud rate generator. The parity generator and checker, the data and clock recovery logic, and the RX and TX control logic is disabled. The USART RX and TX control logic is replaced by a common SPI transfer control logic. However, the pin control logic and interrupt generation logic is identical in both modes of operation.

The I/O register locations are the same in both modes. However, some of the functionality of the control registers changes when using MSPIM.

20.3

Clock Generation

The Clock Generation logic generates the base clock for the Transmitter and Receiver. For

USART MSPIM mode of operation only internal clock generation (i.e. master operation) is supported. The Data Direction Register for the XCKn pin (DDR_XCKn) must therefore be set to one

(i.e. as output) for the USART in MSPIM to operate correctly. Preferably the DDR_XCKn should be set up before the USART in MSPIM is enabled (i.e. TXENn and RXENn bit set to one).

The internal clock generation used in MSPIM mode is identical to the USART synchronous master mode. The baud rate or UBRRn setting can therefore be calculated using the same

equations, see Table 20-1 :

Table 20-1.

Equations for calculating baud rate register setting.

Operating mode

Equation for calculating baud rate

(1)

Equation for calculating UBRRn value

Synchronous Master mode

BAUD

=

f

OSC

2 UBRRn

+

1

)

UBRR

n

=

f

OSC

1

Note: 1. The baud rate is defined to be the transfer rate in bit per second (bps).

BAUD

Baud rate (in bits per second, bps).

f

OSC

UBRRn

System oscillator clock frequency.

Contents of the UBRRnH and UBRRnL registers, (0-4095).

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20.4

SPI Data Modes and Timing

There are four combinations of XCKn (SCK) phase and polarity with respect to serial data, which are determined by control bits UCPHAn and UCPOLn. The data transfer timing diagrams are shown in

Figure 20-1

. Data bits are shifted out and latched in on opposite edges of the XCKn signal, ensuring sufficient time for data signals to stabilize. The UCPOLn and UCPHAn function-

ality is summarized in Table 20-2

. Note that changing the setting of any of these bits will corrupt all ongoing communication for both the Receiver and Transmitter.

Table 20-2.

UCPOLn and UCPHAn functionality.

UCPOLn

0

0

1

1

UCPHAn

0

1

0

1

SPI mode

0

1

2

3

Leading edge

Sample (Rising)

Setup (Rising)

Sample (Falling)

Setup (Falling)

Trailing edge

Setup (Falling)

Sample (Falling)

Setup (Rising)

Sample (Rising)

Figure 20-1.

UCPHAn and UCPOLn data transfer timing diagrams.

UCPOL=0 UCPOL=1

XCK

Data setup (TXD)

Data sample (RXD)

XCK

Data setup (TXD)

Data sample (RXD)

XCK

Data setup (TXD)

Data sample (RXD)

XCK

Data setup (TXD)

Data sample (RXD)

20.5

Frame Formats

A serial frame for the MSPIM is defined to be one character of eight data bits. The USART in

MSPIM mode has two valid frame formats:

• 8-bit data with MSB first

• 8-bit data with LSB first

A frame starts with the least or most significant data bit. Then the next data bits, up to a total of eight, are succeeding, ending with the most or least significant bit accordingly. When a complete frame is transmitted, a new frame can directly follow it, or the communication line can be set to an idle (high) state.

The UDORDn bit in UCSRnC sets the frame format used by the USART in MSPIM mode. The

Receiver and Transmitter use the same setting. Note that changing the setting of any of these bits will corrupt all ongoing communication for both the Receiver and Transmitter.

16-bit data transfer can be achieved by writing two data bytes to UDRn. A UART transmit complete interrupt will then signal that the 16-bit value has been shifted out.

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20.5.1

USART MSPIM Initialization

The USART in MSPIM mode has to be initialized before any communication can take place. The initialization process normally consists of setting the baud rate, setting master mode of operation

(by setting DDR_XCKn to one), setting frame format and enabling the Transmitter and the

Receiver. Only the transmitter can operate independently. For interrupt driven USART operation, the Global Interrupt Flag should be cleared (and thus interrupts globally disabled) when doing the initialization.

Note: To ensure immediate initialization of the XCKn output the baud-rate register (UBRRn) must be zero at the time the transmitter is enabled. Contrary to the normal mode USART operation the

UBRRn must then be written to the desired value after the transmitter is enabled, but before the first transmission is started. Setting UBRRn to zero before enabling the transmitter is not necessary if the initialization is done immediately after a reset since UBRRn is reset to zero.

Before doing a re-initialization with changed baud rate, data mode, or frame format, be sure that there is no ongoing transmissions during the period the registers are changed. The TXCn Flag can be used to check that the Transmitter has completed all transfers, and the RXCn Flag can be used to check that there are no unread data in the receive buffer. Note that the TXCn Flag must be cleared before each transmission (before UDRn is written) if it is used for this purpose.

The following simple USART initialization code examples show one assembly and one C function that are equal in functionality. The examples assume polling (no interrupts enabled). The baud rate is given as a function parameter. For the assembly code, the baud rate parameter is assumed to be stored in the r17:r16 registers.

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Assembly Code Example

(1)

USART_Init:

clr

r18

out

UBRRnH,r18

out

UBRRnL,r18

; Setting the XCKn port pin as output, enables master mode.

sbi

XCKn_DDR, XCKn

; Set MSPI mode of operation and SPI data mode 0.

ldi

r18, (1<<UMSELn1)|(1<<UMSELn0)|(0<<UCPHAn)|(0<<UCPOLn)

out

UCSRnC,r18

; Enable receiver and transmitter.

ldi

r18, (1<<RXENn)|(1<<TXENn)

out

UCSRnB,r18

; Set baud rate.

; IMPORTANT: The Baud Rate must be set after the transmitter is enabled!

out

UBRRnH, r17

out

UBRRnL, r18 ret

C Code Example

(1)

void

USART_Init( unsigned int baud )

{

UBRRn = 0;

/* Setting the XCKn port pin as output, enables master mode. */

XCKn_DDR |= (1<<XCKn);

/* Set MSPI mode of operation and SPI data mode 0. */

UCSRnC = (1<<UMSELn1)|(1<<UMSELn0)|(0<<UCPHAn)|(0<<UCPOLn);

/* Enable receiver and transmitter. */

UCSRnB = (1<<RXENn)|(1<<TXENn);

/* Set baud rate. */

/* IMPORTANT: The Baud Rate must be set after the transmitter is enabled

*/

UBRRn = baud;

}

20.6

Data Transfer

Note: 1.

See “About code examples” on page 9

.

Using the USART in MSPI mode requires the Transmitter to be enabled, that is, the TXENn bit in the UCSRnB register is set to one. When the Transmitter is enabled, the normal port operation of the TxDn pin is overridden and given the function as the Transmitter's serial output. Enabling the receiver is optional and is done by setting the RXENn bit in the UCSRnB register to one.

When the receiver is enabled, the normal pin operation of the RxDn pin is overridden and given the function as the Receiver's serial input. The XCKn will in both cases be used as the transfer clock.

After initialization the USART is ready for doing data transfers. A data transfer is initiated by writing to the UDRn I/O location. This is the case for both sending and receiving data since the

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transmitter controls the transfer clock. The data written to UDRn is moved from the transmit buffer to the shift register when the shift register is ready to send a new frame.

Note: To keep the input buffer in sync with the number of data bytes transmitted, the UDRn register must be read once for each byte transmitted. The input buffer operation is identical to normal USART mode, i.e. if an overflow occurs the character last received will be lost, not the first data in the buffer. This means that if four bytes are transferred, byte 1 first, then byte 2, 3, and 4, and the UDRn is not read before all transfers are completed, then byte 3 to be received will be lost, and not byte

1.

The following code examples show a simple USART in MSPIM mode transfer function based on polling of the Data Register Empty (UDREn) Flag and the Receive Complete (RXCn) Flag. The

USART has to be initialized before the function can be used. For the assembly code, the data to be sent is assumed to be stored in Register R16 and the data received will be available in the same register (R16) after the function returns.

The function simply waits for the transmit buffer to be empty by checking the UDREn Flag, before loading it with new data to be transmitted. The function then waits for data to be present in the receive buffer by checking the RXCn Flag, before reading the buffer and returning the value.

Assembly Code Example

(1)

USART_MSPIM_Transfer:

; Wait for empty transmit buffer

sbis

UCSRnA, UDREn

rjmp

USART_MSPIM_Transfer

; Put data (r16) into buffer, sends the data

out

UDRn,r16

; Wait for data to be received

USART_MSPIM_Wait_RXCn:

sbis

UCSRnA, RXCn

rjmp

USART_MSPIM_Wait_RXCn

; Get and return received data from buffer

in

r16, UDRn ret

C Code Example

(1)

unsigned char

USART_Receive( void )

{

/* Wait for empty transmit buffer */

while

( !( UCSRnA & (1<<UDREn)) );

/* Put data into buffer, sends the data */

UDRn = data;

/* Wait for data to be received */

while

( !(UCSRnA & (1<<RXCn)) );

/* Get and return received data from buffer */

return

UDRn;

}

Note: 1.

See “About code examples” on page 9

.

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20.6.1

Transmitter and Receiver Flags and Interrupts

The RXCn, TXCn, and UDREn flags and corresponding interrupts in USART in MSPIM mode are identical in function to the normal USART operation. However, the receiver error status flags

(FE, DOR, and PE) are not in use and is always read as zero.

Disabling the Transmitter or Receiver 20.6.2

The disabling of the transmitter or receiver in USART in MSPIM mode is identical in function to the normal USART operation.

20.7

AVR USART MSPIM vs. AVR SPI

The USART in MSPIM mode is fully compatible with the AVR SPI regarding:

• Master mode timing diagram.

• The UCPOLn bit functionality is identical to the SPI CPOL bit

• The UCPHAn bit functionality is identical to the SPI CPHA bit

• The UDORDn bit functionality is identical to the SPI DORD bit

However, since the USART in MSPIM mode reuses the USART resources, the use of the

USART in MSPIM mode is somewhat different compared to the SPI. In addition to differences of the control register bits, and that only master operation is supported by the USART in MSPIM mode, the following features differ between the two modules:

• The USART in MSPIM mode includes (double) buffering of the transmitter. The SPI has no buffer

• The USART in MSPIM mode receiver includes an additional buffer level

• The SPI WCOL (Write Collision) bit is not included in USART in MSPIM mode

• The SPI double speed mode (SPI2X) bit is not included. However, the same effect is achieved by setting UBRRn accordingly

• Interrupt timing is not compatible

• Pin control differs due to the master only operation of the USART in MSPIM mode

A comparison of the USART in MSPIM mode and the SPI pins is shown in

Table 20-3 on page

206 .

Table 20-3.

Comparison of USART in MSPIM mode and SPI pins.

USART_MSPIM

TxDn

RxDn

XCKn

(N/A)

SPI

MOSI

MISO

SCK

SS

Comment

Master Out only

Master In only

(Functionally identical)

Not supported by USART in MSPIM

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20.8

Register description

20.8.1

The following section describes the registers used for SPI operation using the USART.

UDRn – USART MSPIM I/O Data Register

20.8.2

The function and bit description of the USART data register (UDRn) in MSPI mode is identical to

normal USART operation. See “UDRn – USART I/O Data Register n” on page 192

.

UCSRnA – USART MSPIM Control and Status Register n A

20.8.3

Bit

Read/Write

Initial Value

7

RXCn

R/W

0

6

TXCn

R/W

0

5

UDREn

R/W

0

R

0

4

R

0

3

R

1

2

R

1

1

R

0

0

– UCSRnA

• Bit 7 – RXCn: USART Receive Complete

This flag bit is set when there are unread data in the receive buffer and cleared when the receive buffer is empty (that is, does not contain any unread data). If the Receiver is disabled, the receive buffer will be flushed and consequently the RXCn bit will become zero. The RXCn Flag can be used to generate a Receive Complete interrupt (see description of the RXCIEn bit).

• Bit 6 – TXCn: USART Transmit Complete

This flag bit is set when the entire frame in the Transmit Shift Register has been shifted out and there are no new data currently present in the transmit buffer (UDRn). The TXCn Flag bit is automatically cleared when a transmit complete interrupt is executed, or it can be cleared by writing a one to its bit location. The TXCn Flag can generate a Transmit Complete interrupt (see description of the TXCIEn bit).

• Bit 5 – UDREn: USART Data Register Empty

The UDREn Flag indicates if the transmit buffer (UDRn) is ready to receive new data. If UDREn is one, the buffer is empty, and therefore ready to be written. The UDREn Flag can generate a

Data Register Empty interrupt (see description of the UDRIE bit). UDREn is set after a reset to indicate that the Transmitter is ready.

• Bit 4:0 – Reserved in MSPI mode

When in MSPI mode, these bits are reserved for future use. For compatibility with future devices, these bits must be written to zero when UCSRnA is written.

UCSRnB – USART MSPIM Control and Status Register n B

Bit

Read/Write

Initial Value

7

RXCIEn

R/W

0

6

TXCIEn

R/W

0

5

UDRIE

R/W

0

4

RXENn

R/W

0

3

TXENn

R/W

0

R

1

2

R

1

1

R

0

0

– UCSRnB

• Bit 7 – RXCIEn: RX Complete Interrupt Enable

Writing this bit to one enables interrupt on the RXCn Flag. A USART Receive Complete interrupt will be generated only if the RXCIEn bit is written to one, the Global Interrupt Flag in SREG is written to one and the RXCn bit in UCSRnA is set.

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20.8.4

• Bit 6 – TXCIEn: TX Complete Interrupt Enable

Writing this bit to one enables interrupt on the TXCn Flag. A USART Transmit Complete interrupt will be generated only if the TXCIEn bit is written to one, the Global Interrupt Flag in SREG is written to one and the TXCn bit in UCSRnA is set.

• Bit 5 – UDRIE: USART Data Register Empty Interrupt Enable

Writing this bit to one enables interrupt on the UDREn Flag. A Data Register Empty interrupt will be generated only if the UDRIE bit is written to one, the Global Interrupt Flag in SREG is written to one and the UDREn bit in UCSRnA is set.

• Bit 4 – RXENn: Receiver Enable

Writing this bit to one enables the USART Receiver in MSPIM mode. The Receiver will override normal port operation for the RxDn pin when enabled. Disabling the Receiver will flush the receive buffer. Only enabling the receiver in MSPI mode (i.e. setting RXENn=1 and TXENn=0) has no meaning since it is the transmitter that controls the transfer clock and since only master mode is supported.

• Bit 3 – TXENn: Transmitter Enable

Writing this bit to one enables the USART Transmitter. The Transmitter will override normal port operation for the TxDn pin when enabled. The disabling of the Transmitter (writing TXENn to zero) will not become effective until ongoing and pending transmissions are completed, that is, when the Transmit Shift Register and Transmit Buffer Register do not contain data to be transmitted. When disabled, the Transmitter will no longer override the TxDn port.

• Bit 2:0 – Reserved in MSPI mode

When in MSPI mode, these bits are reserved for future use. For compatibility with future devices, these bits must be written to zero when UCSRnB is written.

UCSRnC – USART MSPIM Control and Status Register n C

Bit

Read/Write

Initial Value

7

UMSELn1

R/W

0

6

UMSELn0

R/W

0

5

R

0

4

R

0

3

R

0

2

UDORDn

R/W

1

1

UCPHAn

R/W

1

0

UCPOLn

R/W

0

UCSRnC

• Bit 7:6 – UMSELn1:0: USART Mode Select

These bits select the mode of operation of the USART as shown in

Table 20-4

. See

”UCSRnC –

USART Control and Status Register n C” on page 194 for full description of the normal USART

operation. The MSPIM is enabled when both UMSELn bits are set to one. The UDORDn,

UCPHAn, and UCPOLn can be set in the same write operation where the MSPIM is enabled.

Table 20-4.

UMSELn bits settings.

UMSELn1

0

UMSELn0

0

Mode

Asynchronous USART

0 1 Synchronous USART

1 0 (Reserved)

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20.8.5

• Bit 5:3 – Reserved in MSPI mode

When in MSPI mode, these bits are reserved for future use. For compatibility with future devices, these bits must be written to zero when UCSRnC is written.

• Bit 2 – UDORDn: Data Order

When set to one the LSB of the data word is transmitted first. When set to zero the MSB of the data word is transmitted first. Refer to

”Frame Formats” on page 202 for details.

• Bit 1 – UCPHAn: Clock Phase

The UCPHAn bit setting determine if data is sampled on the leasing edge (first) or tailing (last) edge of XCKn. Refer to

”SPI Data Modes and Timing” on page 202 for details.

• Bit 0 – UCPOLn: Clock Polarity

The UCPOLn bit sets the polarity of the XCKn clock. The combination of the UCPOLn and

UCPHAn bit settings determine the timing of the data transfer. Refer to

”SPI Data Modes and

Timing” on page 202

for details.

UBRRnL and UBRRnH –USART MSPIM Baud Rate Registers

The function and bit description of the baud rate registers in MSPI mode is identical to normal

USART operation. See ”UBRRnL and UBRRnH – USART Baud Rate Registers” on page 196 .

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21. Two-wire Serial Interface

21.1

Features

Simple yet powerful and flexible communication interface, only two bus lines needed

Both Master and Slave operation supported

Device can operate as transmitter or receiver

7-bit address space allows up to 128 different Slave addresses

Multi-master arbitration support

Up to 400kHz data transfer speed

Slew-rate limited output drivers

Noise suppression circuitry rejects spikes on bus lines

Fully programmable Slave address with General Call support

Address recognition causes wake-up when AVR is in Sleep mode

21.2

Two-wire Serial Interface bus definition

The Two-wire Serial Interface (TWI) is ideally suited for typical microcontroller applications. The

TWI protocol allows the systems designer to interconnect up to 128 different devices using only two bi-directional bus lines, one for clock (SCL) and one for data (SDA). The only external hardware needed to implement the bus is a single pull-up resistor for each of the TWI bus lines. All devices connected to the bus have individual addresses, and mechanisms for resolving bus contention are inherent in the TWI protocol.

Figure 21-1.

TWI bus interconnection.

V

CC

Device 1

Device 2

Device 3 ........

Device n

R1 R2

SDA

21.2.1

SCL

TWI Terminology

The following definitions are frequently encountered in this section.

Table 21-1.

TWI terminology.

Term

Master

Slave

Transmitter

Receiver

Description

The device that initiates and terminates a transmission. The Master also generates the

SCL clock.

The device addressed by a Master.

The device placing data on the bus.

The device reading data from the bus.

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21.2.2

The Power Reduction TWI bit, PRTWI bit in

”PRR0 – Power Reduction Register 0” on page 48

must be written to zero to enable the two-wire Serial Interface.

Electrical Interconnection

As depicted in Figure 21-1 , both bus lines are connected to the positive supply voltage through

pull-up resistors. The bus drivers of all TWI-compliant devices are open-drain or open-collector.

This implements a wired-AND function which is essential to the operation of the interface. A low level on a TWI bus line is generated when one or more TWI devices output a zero. A high level is output when all TWI devices trim-state their outputs, allowing the pull-up resistors to pull the line high. Note that all AVR devices connected to the TWI bus must be powered in order to allow any bus operation.

The number of devices that can be connected to the bus is only limited by the bus capacitance limit of 400pF and the 7-bit slave address space. A detailed specification of the electrical charac-

teristics of the TWI is given in ”SPI timing characteristics” on page 338

. Two different sets of specifications are presented there, one relevant for bus speeds below 100kHz, and one valid for bus speeds up to 400kHz.

21.3

Data Transfer and Frame Format

21.3.1

Transferring Bits

Each data bit transferred on the TWI bus is accompanied by a pulse on the clock line. The level of the data line must be stable when the clock line is high. The only exception to this rule is for generating start and stop conditions.

Figure 21-2.

Data validity.

SDA

21.3.2

SCL

Data Stable Data Stable

Data Change

START and STOP Conditions

The Master initiates and terminates a data transmission. The transmission is initiated when the

Master issues a START condition on the bus, and it is terminated when the Master issues a

STOP condition. Between a START and a STOP condition, the bus is considered busy, and no other master should try to seize control of the bus. A special case occurs when a new START condition is issued between a START and STOP condition. This is referred to as a REPEATED

START condition, and is used when the Master wishes to initiate a new transfer without relinquishing control of the bus. After a REPEATED START, the bus is considered busy until the next

STOP. This is identical to the START behavior, and therefore START is used to describe both

START and REPEATED START for the remainder of this datasheet, unless otherwise noted. As

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depicted below, START and STOP conditions are signalled by changing the level of the SDA line when the SCL line is high.

Figure 21-3.

START, REPEATED START and STOP conditions.

SDA

SCL

21.3.3

Address Packet Format

START STOP START REPEATED START STOP

All address packets transmitted on the TWI bus are 9 bits long, consisting of 7 address bits, one

READ/WRITE control bit and an acknowledge bit. If the READ/WRITE bit is set, a read operation is to be performed, otherwise a write operation should be performed. When a Slave recognizes that it is being addressed, it should acknowledge by pulling SDA low in the ninth SCL

(ACK) cycle. If the addressed Slave is busy, or for some other reason can not service the Master’s request, the SDA line should be left high in the ACK clock cycle. The Master can then transmit a STOP condition, or a REPEATED START condition to initiate a new transmission. An address packet consisting of a slave address and a READ or a WRITE bit is called SLA+R or

SLA+W, respectively.

The MSB of the address byte is transmitted first. Slave addresses can freely be allocated by the designer, but the address 0000 000 is reserved for a general call.

When a general call is issued, all slaves should respond by pulling the SDA line low in the ACK cycle. A general call is used when a Master wishes to transmit the same message to several slaves in the system. When the general call address followed by a Write bit is transmitted on the bus, all slaves set up to acknowledge the general call will pull the SDA line low in the ack cycle.

The following data packets will then be received by all the slaves that acknowledged the general call. Note that transmitting the general call address followed by a Read bit is meaningless, as this would cause contention if several slaves started transmitting different data.

All addresses of the format 1111 xxx should be reserved for future purposes.

Figure 21-4.

Address packet format.

Addr MSB

SDA

Addr LSB R/W ACK

SCL

1 2 7 8

9

START

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21.3.4

Data Packet Format

All data packets transmitted on the TWI bus are nine bits long, consisting of one data byte and an acknowledge bit. During a data transfer, the Master generates the clock and the START and

STOP conditions, while the Receiver is responsible for acknowledging the reception. An

Acknowledge (ACK) is signalled by the Receiver pulling the SDA line low during the ninth SCL cycle. If the Receiver leaves the SDA line high, a NACK is signalled. When the Receiver has received the last byte, or for some reason cannot receive any more bytes, it should inform the

Transmitter by sending a NACK after the final byte. The MSB of the data byte is transmitted first.

Figure 21-5.

Data packet format.

Data MSB

Aggregate

SDA

SDA from

Transmitter

SDA from

Receiver

SCL from

Master

1

SLA+R/W

2

Data LSB ACK

7

Data Byte

8

9

STOP, REPEATED

START or Next

Data Byte

21.3.5

Combining Address and Data Packets into a Transmission

A transmission basically consists of a START condition, a SLA+R/W, one or more data packets and a STOP condition. An empty message, consisting of a START followed by a STOP condition, is illegal. Note that the Wired-ANDing of the SCL line can be used to implement handshaking between the Master and the Slave. The Slave can extend the SCL low period by pulling the SCL line low. This is useful if the clock speed set up by the Master is too fast for the

Slave, or the Slave needs extra time for processing between the data transmissions. The Slave extending the SCL low period will not affect the SCL high period, which is determined by the

Master. As a consequence, the Slave can reduce the TWI data transfer speed by prolonging the

SCL duty cycle.

Figure 21-6 on page 213

shows a typical data transmission. Note that several data bytes can be transmitted between the SLA+R/W and the STOP condition, depending on the software protocol implemented by the application software.

Figure 21-6.

Typical data transmission.

Addr MSB Addr LSB R/W ACK Data MSB Data LSB ACK

SDA

SCL

START

1 2 7

SLA+R/W

8

9 1 2

Data Byte

7

8

9

STOP

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21.4

Multi-master Bus Systems, Arbitration and Synchronization

The TWI protocol allows bus systems with several masters. Special concerns have been taken in order to ensure that transmissions will proceed as normal, even if two or more masters initiate a transmission at the same time. Two problems arise in multi-master systems:

• An algorithm must be implemented allowing only one of the masters to complete the transmission. All other masters should cease transmission when they discover that they have lost the selection process. This selection process is called arbitration. When a contending master discovers that it has lost the arbitration process, it should immediately switch to Slave mode to check whether it is being addressed by the winning master. The fact that multiple masters have started transmission at the same time should not be detectable to the slaves, that is the data being transferred on the bus must not be corrupted

• Different masters may use different SCL frequencies. A scheme must be devised to synchronize the serial clocks from all masters, in order to let the transmission proceed in a lockstep fashion. This will facilitate the arbitration process

The wired-ANDing of the bus lines is used to solve both these problems. The serial clocks from all masters will be wired-ANDed, yielding a combined clock with a high period equal to the one from the Master with the shortest high period. The low period of the combined clock is equal to the low period of the Master with the longest low period. Note that all masters listen to the SCL line, effectively starting to count their SCL high and low time-out periods when the combined

SCL line goes high or low, respectively.

Figure 21-7.

SCL synchronization between multiple masters.

TA low

TA high

SCL from

Master A

SCL from

Master B

SCL Bus

Line

TB low

Masters Start

Counting Low Period

TB high

Masters Start

Counting High Period

Arbitration is carried out by all masters continuously monitoring the SDA line after outputting data. If the value read from the SDA line does not match the value the Master had output, it has lost the arbitration. Note that a Master can only lose arbitration when it outputs a high SDA value while another Master outputs a low value. The losing Master should immediately go to Slave mode, checking if it is being addressed by the winning Master. The SDA line should be left high, but losing masters are allowed to generate a clock signal until the end of the current data or address packet. Arbitration will continue until only one Master remains, and this may take many

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bits. If several masters are trying to address the same Slave, arbitration will continue into the data packet.

Figure 21-8.

Arbitration between two masters.

START

SDA from

Master A

Master A Loses

Arbitration, SDA

A

SDA

SDA from

Master B

SDA Line

Synchronized

SCL Line

Note that arbitration is not allowed between:

• A REPEATED START condition and a data bit

• A STOP condition and a data bit

• A REPEATED START and a STOP condition

It is the user software’s responsibility to ensure that these illegal arbitration conditions never occur. This implies that in multi-master systems, all data transfers must use the same composition of SLA+R/W and data packets. In other words: All transmissions must contain the same number of data packets, otherwise the result of the arbitration is undefined.

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21.5

Overview of the TWI Module

The TWI module is comprised of several submodules, as shown in Figure 21-9 . All registers

drawn in a thick line are accessible through the AVR data bus.

Figure 21-9.

Overview of the TWI module.

SCL

Slew-rate

Control

Spike

Filter

SDA

Slew-rate

Control

Spike

Filter

START / STOP

Control

Bus Interface Unit

Spike Suppression

Arbitration detection

Address/Data Shift

Register (TWDR)

Ack

Bit Rate Generator

Prescaler

Bit Rate Register

(TWBR)

Address Match Unit

Address Register

(TWAR)

Address Comparator

Status Register

(TWSR)

Control Unit

Control Register

(TWCR)

State Machine and

Status control

21.5.1

21.5.2

SCL and SDA pins

These pins interface the AVR TWI with the rest of the MCU system. The output drivers contain a slew-rate limiter in order to conform to the TWI specification. The input stages contain a spike suppression unit removing spikes shorter than 50ns. Note that the internal pull-ups in the AVR pads can be enabled by setting the PORT bits corresponding to the SCL and SDA pins, as explained in the I/O Port section. The internal pull-ups can in some systems eliminate the need for external ones.

Bit Rate Generator unit

This unit controls the period of SCL when operating in a Master mode. The SCL period is controlled by settings in the TWI Bit Rate Register (TWBR) and the Prescaler bits in the TWI Status

Register (TWSR). Slave operation does not depend on Bit Rate or Prescaler settings, but the

CPU clock frequency in the Slave must be at least 16 times higher than the SCL frequency. Note that slaves may prolong the SCL low period, thereby reducing the average TWI bus clock period. The SCL frequency is generated according to the following equation:

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21.5.3

21.5.4

21.5.5

SCL frequency

=

CPU Clock frequency

-----------------------------------------------------------

16

+

2(TWBR) 4

• TWBR = Value of the TWI Bit Rate Register

• TWPS = Value of the prescaler bits in the TWI Status Register

Note: Pull-up resistor values should be selected according to the SCL frequency and the capacitive bus

line load. See two-wire Serial Bus Requirements in Table 28-16 on page 339 for value of pull-up

resistor.

Bus Interface unit

This unit contains the Data and Address Shift Register (TWDR), a START/STOP Controller and

Arbitration detection hardware. The TWDR contains the address or data bytes to be transmitted, or the address or data bytes received. In addition to the 8-bit TWDR, the Bus Interface Unit also contains a register containing the (N)ACK bit to be transmitted or received. This (N)ACK Register is not directly accessible by the application software. However, when receiving, it can be set or cleared by manipulating the TWI Control Register (TWCR). When in Transmitter mode, the value of the received (N)ACK bit can be determined by the value in the TWSR.

The START/STOP Controller is responsible for generation and detection of START, REPEATED

START, and STOP conditions. The START/STOP controller is able to detect START and STOP conditions even when the AVR MCU is in one of the sleep modes, enabling the MCU to wake up if addressed by a Master.

If the TWI has initiated a transmission as Master, the Arbitration Detection hardware continuously monitors the transmission trying to determine if arbitration is in process. If the TWI has lost an arbitration, the Control Unit is informed. Correct action can then be taken and appropriate status codes generated.

Address Match unit

The Address Match unit checks if received address bytes match the seven-bit address in the

TWI Address Register (TWAR). If the TWI General Call Recognition Enable (TWGCE) bit in the

TWAR is written to one, all incoming address bits will also be compared against the General Call address. Upon an address match, the Control Unit is informed, allowing correct action to be taken. The TWI may or may not acknowledge its address, depending on settings in the TWCR.

The Address Match unit is able to compare addresses even when the AVR MCU is in sleep mode, enabling the MCU to wake up if addressed by a Master.

Control unit

The Control unit monitors the TWI bus and generates responses corresponding to settings in the

TWI Control Register (TWCR). When an event requiring the attention of the application occurs on the TWI bus, the TWI Interrupt Flag (TWINT) is asserted. In the next clock cycle, the TWI Status Register (TWSR) is updated with a status code identifying the event. The TWSR only contains relevant status information when the TWI Interrupt Flag is asserted. At all other times, the TWSR contains a special status code indicating that no relevant status information is available. As long as the TWINT Flag is set, the SCL line is held low. This allows the application software to complete its tasks before allowing the TWI transmission to continue.

The TWINT Flag is set in the following situations:

• After the TWI has transmitted a START/REPEATED START condition

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21.6

Using the TWI

• After the TWI has transmitted SLA+R/W

• After the TWI has transmitted an address byte

• After the TWI has lost arbitration

• After the TWI has been addressed by own slave address or general call

• After the TWI has received a data byte

• After a STOP or REPEATED START has been received while still addressed as a Slave

• When a bus error has occurred due to an illegal START or STOP condition

The AVR TWI is byte-oriented and interrupt based. Interrupts are issued after all bus events, like reception of a byte or transmission of a START condition. Because the TWI is interrupt-based, the application software is free to carry on other operations during a TWI byte transfer. Note that the TWI Interrupt Enable (TWIE) bit in TWCR together with the Global Interrupt Enable bit in

SREG allow the application to decide whether or not assertion of the TWINT Flag should generate an interrupt request. If the TWIE bit is cleared, the application must poll the TWINT Flag in order to detect actions on the TWI bus.

When the TWINT Flag is asserted, the TWI has finished an operation and awaits application response. In this case, the TWI Status Register (TWSR) contains a value indicating the current state of the TWI bus. The application software can then decide how the TWI should behave in the next TWI bus cycle by manipulating the TWCR and TWDR Registers.

Figure 21-10 is a simple example of how the application can interface to the TWI hardware. In

this example, a Master wishes to transmit a single data byte to a Slave. This description is quite abstract, a more detailed explanation follows later in this section. A simple code example implementing the desired behavior is also presented.

Figure 21-10.

Interfacing the application to the TWI in a typical transmission.

1. Application writes to TWCR to initiate transmission of

START

3. Check TWSR to see if START was sent. Application loads SLA+W into

TWDR, and loads appropriate control signals into TWCR, makin sure that

TWINT is written to one, and TWSTA is written to zero.

5. Check TWSR to see if SLA+W was sent and ACK received.

Application loads data into TWDR, and loads appropriate control signals into

TWCR, making sure that TWINT is written to one

7. Check TWSR to see if data was sent and ACK received.

Application loads appropriate control signals to send STOP into TWCR, making sure that TWINT is written to one

TWI bus START SLA+W A Data A STOP

2. TWINT set.

Status code indicates

START condition sent

4. TWINT set.

Status code indicates

SLA+W sent, ACK received

6. TWINT set.

Status code indicates data sent, ACK received

Indicates

TWINT set

1. The first step in a TWI transmission is to transmit a START condition. This is done by writing a specific value into TWCR, instructing the TWI hardware to transmit a START condition. Which value to write is described later on. However, it is important that the

TWINT bit is set in the value written. Writing a one to TWINT clears the flag. The TWI will

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not start any operation as long as the TWINT bit in TWCR is set. Immediately after the application has cleared TWINT, the TWI will initiate transmission of the START condition.

2. When the START condition has been transmitted, the TWINT Flag in TWCR is set, and

TWSR is updated with a status code indicating that the START condition has successfully been sent.

3. The application software should now examine the value of TWSR, to make sure that the

START condition was successfully transmitted. If TWSR indicates otherwise, the application software might take some special action, like calling an error routine. Assuming that the status code is as expected, the application must load SLA+W into TWDR. Remember that TWDR is used both for address and data. After TWDR has been loaded with the desired SLA+W, a specific value must be written to TWCR, instructing the TWI hardware to transmit the SLA+W present in TWDR. Which value to write is described later on.

However, it is important that the TWINT bit is set in the value written. Writing a one to

TWINT clears the flag. The TWI will not start any operation as long as the TWINT bit in

TWCR is set. Immediately after the application has cleared TWINT, the TWI will initiate transmission of the address packet.

4. When the address packet has been transmitted, the TWINT Flag in TWCR is set, and

TWSR is updated with a status code indicating that the address packet has successfully been sent. The status code will also reflect whether a Slave acknowledged the packet or not.

5. The application software should now examine the value of TWSR, to make sure that the address packet was successfully transmitted, and that the value of the ACK bit was as expected. If TWSR indicates otherwise, the application software might take some special action, like calling an error routine. Assuming that the status code is as expected, the application must load a data packet into TWDR. Subsequently, a specific value must be written to TWCR, instructing the TWI hardware to transmit the data packet present in

TWDR. Which value to write is described later on. However, it is important that the

TWINT bit is set in the value written. Writing a one to TWINT clears the flag. The TWI will not start any operation as long as the TWINT bit in TWCR is set. Immediately after the application has cleared TWINT, the TWI will initiate transmission of the data packet.

6. When the data packet has been transmitted, the TWINT Flag in TWCR is set, and TWSR is updated with a status code indicating that the data packet has successfully been sent.

The status code will also reflect whether a Slave acknowledged the packet or not.

7. The application software should now examine the value of TWSR, to make sure that the data packet was successfully transmitted, and that the value of the ACK bit was as expected. If TWSR indicates otherwise, the application software might take some special action, like calling an error routine. Assuming that the status code is as expected, the application must write a specific value to TWCR, instructing the TWI hardware to transmit a STOP condition. Which value to write is described later on. However, it is important that the TWINT bit is set in the value written. Writing a one to TWINT clears the flag. The TWI will not start any operation as long as the TWINT bit in TWCR is set. Immediately after the application has cleared TWINT, the TWI will initiate transmission of the STOP condition. Note that TWINT is NOT set after a STOP condition has been sent.

Even though this example is simple, it shows the principles involved in all TWI transmissions.

These can be summarized as follows:

• When the TWI has finished an operation and expects application response, the TWINT Flag is set. The SCL line is pulled low until TWINT is cleared

• When the TWINT Flag is set, the user must update all TWI Registers with the value relevant for the next TWI bus cycle. As an example, TWDR must be loaded with the value to be transmitted in the next bus cycle

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• After all TWI Register updates and other pending application software tasks have been completed, TWCR is written. When writing TWCR, the TWINT bit should be set. Writing a one to TWINT clears the flag. The TWI will then commence executing whatever operation was specified by the TWCR setting

In the following an assembly and C implementation of the example is given. Note that the code below assumes that several definitions have been made, for example by using include-files.

1

2

3

4

5

6

7

Assembly code example ldi

r16, (1<<TWINT)|(1<<TWSTA)|

(1<<TWEN)

out

TWCR, r16 wait1:

in

r16,TWCR

sbrs

r16,TWINT

rjmp

wait1

in

r16,TWSR

andi

r16, 0xF8

cpi

r16, START

brne

ERROR

ldi

r16, SLA_W

out

TWDR, r16

ldi

r16, (1<<TWINT) | (1<<TWEN)

out

TWCR, r16 wait2:

in

r16,TWCR

sbrs

r16,TWINT

rjmp

wait2

in

r16,TWSR

andi

r16, 0xF8

cpi

r16, MT_SLA_ACK

brne

ERROR

ldi

r16, DATA

out

TWDR, r16

ldi

r16, (1<<TWINT) | (1<<TWEN)

out

TWCR, r16 wait3:

in

r16,TWCR

sbrs

r16,TWINT

rjmp

wait3

in

r16,TWSR

andi

r16, 0xF8

cpi

r16, MT_DATA_ACK

brne

ERROR

ldi

r16, (1<<TWINT)|(1<<TWEN)|

(1<<TWSTO)

out

TWCR, r16

C example

TWCR = (1<<TWINT)|(1<<TWSTA)|

(1<<TWEN)

while if

TWDR = SLA_W;

TWCR = (1<<TWINT) | (1<<TWEN);

while if

((TWSR & 0xF8) !=

MT_SLA_ACK)

ERROR();

TWDR = DATA;

TWCR = (1<<TWINT) | (1<<TWEN);

while if

(!(TWCR & (1<<TWINT)))

;

((TWSR & 0xF8) != START)

ERROR();

(!(TWCR & (1<<TWINT)))

;

(!(TWCR & (1<<TWINT)))

;

((TWSR & 0xF8) !=

MT_DATA_ACK)

ERROR();

TWCR = (1<<TWINT)|(1<<TWEN)|

(1<<TWSTO);

Comments

Send START condition

Wait for TWINT Flag set. This indicates that the START condition has been transmitted

Check value of TWI Status

Register. Mask prescaler bits. If status different from START go to

ERROR

Load SLA_W into TWDR Register.

Clear TWINT bit in TWCR to start transmission of address

Wait for TWINT Flag set. This indicates that the SLA+W has been transmitted, and ACK/NACK has been received.

Check value of TWI Status

Register. Mask prescaler bits. If status different from MT_SLA_ACK go to ERROR

Load DATA into TWDR Register.

Clear TWINT bit in TWCR to start transmission of data

Wait for TWINT Flag set. This indicates that the DATA has been transmitted, and ACK/NACK has been received.

Check value of TWI Status

Register. Mask prescaler bits. If status different from

MT_DATA_ACK go to ERROR

Transmit STOP condition

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21.7

Transmission modes

21.7.1

The TWI can operate in one of four major modes. These are named Master Transmitter (MT),

Master Receiver (MR), Slave Transmitter (ST) and Slave Receiver (SR). Several of these modes can be used in the same application. As an example, the TWI can use MT mode to write data into a TWI EEPROM, MR mode to read the data back from the EEPROM. If other masters are present in the system, some of these might transmit data to the TWI, and then SR mode would be used. It is the application software that decides which modes are legal.

The following sections describe each of these modes. Possible status codes are described along with figures detailing data transmission in each of the modes. These figures contain the following abbreviations:

S

: START condition

Rs

: REPEATED START condition

R

: Read bit (high level at SDA)

W

: Write bit (low level at SDA)

A

: Acknowledge bit (low level at SDA)

A

: Not acknowledge bit (high level at SDA)

Data

: 8-bit data byte

P

: STOP condition

SLA

: Slave Address

In

Figure 21-12 on page 224

to

Figure 21-18 on page 233

, circles are used to indicate that the

TWINT Flag is set. The numbers in the circles show the status code held in TWSR, with the prescaler bits masked to zero. At these points, actions must be taken by the application to continue or complete the TWI transfer. The TWI transfer is suspended until the TWINT Flag is cleared by software.

When the TWINT Flag is set, the status code in TWSR is used to determine the appropriate software action. For each status code, the required software action and details of the following serial transfer are given in

Table 21-2 on page 223

to Table 21-5 on page 232

. Note that the prescaler bits are masked to zero in these tables.

Master Transmitter mode

In the Master Transmitter mode, a number of data bytes are transmitted to a Slave Receiver

(see

Figure 21-11 on page 222

). In order to enter a Master mode, a START condition must be transmitted. The format of the following address packet determines whether Master Transmitter or Master Receiver mode is to be entered. If SLA+W is transmitted, MT mode is entered, if

SLA+R is transmitted, MR mode is entered. All the status codes mentioned in this section assume that the prescaler bits are zero or are masked to zero.

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Figure 21-11.

Data transfer in Master Transmitter mode.

V

CC

Device 1

MASTER

TRANSMITTER

Device 2

SLAVE

RECEIVER

Device 3

........

Device n R1 R2

SDA

SCL

A START condition is sent by writing the following value to TWCR:

TWCR

value

TWINT

1

TWEA

X

TWSTA

1

TWSTO

0

TWWC

X

TWEN

1

0

TWIE

X

TWEN must be set to enable the two-wire Serial Interface, TWSTA must be written to one to transmit a START condition and TWINT must be written to one to clear the TWINT Flag. The

TWI will then test the two-wire Serial Bus and generate a START condition as soon as the bus becomes free. After a START condition has been transmitted, the TWINT Flag is set by hardware, and the status code in TWSR will be 0x08 (see

Table 21-2 on page 223

). In order to enter

MT mode, SLA+W must be transmitted. This is done by writing SLA+W to TWDR. Thereafter the

TWINT bit should be cleared (by writing it to one) to continue the transfer. This is accomplished by writing the following value to TWCR:

TWCR

value

TWINT

1

TWEA

X

TWSTA

0

TWSTO

0

TWWC

X

TWEN

1

0

TWIE

X

When SLA+W have been transmitted and an acknowledgement bit has been received, TWINT is set again and a number of status codes in TWSR are possible. Possible status codes in Master mode are 0x18, 0x20, or 0x38. The appropriate action to be taken for each of these status codes

is detailed in Table 21-2 on page 223

.

When SLA+W has been successfully transmitted, a data packet should be transmitted. This is done by writing the data byte to TWDR. TWDR must only be written when TWINT is high. If not, the access will be discarded, and the Write Collision bit (TWWC) will be set in the TWCR Register. After updating TWDR, the TWINT bit should be cleared (by writing it to one) to continue the transfer. This is accomplished by writing the following value to TWCR:

TWCR

value

TWINT

1

TWEA

X

TWSTA

0

TWSTO

0

TWWC

X

TWEN

1

0

TWIE

X

This scheme is repeated until the last byte has been sent and the transfer is ended by generating a STOP condition or a repeated START condition. A STOP condition is generated by writing the following value to TWCR:

TWCR

value

TWINT

1

TWEA

X

TWSTA

0

TWSTO

1

TWWC

X

TWEN

1

0

TWIE

X

A REPEATED START condition is generated by writing the following value to TWCR:

TWCR

value

TWINT

1

TWEA

X

TWSTA

1

TWSTO

0

TWWC

X

TWEN

1

0

TWIE

X

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After a repeated START condition (state 0x10) the two-wire Serial Interface can access the same Slave again, or a new Slave without transmitting a STOP condition. Repeated START enables the Master to switch between Slaves, Master Transmitter mode and Master Receiver mode without losing control of the bus.

Table 21-2.

Status codes for Master Transmitter mode.

Status Code

(TWSR)

Prescaler Bits are 0

0x08

0x10

Status of the two-wire Serial Bus and two-wire Serial Interface

Hardware

A START condition has been transmitted

A repeated START condition has been transmitted

To/from TWDR

Application Software Response

STA

To TWCR

STO TWINT TWEA

Load SLA+W

Load SLA+W or

0

0

0

0

1

1

X

X

Load SLA+R 0 0 1 X

0x18

0x20

0x28

0x30

0x38

SLA+W has been transmitted;

ACK has been received

SLA+W has been transmitted;

NOT ACK has been received

Load data byte or

No TWDR action or

No TWDR action or

No TWDR action

Load data byte or

No TWDR action or

No TWDR action or

No TWDR action

Data byte has been transmitted;

ACK has been received

Load data byte or

No TWDR action or

No TWDR action or

No TWDR action

Data byte has been transmitted;

NOT ACK has been received

Load data byte or

No TWDR action or

No TWDR action or

No TWDR action

Arbitration lost in SLA+W or data bytes

No TWDR action or

No TWDR action

0

1

0

1

0

1

0

1

0

1

0

1

0

1

0

1

0

1

0

0

1

1

0

0

1

1

0

0

1

1

0

0

1

1

0

0

1

1

1

1

1

1

1

1

1

1

1

1

1

1

1

1

1

1

X

X

X

X

X

X

X

X

X

X

X

X

X

X

X

X

X

X

Next Action Taken by TWI Hardware

SLA+W will be transmitted;

ACK or NOT ACK will be received

SLA+W will be transmitted;

ACK or NOT ACK will be received

SLA+R will be transmitted;

Logic will switch to Master Receiver mode

Data byte will be transmitted and ACK or NOT ACK will be received

Repeated START will be transmitted

STOP condition will be transmitted and

TWSTO Flag will be reset

STOP condition followed by a START condition will be transmitted and TWSTO Flag will be reset

Data byte will be transmitted and ACK or NOT ACK will be received

Repeated START will be transmitted

STOP condition will be transmitted and

TWSTO Flag will be reset

STOP condition followed by a START condition will be transmitted and TWSTO Flag will be reset

Data byte will be transmitted and ACK or NOT ACK will be received

Repeated START will be transmitted

STOP condition will be transmitted and

TWSTO Flag will be reset

STOP condition followed by a START condition will be transmitted and TWSTO Flag will be reset

Data byte will be transmitted and ACK or NOT ACK will be received

Repeated START will be transmitted

STOP condition will be transmitted and

TWSTO Flag will be reset

STOP condition followed by a START condition will be transmitted and TWSTO Flag will be reset two-wire Serial Bus will be released and not addressed

Slave mode entered

A START condition will be transmitted when the bus becomes free

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Figure 21-12.

Formats and states in the Master Transmitter mode.

MT

Successfull transmission to a slave receiver

S

$08

Next transfer started with a repeated start condition

SLA

Not acknowledge received after the slave address

W A

$18

A

$20

P

DATA A

$28

P

R

S

$10

SLA

Not acknowledge received after a data byte

Arbitration lost in slave address or data byte

Arbitration lost and addressed as slave

A or A

Other master continues

$38

A

Other master continues

$68 $78 $B0

A P

$30

A or A

Other master continues

$38

To corresponding states in slave mode

W

R

MR

21.7.2

From master to slave

DATA A

Any number of data bytes and their associated acknowledge bits

From slave to master n

This number (contained in TWSR) corresponds to a defined state of the Two-Wire Serial Bus. The prescaler bits are zero or masked to zero

Master Receiver mode

In the Master Receiver mode, a number of data bytes are received from a Slave Transmitter

(Slave see

Figure 21-13 on page 225

). In order to enter a Master mode, a START condition must be transmitted. The format of the following address packet determines whether Master

Transmitter or Master Receiver mode is to be entered. If SLA+W is transmitted, MT mode is entered, if SLA+R is transmitted, MR mode is entered. All the status codes mentioned in this section assume that the prescaler bits are zero or are masked to zero.

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Figure 21-13.

Data transfer in Master Receiver mode.

V

CC

Device 1

MASTER

RECEIVER

Device 2

SLAVE

TRANSMITTER

Device 3

........

Device n R1 R2

SDA

SCL

A START condition is sent by writing the following value to TWCR:

TWCR

value

TWINT

1

TWEA

X

TWSTA

1

TWSTO

0

TWWC

X

TWEN

1

0

TWIE

X

TWEN must be written to one to enable the two-wire Serial Interface, TWSTA must be written to one to transmit a START condition and TWINT must be set to clear the TWINT Flag. The TWI will then test the two-wire Serial Bus and generate a START condition as soon as the bus becomes free. After a START condition has been transmitted, the TWINT Flag is set by hardware, and the status code in TWSR will be 0x08 (See

Table 21-2 on page 223 ). In order to enter

MR mode, SLA+R must be transmitted. This is done by writing SLA+R to TWDR. Thereafter the

TWINT bit should be cleared (by writing it to one) to continue the transfer. This is accomplished by writing the following value to TWCR:

TWCR

value

TWINT

1

TWEA

X

TWSTA

0

TWSTO

0

TWWC

X

TWEN

1

0

TWIE

X

When SLA+R have been transmitted and an acknowledgement bit has been received, TWINT is set again and a number of status codes in TWSR are possible. Possible status codes in Master mode are 0x38, 0x40, or 0x48. The appropriate action to be taken for each of these status codes is detailed in

Table 21-3 on page 226 . Received data can be read from the TWDR Register

when the TWINT Flag is set high by hardware. This scheme is repeated until the last byte has been received. After the last byte has been received, the MR should inform the ST by sending a

NACK after the last received data byte. The transfer is ended by generating a STOP condition or a repeated START condition. A STOP condition is generated by writing the following value to

TWCR:

TWCR

value

TWINT

1

TWEA

X

TWSTA

0

TWSTO

1

TWWC

X

TWEN

1

0

TWIE

X

A REPEATED START condition is generated by writing the following value to TWCR:

TWCR

value

TWINT

1

TWEA

X

TWSTA

1

TWSTO

0

TWWC

X

TWEN

1

0

TWIE

X

After a repeated START condition (state 0x10) the two-wire Serial Interface can access the same Slave again, or a new Slave without transmitting a STOP condition. Repeated START

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enables the Master to switch between Slaves, Master Transmitter mode and Master Receiver mode without losing control over the bus.

Table 21-3.

Status codes for Master Receiver mode.

Status Code

(TWSR)

Prescaler Bits are 0

0x08

0x10

Status of the two-wire Serial Bus and two-wire Serial Interface

Hardware

A START condition has been transmitted

A repeated START condition has been transmitted

To/from TWDR

Application Software Response

STA

To TWCR

STO TWINT TWEA

Load SLA+R

Load SLA+R or

0

0

0

0

1

1

X

X

Load SLA+W 0 0 1 X

0x38

0x40

Arbitration lost in SLA+R or NOT

ACK bit

No TWDR action or

No TWDR action

SLA+R has been transmitted;

ACK has been received

No TWDR action or

No TWDR action

0

0

0

1

0

0

0

0

1

1

1

1

0

1

X

X

Next Action Taken by TWI Hardware

SLA+R will be transmitted

ACK or NOT ACK will be received

SLA+R will be transmitted

ACK or NOT ACK will be received

SLA+W will be transmitted

Logic will switch to Master Transmitter mode two-wire Serial Bus will be released and not addressed

Slave mode will be entered

A START condition will be transmitted when the bus becomes free

Data byte will be received and NOT ACK will be returned

Data byte will be received and ACK will be returned

0x48

0x50

0x58

SLA+R has been transmitted;

NOT ACK has been received

Data byte has been received;

ACK has been returned

Data byte has been received;

NOT ACK has been returned

No TWDR action or

No TWDR action or

No TWDR action

Read data byte or

Read data byte

Read data byte or

Read data byte or

Read data byte

0

0

1

0

1

1

0

1

0

0

0

1

1

0

1

1

1

1

1

1

1

1

1

1

0

1

X

X

X

X

X

X

Repeated START will be transmitted

STOP condition will be transmitted and TWSTO Flag will be reset

STOP condition followed by a START condition will be transmitted and TWSTO Flag will be reset

Data byte will be received and NOT ACK will be returned

Data byte will be received and ACK will be returned

Repeated START will be transmitted

STOP condition will be transmitted and TWSTO Flag will be reset

STOP condition followed by a START condition will be transmitted and TWSTO Flag will be reset

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Figure 21-14.

Formats and states in the Master Receiver mode.

MR

Successfull reception from a slave receiver

S

$08

Next transfer started with a repeated start condition

SLA

Not acknowledge received after the slave address

R A

$40

DATA A DATA A

$50 $58

P

R

S

$10

SLA

Arbitration lost in slave address or data byte

Arbitration lost and addressed as slave

A P

$48

A or A

Other master continues

$38

A

Other master continues

$68 $78 $B0

A

Other master continues

$38

To corresponding states in slave mode

R

W

MT

From master to slave

From slave to master

DATA n

A

Any number of data bytes and their associated acknowledge bits

This number (contained in TWSR) corresponds to a defined state of the Two-Wire Serial Bus. The prescaler bits are zero or masked to zero

21.7.3

Slave Receiver mode

In the Slave Receiver mode, a number of data bytes are received from a Master Transmitter

(see

Figure 21-15 ). All the status codes mentioned in this section assume that the prescaler bits

are zero or are masked to zero.

Figure 21-15.

Data transfer in Slave Receiver mode.

V

CC

Device 1

SLAVE

RECEIVER

Device 2

MASTER

TRANSMITTER

Device 3 ........

Device n R1 R2

SDA

SCL

To initiate the Slave Receiver mode, TWAR and TWCR must be initialized as follows:

TWAR

value

TWA6 TWA5 TWA4 TWA3 TWA2

Device’s Own Slave Address

TWA1 TWA0 TWGCE

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The upper seven bits are the address to which the two-wire Serial Interface will respond when addressed by a Master. If the LSB is set, the TWI will respond to the general call address (0x00), otherwise it will ignore the general call address.

TWCR

value

TWINT

0

TWEA

1

TWSTA

0

TWSTO

0

TWWC

0

TWEN

1

0

TWIE

X

TWEN must be written to one to enable the TWI. The TWEA bit must be written to one to enable the acknowledgement of the device’s own slave address or the general call address. TWSTA and TWSTO must be written to zero.

When TWAR and TWCR have been initialized, the TWI waits until it is addressed by its own slave address (or the general call address if enabled) followed by the data direction bit. If the direction bit is “0” (write), the TWI will operate in SR mode, otherwise ST mode is entered. After its own slave address and the write bit have been received, the TWINT Flag is set and a valid status code can be read from TWSR. The status code is used to determine the appropriate software action. The appropriate action to be taken for each status code is detailed in

Table 21-4 on page 229

. The Slave Receiver mode may also be entered if arbitration is lost while the TWI is in the Master mode (see states 0x68 and 0x78).

If the TWEA bit is reset during a transfer, the TWI will return a “Not Acknowledge” (“1”) to SDA after the next received data byte. This can be used to indicate that the Slave is not able to receive any more bytes. While TWEA is zero, the TWI does not acknowledge its own slave address. However, the two-wire Serial Bus is still monitored and address recognition may resume at any time by setting TWEA. This implies that the TWEA bit may be used to temporarily isolate the TWI from the two-wire Serial Bus.

In all sleep modes other than Idle mode, the clock system to the TWI is turned off. If the TWEA bit is set, the interface can still acknowledge its own slave address or the general call address by using the two-wire Serial Bus clock as a clock source. The part will then wake up from sleep and the TWI will hold the SCL clock low during the wake up and until the TWINT Flag is cleared (by writing it to one). Further data reception will be carried out as normal, with the AVR clocks running as normal. Observe that if the AVR is set up with a long start-up time, the SCL line may be held low for a long time, blocking other data transmissions.

Note that the two-wire Serial Interface Data Register – TWDR does not reflect the last byte present on the bus when waking up from these Sleep modes.

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Table 21-4.

Status codes for Slave Receiver mode.

Status Code

(TWSR)

Prescaler Bits are 0

0x60

Status of the two-wire Serial Bus and two-wire Serial Interface Hardware

Own SLA+W has been received;

ACK has been returned

Application Software Response

To TWCR

To/from TWDR

STA STO TWINT TWEA

No TWDR action or X 0 1 0

0x68

No TWDR action

No TWDR action or

X

X

0

0

1

1

1

0

0x70

Arbitration lost in SLA+R/W as

Master; own SLA+W has been received; ACK has been returned

General call address has been received; ACK has been returned

No TWDR action

No TWDR action or

X

X

0

0

1

1

1

0

0x78

No TWDR action

No TWDR action or

X

X

0

0

1

1

1

0

0x80

0x88

Arbitration lost in SLA+R/W as

Master; General call address has been received; ACK has been returned

Previously addressed with own

SLA+W; data has been received;

ACK has been returned

Previously addressed with own

SLA+W; data has been received;

NOT ACK has been returned

No TWDR action

Read data byte or

Read data byte

Read data byte or

Read data byte or

X

X

X

0

0

0

0

0

0

0

1

1

1

1

1

1

0

1

0

1

0x90

0x98

0xA0

Read data byte or

Read data byte

Previously addressed with general call; data has been received; ACK has been returned

Previously addressed with general call; data has been received; NOT ACK has been returned

Read data byte or

Read data byte

Read data byte or

Read data byte or

Read data byte or

Read data byte

A STOP condition or repeated

START condition has been received while still addressed as

Slave

No action

1

1

X

X

0

0

1

1

0

0

1

1

0

0

0

0

0

0

0

0

0

0

0

0

1

1

1

1

1

1

1

1

1

1

1

1

0

1

0

1

0

1

0

1

0

1

0

1

Next Action Taken by TWI Hardware

Data byte will be received and NOT ACK will be returned

Data byte will be received and ACK will be returned

Data byte will be received and NOT ACK will be returned

Data byte will be received and ACK will be returned

Data byte will be received and NOT ACK will be returned

Data byte will be received and ACK will be returned

Data byte will be received and NOT ACK will be returned

Data byte will be received and ACK will be returned

Data byte will be received and NOT ACK will be returned

Data byte will be received and ACK will be returned

Switched to the not addressed Slave mode; no recognition of own SLA or GCA

Switched to the not addressed Slave mode; own SLA will be recognized;

GCA will be recognized if TWGCE = “1”

Switched to the not addressed Slave mode; no recognition of own SLA or GCA; a START condition will be transmitted when the bus becomes free

Switched to the not addressed Slave mode; own SLA will be recognized;

GCA will be recognized if TWGCE = “1”; a START condition will be transmitted when the bus becomes free

Data byte will be received and NOT ACK will be returned

Data byte will be received and ACK will be returned

Switched to the not addressed Slave mode; no recognition of own SLA or GCA

Switched to the not addressed Slave mode; own SLA will be recognized;

GCA will be recognized if TWGCE = “1”

Switched to the not addressed Slave mode; no recognition of own SLA or GCA; a START condition will be transmitted when the bus becomes free

Switched to the not addressed Slave mode; own SLA will be recognized;

GCA will be recognized if TWGCE = “1”; a START condition will be transmitted when the bus becomes free

Switched to the not addressed Slave mode; no recognition of own SLA or GCA

Switched to the not addressed Slave mode; own SLA will be recognized;

GCA will be recognized if TWGCE = “1”

Switched to the not addressed Slave mode; no recognition of own SLA or GCA; a START condition will be transmitted when the bus becomes free

Switched to the not addressed Slave mode; own SLA will be recognized;

GCA will be recognized if TWGCE = “1”; a START condition will be transmitted when the bus becomes free

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Figure 21-16.

Formats and states in the Slave Receiver mode.

Reception of the own slave address and one or more data bytes. All are acknowledged

S SLA W A DATA A

$60 $80

Last data byte received is not acknowledged

DATA A

$80

A

P or S

$A0

P or S

$88

Arbitration lost as master and addressed as slave

A

Reception of the general call address and one or more data bytes

General Call

$68

A DATA A DATA A P or S

Last data byte received is not acknowledged

$70 $90 $90

A

$A0

P or S

$98

Arbitration lost as master and addressed as slave by general call

A

$78

From master to slave

From slave to master

DATA n

A

Any number of data bytes and their associated acknowledge bits

This number (contained in TWSR) corresponds to a defined state of the Two-Wire Serial Bus. The prescaler bits are zero or masked to zero

21.7.4

Slave Transmitter mode

In the Slave Transmitter mode, a number of data bytes are transmitted to a Master Receiver

(see

Figure 21-17 ). All the status codes mentioned in this section assume that the prescaler bits

are zero or are masked to zero.

Figure 21-17.

Data transfer in Slave Transmitter mode.

V

CC

Device 1

SLAVE

TRANSMITTER

Device 2

MASTER

RECEIVER

Device 3

........

Device n R1 R2

SDA

SCL

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To initiate the Slave Transmitter mode, TWAR and TWCR must be initialized as follows:

TWAR

value

TWA6 TWA5 TWA4 TWA3 TWA2

Device’s Own Slave Address

TWA1 TWA0 TWGCE

The upper seven bits are the address to which the two-wire Serial Interface will respond when addressed by a Master. If the LSB is set, the TWI will respond to the general call address (0x00), otherwise it will ignore the general call address.

TWCR

value

TWINT

0

TWEA

1

TWSTA

0

TWSTO

0

TWWC

0

TWEN

1

0

TWIE

X

TWEN must be written to one to enable the TWI. The TWEA bit must be written to one to enable the acknowledgement of the device’s own slave address or the general call address. TWSTA and TWSTO must be written to zero.

When TWAR and TWCR have been initialized, the TWI waits until it is addressed by its own slave address (or the general call address if enabled) followed by the data direction bit. If the direction bit is “1” (read), the TWI will operate in ST mode, otherwise SR mode is entered. After its own slave address and the write bit have been received, the TWINT Flag is set and a valid status code can be read from TWSR. The status code is used to determine the appropriate software action. The appropriate action to be taken for each status code is detailed in

Table 21-5 on page 232 . The Slave Transmitter mode may also be entered if arbitration is lost while the TWI is

in the Master mode (see state 0xB0).

If the TWEA bit is written to zero during a transfer, the TWI will transmit the last byte of the transfer. State 0xC0 or state 0xC8 will be entered, depending on whether the Master Receiver transmits a NACK or ACK after the final byte. The TWI is switched to the not addressed Slave mode, and will ignore the Master if it continues the transfer. Thus the Master Receiver receives all “1” as serial data. State 0xC8 is entered if the Master demands additional data bytes (by transmitting ACK), even though the Slave has transmitted the last byte (TWEA zero and expecting NACK from the Master).

While TWEA is zero, the TWI does not respond to its own slave address. However, the two-wire

Serial Bus is still monitored and address recognition may resume at any time by setting TWEA.

This implies that the TWEA bit may be used to temporarily isolate the TWI from the two-wire

Serial Bus.

In all sleep modes other than Idle mode, the clock system to the TWI is turned off. If the TWEA bit is set, the interface can still acknowledge its own slave address or the general call address by using the two-wire Serial Bus clock as a clock source. The part will then wake up from sleep and the TWI will hold the SCL clock will low during the wake up and until the TWINT Flag is cleared

(by writing it to one). Further data transmission will be carried out as normal, with the AVR clocks running as normal. Observe that if the AVR is set up with a long start-up time, the SCL line may be held low for a long time, blocking other data transmissions.

Note that the two-wire Serial Interface Data Register – TWDR does not reflect the last byte present on the bus when waking up from these sleep modes.

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Table 21-5.

Status codes for Slave Transmitter mode.

Status Code

(TWSR)

Prescaler Bits are 0

0xA8

Status of the two-wire Serial Bus and two-wire Serial Interface Hardware

Own SLA+R has been received;

ACK has been returned

Application Software Response

To TWCR

To/from TWDR

STA STO TWINT TWEA

Load data byte or X 0 1 0

Load data byte X 0 1 1

0xB0

0xB8

0xC0

0xC8

Arbitration lost in SLA+R/W as

Master; own SLA+R has been received; ACK has been returned

Load data byte or

Load data byte

Data byte in TWDR has been transmitted; ACK has been received

Data byte in TWDR has been transmitted; NOT ACK has been received

Load data byte or

Load data byte

No TWDR action or

No TWDR action or

No TWDR action or

No TWDR action

Last data byte in TWDR has been transmitted (TWEA = “0”); ACK has been received

No TWDR action or

No TWDR action or

No TWDR action or

No TWDR action

0

0

X

X

X

X

1

1

0

0

1

1

0

0

0

0

0

0

0

0

0

0

0

0

1

1

1

1

1

1

1

1

1

1

1

1

0

1

0

1

0

1

0

1

0

1

0

1

Next Action Taken by TWI Hardware

Last data byte will be transmitted and NOT ACK should be received

Data byte will be transmitted and ACK should be received

Last data byte will be transmitted and NOT ACK should be received

Data byte will be transmitted and ACK should be received

Last data byte will be transmitted and NOT ACK should be received

Data byte will be transmitted and ACK should be received

Switched to the not addressed Slave mode; no recognition of own SLA or GCA

Switched to the not addressed Slave mode; own SLA will be recognized;

GCA will be recognized if TWGCE = “1”

Switched to the not addressed Slave mode; no recognition of own SLA or GCA; a START condition will be transmitted when the bus becomes free

Switched to the not addressed Slave mode; own SLA will be recognized;

GCA will be recognized if TWGCE = “1”; a START condition will be transmitted when the bus becomes free

Switched to the not addressed Slave mode; no recognition of own SLA or GCA

Switched to the not addressed Slave mode; own SLA will be recognized;

GCA will be recognized if TWGCE = “1”

Switched to the not addressed Slave mode; no recognition of own SLA or GCA; a START condition will be transmitted when the bus becomes free

Switched to the not addressed Slave mode; own SLA will be recognized;

GCA will be recognized if TWGCE = “1”; a START condition will be transmitted when the bus becomes free

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Figure 21-18.

Formats and states in the Slave Transmitter mode.

Reception of the own slave address and one or more data bytes

S SLA R A DATA A DATA

$A8 $B8

Arbitration lost as master and addressed as slave

A

A

$C0

P or S

$B0

Last data byte transmitted.

Switched to not addressed slave (TWEA = '0')

A All 1's P or S

$C8

21.7.5

From master to slave

From slave to master

DATA n

A

Any number of data bytes and their associated acknowledge bits

This number (contained in TWSR) corresponds to a defined state of the Two-Wire Serial Bus. The prescaler bits are zero or masked to zero

Miscellaneous States

There are two status codes that do not correspond to a defined TWI state, see Table 21-6 .

Status 0xF8 indicates that no relevant information is available because the TWINT Flag is not set. This occurs between other states, and when the TWI is not involved in a serial transfer.

Status 0x00 indicates that a bus error has occurred during a two-wire Serial Bus transfer. A bus error occurs when a START or STOP condition occurs at an illegal position in the format frame.

Examples of such illegal positions are during the serial transfer of an address byte, a data byte, or an acknowledge bit. When a bus error occurs, TWINT is set. To recover from a bus error, the

TWSTO Flag must set and TWINT must be cleared by writing a logic one to it. This causes the

TWI to enter the not addressed Slave mode and to clear the TWSTO Flag (no other bits in

TWCR are affected). The SDA and SCL lines are released, and no STOP condition is transmitted.

Table 21-6.

Miscellaneous states.

Status Code

(TWSR)

Prescaler Bits are 0

0xF8

0x00

Status of the two-wire Serial Bus and two-wire Serial Interface

Hardware

No relevant state information available; TWINT = “0”

Bus error due to an illegal

START or STOP condition

To/from TWDR

Application Software Response

To TWCR

STA STO TWINT TWEA

No TWDR action No TWCR action

No TWDR action 0 1 1 X

Next Action Taken by TWI Hardware

Wait or proceed current transfer

Only the internal hardware is affected, no STOP condition is sent on the bus. In all cases, the bus is released and TWSTO is cleared.

21.7.6

Combining several TWI modes

In some cases, several TWI modes must be combined in order to complete the desired action.

Consider for example reading data from a serial EEPROM. Typically, such a transfer involves the following steps:

1. The transfer must be initiated.

2. The EEPROM must be instructed what location should be read.

3. The reading must be performed.

4. The transfer must be finished.

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Note that data is transmitted both from Master to Slave and vice versa. The Master must instruct the Slave what location it wants to read, requiring the use of the MT mode. Subsequently, data must be read from the Slave, implying the use of the MR mode. Thus, the transfer direction must be changed. The Master must keep control of the bus during all these steps, and the steps should be carried out as an atomical operation. If this principle is violated in a multimaster system, another Master can alter the data pointer in the EEPROM between steps 2 and 3, and the

Master will read the wrong data location. Such a change in transfer direction is accomplished by transmitting a REPEATED START between the transmission of the address byte and reception of the data. After a REPEATED START, the Master keeps ownership of the bus. The following figure shows the flow in this transfer.

Figure 21-19.

Combining several TWI modes to access a serial EEPROM.

Master Transmitter Master Receiver

S SLA+W A ADDRESS

S = START

Transmitted from master to slave

A Rs SLA+R A

Rs = REPEATED START

Transmitted from slave to master

DATA A P

P = STOP

21.8

Multi-master Systems and Arbitration

If multiple masters are connected to the same bus, transmissions may be initiated simultaneously by one or more of them. The TWI standard ensures that such situations are handled in such a way that one of the masters will be allowed to proceed with the transfer, and that no data will be lost in the process. An example of an arbitration situation is depicted below, where two masters are trying to transmit data to a Slave Receiver.

Figure 21-20.

An Arbitration example.

V

CC

Device 1

MASTER

TRANSMITTER

Device 2

MASTER

TRANSMITTER

Device 3

SLAVE

RECEIVER

........

Device n R1 R2

SDA

SCL

Several different scenarios may arise during arbitration, as described below:

• Two or more masters are performing identical communication with the same Slave. In this case, neither the Slave nor any of the masters will know about the bus contention

• Two or more masters are accessing the same Slave with different data or direction bit. In this case, arbitration will occur, either in the READ/WRITE bit or in the data bits. The masters trying to output a one on SDA while another Master outputs a zero will lose the arbitration. Losing masters will switch to not addressed Slave mode or wait until the bus is free and transmit a new

START condition, depending on application software action

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• Two or more masters are accessing different slaves. In this case, arbitration will occur in the

SLA bits. Masters trying to output a one on SDA while another Master outputs a zero will lose the arbitration. Masters losing arbitration in SLA will switch to Slave mode to check if they are being addressed by the winning Master. If addressed, they will switch to SR or ST mode, depending on the value of the READ/WRITE bit. If they are not being addressed, they will switch to not addressed Slave mode or wait until the bus is free and transmit a new START condition, depending on application software action

This is summarized in

Figure 21-21 . Possible status values are given in circles.

Figure 21-21.

Possible status codes caused by Arbitration.

START SLA Data STOP

Arbitration lost in SLA Arbitration lost in Data

Own

Address / General Call received

Yes

No

Direction

Write

Read

38

TWI bus will be released and not addressed slave mode will be entered

A START condition will be transmitted when the bus becomes free

68/78

Data byte will be received and NOT ACK will be returned

Data byte will be received and ACK will be returned

B0

Last data byte will be transmitted and NOT ACK should be received

Data byte will be transmitted and ACK should be received

21.9

Register description

21.9.1

TWBR – TWI Bit Rate Register

21.9.2

Bit

(0xB8)

Read/Write

Initial Value

7

TWBR7

R/W

0

6

TWBR6

R/W

0

5

TWBR5

R/W

0

4

TWBR4

R/W

0

3

TWBR3

R/W

0

2

TWBR2

R/W

0

1

TWBR1

R/W

0

0

TWBR0

R/W

0

TWBR

• Bits 7:0 – TWI Bit Rate Register

TWBR selects the division factor for the bit rate generator. The bit rate generator is a frequency divider which generates the SCL clock frequency in the Master modes. See

”Bit Rate Generator unit” on page 216

for calculating bit rates.

TWCR – TWI Control Register

Bit

(0xBC)

Read/Write

Initial Value

7

TWINT

R/W

0

6

TWEA

R/W

0

5

TWSTA

R/W

0

4

TWSTO

R/W

0

3

TWWC

R

0

2

TWEN

R/W

0

R

0

1

0

TWIE

R/W

0

TWCR

The TWCR is used to control the operation of the TWI. It is used to enable the TWI, to initiate a

Master access by applying a START condition to the bus, to generate a Receiver acknowledge, to generate a stop condition, and to control halting of the bus while the data to be written to the

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bus are written to the TWDR. It also indicates a write collision if data is attempted written to

TWDR while the register is inaccessible.

• Bit 7 – TWINT: TWI Interrupt Flag

This bit is set by hardware when the TWI has finished its current job and expects application software response. If the I-bit in SREG and TWIE in TWCR are set, the MCU will jump to the

TWI Interrupt Vector. While the TWINT Flag is set, the SCL low period is stretched. The TWINT

Flag must be cleared by software by writing a logic one to it. Note that this flag is not automatically cleared by hardware when executing the interrupt routine. Also note that clearing this flag starts the operation of the TWI, so all accesses to the TWI Address Register (TWAR), TWI Status Register (TWSR), and TWI Data Register (TWDR) must be complete before clearing this flag.

• Bit 6 – TWEA: TWI Enable Acknowledge Bit

The TWEA bit controls the generation of the acknowledge pulse. If the TWEA bit is written to one, the ACK pulse is generated on the TWI bus if the following conditions are met:

1. The device’s own slave address has been received.

2. A general call has been received, while the TWGCE bit in the TWAR is set.

3. A data byte has been received in Master Receiver or Slave Receiver mode.

By writing the TWEA bit to zero, the device can be virtually disconnected from the two-wire

Serial Bus temporarily. Address recognition can then be resumed by writing the TWEA bit to one again.

• Bit 5 – TWSTA: TWI START Condition Bit

The application writes the TWSTA bit to one when it desires to become a Master on the two-wire

Serial Bus. The TWI hardware checks if the bus is available, and generates a START condition on the bus if it is free. However, if the bus is not free, the TWI waits until a STOP condition is detected, and then generates a new START condition to claim the bus Master status. TWSTA must be cleared by software when the START condition has been transmitted.

• Bit 4 – TWSTO: TWI STOP Condition Bit

Writing the TWSTO bit to one in Master mode will generate a STOP condition on the two-wire

Serial Bus. When the STOP condition is executed on the bus, the TWSTO bit is cleared automatically. In Slave mode, setting the TWSTO bit can be used to recover from an error condition.

This will not generate a STOP condition, but the TWI returns to a well-defined unaddressed

Slave mode and releases the SCL and SDA lines to a high impedance state.

• Bit 3 – TWWC: TWI Write Collision Flag

The TWWC bit is set when attempting to write to the TWI Data Register – TWDR when TWINT is low. This flag is cleared by writing the TWDR Register when TWINT is high.

• Bit 2 – TWEN: TWI Enable Bit

The TWEN bit enables TWI operation and activates the TWI interface. When TWEN is written to one, the TWI takes control over the I/O pins connected to the SCL and SDA pins, enabling the slew-rate limiters and spike filters. If this bit is written to zero, the TWI is switched off and all TWI transmissions are terminated, regardless of any ongoing operation.

• Bit 1 – Reserved

This bit is a reserved bit and will always read as zero.

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21.9.3

• Bit 0 – TWIE: TWI Interrupt Enable

When this bit is written to one, and the I-bit in SREG is set, the TWI interrupt request will be activated for as long as the TWINT Flag is high.

TWSR – TWI Status Register

21.9.4

Bit

(0xB9)

Read/Write

Initial Value

7

TWS7

R

1

6

TWS6

R

1

5

TWS5

R

1

4

TWS4

R

1

3

TWS3

R

1

2

R

0

1

TWPS1

R/W

0

0

TWPS0

R/W

0

TWSR

• Bits 7:3 – TWS: TWI Status

These 5 bits reflect the status of the TWI logic and the two-wire Serial Bus. The different status codes are described

”Transmission modes” on page 221

. Note that the value read from TWSR contains both the 5-bit status value and the 2-bit prescaler value. The application designer should mask the prescaler bits to zero when checking the Status bits. This makes status checking independent of prescaler setting. This approach is used in this datasheet, unless otherwise noted.

• Bit 2 – Reserved

This bit is reserved and will always read as zero.

• Bits 1:0 – TWPS: TWI Prescaler Bits

These bits can be read and written, and control the bit rate prescaler.

Table 21-7.

TWI Bit Rate Prescaler.

1

1

TWPS1

0

0

0

1

TWPS0

0

1

Prescaler value

1

4

16

64

To calculate bit rates, see

”Bit Rate Generator unit” on page 216

. The value of TWPS1..0 is used in the equation.

TWDR – TWI Data Register

Bit

(0xBB)

Read/Write

Initial Value

7

TWD7

R/W

1

6

TWD6

R/W

1

5

TWD5

R/W

1

4

TWD4

R/W

1

3

TWD3

R/W

1

2

TWD2

R/W

1

1

TWD1

R/W

1

0

TWD0

R/W

1

TWDR

In Transmit mode, TWDR contains the next byte to be transmitted. In Receive mode, the TWDR contains the last byte received. It is writable while the TWI is not in the process of shifting a byte.

This occurs when the TWI Interrupt Flag (TWINT) is set by hardware. Note that the Data Register cannot be initialized by the user before the first interrupt occurs. The data in TWDR remains stable as long as TWINT is set. While data is shifted out, data on the bus is simultaneously shifted in. TWDR always contains the last byte present on the bus, except after a wake up from a sleep mode by the TWI interrupt. In this case, the contents of TWDR is undefined. In the case

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21.9.5

of a lost bus arbitration, no data is lost in the transition from Master to Slave. Handling of the

ACK bit is controlled automatically by the TWI logic, the CPU cannot access the ACK bit directly.

• Bits 7:0 – TWD: TWI Data Register

These eight bits constitute the next data byte to be transmitted, or the latest data byte received on the two-wire Serial Bus.

TWAR – TWI (Slave) Address Register

21.9.6

Bit

(0xBA)

Read/Write

Initial Value

7

TWA6

R/W

1

6

TWA5

R/W

1

5

TWA4

R/W

1

4

TWA3

R/W

1

3

TWA2

R/W

1

2

TWA1

R/W

1

1

TWA0

R/W

1

0

TWGCE

R/W

0

TWAR

The TWAR should be loaded with the 7-bit Slave address (in the seven most significant bits of

TWAR) to which the TWI will respond when programmed as a Slave Transmitter or Receiver, and not needed in the Master modes. In multimaster systems, TWAR must be set in masters which can be addressed as Slaves by other Masters.

The LSB of TWAR is used to enable recognition of the general call address (0x00). There is an associated address comparator that looks for the slave address (or general call address if enabled) in the received serial address. If a match is found, an interrupt request is generated.

• Bits 7:1 – TWA: TWI (Slave) Address Register

These seven bits constitute the slave address of the TWI unit.

• Bit 0 – TWGCE: TWI General Call Recognition Enable Bit

If set, this bit enables the recognition of a General Call given over the two-wire Serial Bus.

TWAMR – TWI (Slave) Address Mask Register

Bit

(0xBD)

Read/Write

Initial Value

7

R/W

0

6

R/W

0

5

R/W

0

4

TWAM[6:0]

R/W

0

3

R/W

0

2

R/W

0

1

R/W

0

R

0

0

– TWAMR

• Bits 7:1 – TWAM: TWI Address Mask

The TWAMR can be loaded with a 7-bit Slave Address mask. Each of the bits in TWAMR can mask (disable) the corresponding address bit in the TWI Address Register (TWAR). If the mask bit is set to one then the address match logic ignores the compare between the incoming address bit and the corresponding bit in TWAR.

Figure 21-22 shows the address match logic in

detail.

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Figure 21-22.

TWI address match logic, block diagram.

TWAR0

Address

Bit 0

TWAMR0

Address Bit Comparator 0

Address Bit Comparator 6..1

• Bit 0 – Reserved

This bit is reserved and will always read as zero.

Address

Match

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22. AC - Analog Comparator

22.1

Overview

The Analog Comparator compares the input values on the positive pin AIN0 and negative pin

AIN1. When the voltage on the positive pin AIN0 is higher than the voltage on the negative pin

AIN1, the Analog Comparator output, ACO, is set. The comparator’s output can be set to trigger the Timer/Counter1 Input Capture function. In addition, the comparator can trigger a separate interrupt, exclusive to the Analog Comparator. The user can select Interrupt triggering on comparator output rise, fall or toggle. A block diagram of the comparator and its surrounding logic is shown in

Figure 22-1

.

The Power Reduction ADC bit, PRADC, in ”PRR0 – Power Reduction Register 0” on page 48

must be disabled by writing a logical zero to be able to use the ADC input MUX.

Figure 22-1.

Analog Comparator block diagram

(2)

.

BANDGAP

REFERENCE

ACBG

ACME

ADEN

ADC MULTIPLEXER

OUTPUT

(1)

Notes: 1. See

Table 22-1 on page 240 .

2. Refer to Figure 1-1 on page 2

and Table 14-5 on page 81 for Analog Comparator pin

placement.

22.2

Analog Comparator Multiplexed Input

It is possible to select any of the ADC7..0 pins to replace the negative input to the Analog Comparator. The ADC multiplexer is used to select this input, and consequently, the ADC must be switched off to utilize this feature. If the Analog Comparator Multiplexer Enable bit (ACME in

ADCSRB) is set and the ADC is switched off (ADEN in ADCSRA is zero), MUX2..0 in ADMUX

select the input pin to replace the negative input to the Analog Comparator, as shown in Table

22-1 on page 240 . If ACME is cleared or ADEN is set, AIN1 is applied to the negative input to the

Analog Comparator.

Table 22-1.

Analog Comparator Mulitiplexed input.

ACME

0

ADEN

x

MUX2..0

xxx

Analog Comparator negative input

AIN1

1

1

1

0 xxx

000

AIN1

ADC0

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Table 22-1.

Analog Comparator Mulitiplexed input. (Continued)

ACME

1

1

1

1

1

1

1

ADEN

0

0

0

0

0

0

0

MUX2..0

001

010

011

100

101

110

111

Analog Comparator negative input

ADC1

ADC2

ADC3

ADC4

ADC5

ADC6

ADC7

22.3

Register description

22.3.1

ADCSRB – ADC Control and Status Register B

22.3.2

Bit

(0x7B)

Read/Write

Initial Value

7

R

0

6

ACME

R/W

0

5

R

0

4

R

0

3

-

R

0

2

ADTS2

R/W

0

1

ADTS1

R/W

0

0

ADTS0

R/W

0

ADCSRB

• Bit 6 – ACME: Analog Comparator Multiplexer Enable

When this bit is written logic one and the ADC is switched off (ADEN in ADCSRA is zero), the

ADC multiplexer selects the negative input to the Analog Comparator. When this bit is written logic zero, AIN1 is applied to the negative input of the Analog Comparator. For a detailed description of this bit, see

”Analog Comparator Multiplexed Input” on page 240 .

ACSR – Analog Comparator Control and Status Register

Bit

0x30 (0x50)

Read/Write

Initial Value

7

ACD

R/W

0

6

ACBG

R/W

0

5

ACO

R

N/A

4

ACI

R/W

0

3

ACIE

R/W

0

2

ACIC

R/W

0

1

ACIS1

R/W

0

0

ACIS0

R/W

0

ACSR

• Bit 7 – ACD: Analog Comparator Disable

When this bit is written logic one, the power to the Analog Comparator is switched off. This bit can be set at any time to turn off the Analog Comparator. This will reduce power consumption in

Active and Idle mode. When changing the ACD bit, the Analog Comparator Interrupt must be disabled by clearing the ACIE bit in ACSR. Otherwise an interrupt can occur when the bit is changed.

• Bit 6 – ACBG: Analog Comparator Bandgap Select

When this bit is set, a fixed bandgap reference voltage replaces the positive input to the Analog

Comparator. When this bit is cleared, AIN0 is applied to the positive input of the Analog Comparator. When bandgap reference is used as input to the Analog Comparator, it will take a certain time for the voltage to stabilize. If not stabilized, the first conversion may give wrong value. See

”Internal Voltage Reference” on page 54 .

• Bit 5 – ACO: Analog Comparator Output

The output of the Analog Comparator is synchronized and then directly connected to ACO. The synchronization introduces a delay of 1 - 2 clock cycles.

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22.3.3

• Bit 4 – ACI: Analog Comparator Interrupt Flag

This bit is set by hardware when a comparator output event triggers the interrupt mode defined by ACIS1 and ACIS0. The Analog Comparator interrupt routine is executed if the ACIE bit is set and the I-bit in SREG is set. ACI is cleared by hardware when executing the corresponding interrupt handling vector. Alternatively, ACI is cleared by writing a logic one to the flag.

• Bit 3 – ACIE: Analog Comparator Interrupt Enable

When the ACIE bit is written logic one and the I-bit in the Status Register is set, the Analog Comparator interrupt is activated. When written logic zero, the interrupt is disabled.

• Bit 2 – ACIC: Analog Comparator Input Capture Enable

When written logic one, this bit enables the input capture function in Timer/Counter1 to be triggered by the Analog Comparator. The comparator output is in this case directly connected to the input capture front-end logic, making the comparator utilize the noise canceler and edge select features of the Timer/Counter1 Input Capture interrupt. When written logic zero, no connection between the Analog Comparator and the input capture function exists. To make the comparator trigger the Timer/Counter1 Input Capture interrupt, the ICIE1 bit in the Timer Interrupt Mask

Register (TIMSK1) must be set.

• Bits 1:0 – ACIS1:ACIS0: Analog Comparator Interrupt Mode Select

These bits determine which comparator events that trigger the Analog Comparator interrupt. The different settings are shown in

Table 22-2

.

Table 22-2.

ACIS1/ACIS0 settings.

ACIS1

0

0

1

1

ACIS0

0

1

0

1

Interrupt mode

Comparator Interrupt on Output Toggle.

Reserved

Comparator Interrupt on Falling Output Edge.

Comparator Interrupt on Rising Output Edge.

When changing the ACIS1/ACIS0 bits, the Analog Comparator Interrupt must be disabled by clearing its Interrupt Enable bit in the ACSR Register. Otherwise an interrupt can occur when the bits are changed.

DIDR1 – Digital Input Disable Register 1

Bit

(0x7F)

Read/Write

Initial Value

R

0

7

R

0

6

R

0

5

R

0

4

R

0

3

R

0

2

1

AIN1D

R/W

0

0

AIN0D

R/W

0

DIDR1

• Bit 1:0 – AIN1D:AIN0D: AIN1:AIN0 Digital Input Disable

When this bit is written logic one, the digital input buffer on the AIN1/0 pin is disabled. The corresponding PIN Register bit will always read as zero when this bit is set. When an analog signal is applied to the AIN1/0 pin and the digital input from this pin is not needed, this bit should be written logic one to reduce power consumption in the digital input buffer.

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23. ADC - Analog-to-digital converter

23.1

Features

10-bit resolution

0.5LSB integral non-linearity

±2LSB absolute accuracy

13 - 260µs conversion time

Up to 15kSPS at maximum resolution

Eight multiplexed single ended input channels

Differential mode with selectable gain at 1×, 10×, or 200×

Optional left adjustment for ADC result readout

0 - V

CC

ADC input voltage range

2.7 - V

CC

differential ADC voltage range

Selectable 2.56V or 1.1V ADC reference voltage

Free Running or Single Conversion mode

ADC start conversion by auto triggering on interrupt sources

Interrupt on ADC conversion complete

Sleep mode noise canceler

Note: 1. The differential input channels are not tested for devices in PDIP package. This feature is only guaranteed to work for devices in TQFP, VQFN/QFN/MLF, VFBGA and DRQFN packages.

23.2

Overview

The Atmel ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P features a 10-bit successive approximation ADC. The ADC is connected to an 8-channel Analog Multiplexer which allows 8 single-ended voltage inputs constructed from the pins of Port A. The single-ended voltage inputs refer to 0V (GND).

The device also supports 16 differential voltage input combinations. Two of the differential inputs

(ADC1, ADC0 and ADC3, ADC2) are equipped with a programmable gain stage. This provides amplification steps of 0 dB (1×), 20 dB (10×), or 46 dB (200×) on the differential input voltage before the A/D conversion. Seven differential analog input channels share a common negative terminal (ADC1), while any other ADC input can be selected as the positive input terminal. If 1× or 10× gain is used, 8-bit resolution can be expected. If 200× gain is used, 6-bit resolution can be expected. Note that internal references of 1.1V should not be used on 10× and 200× gain.

The ADC contains a Sample and Hold circuit which ensures that the input voltage to the ADC is

held at a constant level during conversion. A block diagram of the ADC is shown in Figure 23-1 on page 244 .

The ADC has a separate analog supply voltage pin, AV

CC

. AV

CC

must not differ more than ±0.3V

from V

CC

. See the paragraph

”ADC Noise Canceler” on page 251

on how to connect this pin.

Internal reference voltages of nominally 1.1V, 2.56V, or AV

CC

are provided On-chip. The voltage reference may be externally decoupled at the AREF pin by a capacitor for better noise performance. If V

CC

is below 2.1V, internal voltage reference of 1.1V should not be used on single ended channels.

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Figure 23-1.

Analog-to-digital Converter block schematic.

ADC CONVERSION

COMPLETE IRQ

INTERRUPT

FLAGS

ADTS[2:0]

8 -BIT DATABUS

ADC MULTIPLEXER

SELECT (ADMUX)

ADC CTRL & STATUS

REGISTER B (ADCSRB)

ADC CTRL & STATUS

REGISTER A (ADCSRA)

15

ADC DATA REGISTER

(ADCH/ADCL)

0

TRIGGER

SELECT

PRESCALER

START

MUX DECODER

CONVERSION LOGIC

AVCC

INTERNAL

REFERENCE

(1.1V/2.56V)

AREF 10-bit DAC

-

+

SAMPLE & HOLD

COMPARATOR

ADC[2:0]

N

EG

INPUT

MUX

-

+

GAIN

AMPLIFIER

ADC[7:0]

BANDGAP (1.1V)

REFERENCE

GND

23.3

Operation

POS

INPUT

MUX

ADC

MULTIPLEXER

OUTPUT

The ADC converts an analog input voltage to a 10-bit digital value through successive approximation. The minimum value represents GND and the maximum value represents the voltage on the AREF pin minus 1LSB. Optionally, AV

CC

or an internal 2.56V reference voltage may be connected to the AREF pin by writing to the REFSn bits in the ADMUX Register. The internal voltage reference may thus be decoupled by an external capacitor at the AREF pin to improve noise immunity.

The analog input channel and differential gain are selected by writing to the MUX bits in

ADMUX. Any of the ADC input pins, as well as GND and a fixed bandgap voltage reference, can be selected as single ended inputs to the ADC. A selection of ADC input pins can be selected as positive and negative inputs to the differential gain amplifier.

If differential channels are selected, the differential gain stage amplifies the voltage difference between the selected input channel pair by the selected gain factor. This amplified value then

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becomes the analog input to the ADC. If single ended channels are used, the gain amplifier is bypassed altogether.

The ADC is enabled by setting the ADC Enable bit, ADEN in ADCSRA. Voltage reference and input channel selections will not go into effect until ADEN is set. The ADC does not consume power when ADEN is cleared, so it is recommended to switch off the ADC before entering power saving sleep modes.

The ADC generates a 10-bit result which is presented in the ADC Data Registers, ADCH and

ADCL. By default, the result is presented right adjusted, but can optionally be presented left adjusted by setting the ADLAR bit in ADMUX.

If the result is left adjusted and no more than 8-bit precision is required, it is sufficient to read

ADCH. Otherwise, ADCL must be read first, then ADCH, to ensure that the content of the Data

Registers belongs to the same conversion. Once ADCL is read, ADC access to Data Registers is blocked. This means that if ADCL has been read, and a conversion completes before ADCH is read, neither register is updated and the result from the conversion is lost. When ADCH is read,

ADC access to the ADCH and ADCL Registers is re-enabled.

The ADC has its own interrupt which can be triggered when a conversion completes. When ADC access to the Data Registers is prohibited between reading of ADCH and ADCL, the interrupt will trigger even if the result is lost.

23.4

Starting a conversion

A single conversion is started by writing a logical one to the ADC Start Conversion bit, ADSC.

This bit stays high as long as the conversion is in progress and will be cleared by hardware when the conversion is completed. If a different data channel is selected while a conversion is in progress, the ADC will finish the current conversion before performing the channel change.

Alternatively, a conversion can be triggered automatically by various sources. Auto Triggering is enabled by setting the ADC Auto Trigger Enable bit, ADATE in ADCSRA. The trigger source is selected by setting the ADC Trigger Select bits, ADTS in ADCSRB (see description of the ADTS bits for a list of the trigger sources). When a positive edge occurs on the selected trigger signal, the ADC prescaler is reset and a conversion is started. This provides a method of starting conversions at fixed intervals. If the trigger signal still is set when the conversion completes, a new conversion will not be started. If another positive edge occurs on the trigger signal during conversion, the edge will be ignored. Note that an Interrupt Flag will be set even if the specific interrupt is disabled or the global interrupt enable bit in SREG is cleared. A conversion can thus be triggered without causing an interrupt. However, the Interrupt Flag must be cleared in order to trigger a new conversion at the next interrupt event.

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Figure 23-2.

ADC auto trigger logic.

ADTS[2:0]

PRESCALER

START

CLK

ADC

.

.

.

.

ADIF

SOURCE 1

SOURCE n

ADSC

EDGE

DETECTOR

ADATE

CONVERSION

LOGIC

Using the ADC Interrupt Flag as a trigger source makes the ADC start a new conversion as soon as the ongoing conversion has finished. The ADC then operates in Free Running mode, constantly sampling and updating the ADC Data Register. The first conversion must be started by writing a logical one to the ADSC bit in ADCSRA. In this mode the ADC will perform successive conversions independently of whether the ADC Interrupt Flag, ADIF is cleared or not.

If Auto Triggering is enabled, single conversions can be started by writing ADSC in ADCSRA to one. ADSC can also be used to determine if a conversion is in progress. The ADSC bit will be read as one during a conversion, independently of how the conversion was started.

23.5

Prescaling and Conversion Timing

Figure 23-3.

ADC prescaler.

ADEN

START

CK

Reset

7-BIT ADC PRESCALER

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ADPS0

ADPS1

ADPS2

ADC CLOCK SOURCE

By default, the successive approximation circuitry requires an input clock frequency between

50kHz and 200kHz to get maximum resolution. If a lower resolution than 10 bits is needed, the input clock frequency to the ADC can be higher than 200kHz to get a higher sample rate.

The ADC module contains a prescaler, which generates an acceptable ADC clock frequency from any CPU frequency above 100kHz. The prescaling is set by the ADPS bits in ADCSRA.

The prescaler starts counting from the moment the ADC is switched on by setting the ADEN bit

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in ADCSRA. The prescaler keeps running for as long as the ADEN bit is set, and is continuously reset when ADEN is low.

When initiating a single ended conversion by setting the ADSC bit in ADCSRA, the conversion

starts at the following rising edge of the ADC clock cycle. See ”Differential Gain Channels” on page 249

for details on differential conversion timing.

A normal conversion takes 13 ADC clock cycles. The first conversion after the ADC is switched on (ADEN in ADCSRA is set) takes 25 ADC clock cycles in order to initialize the analog circuitry.

When the bandgap reference voltage is used as input to the ADC, it will take a certain time for the voltage to stabilize. If not stabilized, the first value read after the first conversion may be wrong.

The actual sample-and-hold takes place 1.5 ADC clock cycles after the start of a normal conversion and 13.5 ADC clock cycles after the start of a first conversion. When a conversion is complete, the result is written to the ADC Data Registers, and ADIF is set. In single conversion mode, ADSC is cleared simultaneously. The software may then set ADSC again, and a new conversion will be initiated on the first rising ADC clock edge.

When Auto Triggering is used, the prescaler is reset when the trigger event occurs. This assures a fixed delay from the trigger event to the start of conversion. In this mode, the sample-and-hold takes place 2 ADC clock cycles after the rising edge on the trigger source signal. Three additional CPU clock cycles are used for synchronization logic.

When using Differential mode, along with Auto Trigging from a source other than the ADC Conversion Complete, each conversion will require 25 ADC clocks. This is because the ADC must be disabled and re-enabled after every conversion.

In Free Running mode, a new conversion will be started immediately after the conversion completes, while ADSC remains high. For a summary of conversion times, see

Table 23-1 on page

249 .

Figure 23-4.

ADC Timing diagram, first conversion (Single Conversion mode).

First Conversion

Next

Conversion

Cycle Number

ADC Clock

ADEN

ADSC

ADIF

ADCH

ADCL

1 2 12 13 14 15 16 17 18 19 20 21 22 23 24 25 1 2 3

MSB of Result

LSB of Result

MUX and REFS

Update

Sample & Hold

Conversion

Complete

MUX and REFS

Update

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Figure 23-5.

ADC Timing diagram, single conversion.

One Conversion

1 2 3 4 5 6 7 8 9 10 11 12 13

Cycle Number

ADC Clock

ADSC

ADIF

ADCH

ADCL

Sample & Hold

MUX and REFS

Update

Conversion

Complete

Next Conversion

1 2 3

MSB of Result

LSB of Result

MUX and REFS

Update

Figure 23-6.

ADC Timing diagram, auto triggered conversion.

One Conversion Next Conversion

Cycle Number

ADC Clock

Trigger

Source

ADATE

ADIF

ADCH

ADCL

1 2 3 4 5

Prescaler

Reset

MUX and REFS

Update

Sample & Hold

6 7 8 9 10 11 12 13

Conversion

Complete

1 2

MSB of Result

LSB of Result

Prescaler

Reset

Figure 23-7.

ADC Timing diagram, free running conversion.

One Conversion Next Conversion

4

Cycle Number

11

ADC Clock

ADSC

12 13 1

ADIF

ADCH

ADCL

2 3

MSB of Result

LSB of Result

Conversion

Complete

Sample & Hold

MUX and REFS

Update

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Table 23-1.

ADC conversion time.

Condition

First conversion

Normal conversions, single ended

Auto Triggered conversions

Normal conversions, differential

Sample & Hold (cycles from start of conversion) Conversion time (cycles)

14.5

1.5

25

13

2

1.5/2.5

13.5

13/14

23.5.1

Differential Gain Channels

When using differential gain channels, certain aspects of the conversion need to be taken into consideration. Note that the differential channels should not be used with an AREF < 2V.

Differential conversions are synchronized to the internal clock CK

ADC2

equal to half the ADC clock. This synchronization is done automatically by the ADC interface in such a way that the sample-and-hold occurs at a specific phase of CK

ADC2

. A conversion initiated by the user (that is, all single conversions, and the first free running conversion) when CK

ADC2

is low will take the same amount of time as a single ended conversion (13 ADC clock cycles from the next prescaled clock cycle). A conversion initiated by the user when CK

ADC2

is high will take 14 ADC clock cycles due to the synchronization mechanism. In Free Running mode, a new conversion is initiated immediately after the previous conversion completes, and since CK

ADC2

is high at this time, all automatically started (that is, all but the first) free running conversions will take 14 ADC clock cycles.

The gain stage is optimized for a bandwidth of 4kHz at all gain settings. Higher frequencies may be subjected to non-linear amplification. An external low-pass filter should be used if the input signal contains higher frequency components than the gain stage bandwidth. Note that the ADC clock frequency is independent of the gain stage bandwidth limitation. For example, the ADC clock period may be 6µs, allowing a channel to be sampled at 12kSPS, regardless of the bandwidth of this channel.

If differential gain channels are used and conversions are started by Auto Triggering, the ADC must be switched off between conversions. When Auto Triggering is used, the ADC prescaler is reset before the conversion is started. Since the gain stage is dependent of a stable ADC clock prior to the conversion, this conversion will not be valid. By disabling and then re-enabling the

ADC between each conversion (writing ADEN in ADCSRA to “0” then to “1”), only extended con-

versions are performed. The result from the extended conversions will be valid. See ”Prescaling and Conversion Timing” on page 246

for timing details.

23.6

Changing Channel or Reference Selection

The MUXn and REFS1:0 bits in the ADMUX Register are single buffered through a temporary register to which the CPU has random access. This ensures that the channels and reference selection only takes place at a safe point during the conversion. The channel and reference selection is continuously updated until a conversion is started. Once the conversion starts, the channel and reference selection is locked to ensure a sufficient sampling time for the ADC. Continuous updating resumes in the last ADC clock cycle before the conversion completes (ADIF in

ADCSRA is set). Note that the conversion starts on the following rising ADC clock edge after

ADSC is written. The user is thus advised not to write new channel or reference selection values to ADMUX until one ADC clock cycle after ADSC is written.

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23.6.1

23.6.2

If Auto Triggering is used, the exact time of the triggering event can be indeterministic. Special care must be taken when updating the ADMUX Register, in order to control which conversion will be affected by the new settings.

If both ADATE and ADEN is written to one, an interrupt event can occur at any time. If the

ADMUX Register is changed in this period, the user cannot tell if the next conversion is based on the old or the new settings. ADMUX can be safely updated in the following ways:

1.

When ADATE or ADEN is cleared.

2.

3.

During conversion, minimum one ADC clock cycle after the trigger event.

After a conversion, before the Interrupt Flag used as trigger source is cleared.

When updating ADMUX in one of these conditions, the new settings will affect the next ADC conversion.

Special care should be taken when changing differential channels. Once a differential channel has been selected, the gain stage may take as much as 125µs to stabilize to the new value.

Thus conversions should not be started within the first 125µs after selecting a new differential channel. Alternatively, conversion results obtained within this period should be discarded.

The same settling time should be observed for the first differential conversion after changing

ADC reference (by changing the REFS1:0 bits in ADMUX).

ADC Input Channels

When changing channel selections, the user should observe the following guidelines to ensure that the correct channel is selected:

In Single Conversion mode, always select the channel before starting the conversion. The channel selection may be changed one ADC clock cycle after writing one to ADSC. However, the simplest method is to wait for the conversion to complete before changing the channel selection.

In Free Running mode, always select the channel before starting the first conversion. The channel selection may be changed one ADC clock cycle after writing one to ADSC. However, the simplest method is to wait for the first conversion to complete, and then change the channel selection. Since the next conversion has already started automatically, the next result will reflect the previous channel selection. Subsequent conversions will reflect the new channel selection.

When switching to a differential gain channel, the first conversion result may have a poor accuracy due to the required settling time for the automatic offset cancellation circuitry. The user should preferably disregard the first conversion result.

ADC Voltage Reference

The reference voltage for the ADC (V

REF

) indicates the conversion range for the ADC. Single ended channels that exceed V

REF

will result in codes close to 0x3FF. V

REF

can be selected as either AVCC, internal 2.56V reference, or external AREF pin.

AVCC is connected to the ADC through a passive switch. The internal 2.56V reference is generated from the internal bandgap reference (V

BG

) through an internal amplifier. In either case, the external AREF pin is directly connected to the ADC, and the reference voltage can be made more immune to noise by connecting a capacitor between the AREF pin and ground. V

REF

can also be measured at the AREF pin with a high impedant voltmeter. Note that V

REF

is a high impedant source, and only a capacitive load should be connected in a system.

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If the user has a fixed voltage source connected to the AREF pin, the user may not use the other reference voltage options in the application, as they will be shorted to the external voltage. If no external voltage is applied to the AREF pin, the user may switch between AV

CC

and 2.56V as reference selection. The first ADC conversion result after switching reference voltage source may be inaccurate, and the user is advised to discard this result.

If differential channels are used, the selected reference should not be closer to AVCC than indicated in

Table 28-17 on page 341 .

23.7

ADC Noise Canceler

23.7.1

The ADC features a noise canceler that enables conversion during sleep mode to reduce noise induced from the CPU core and other I/O peripherals. The noise canceler can be used with ADC

Noise Reduction and Idle mode. To make use of this feature, the following procedure should be used: a. Make sure that the ADC is enabled and is not busy converting. Single Conversion

Mode must be selected and the ADC conversion complete interrupt must be enabled.

b.

Enter ADC Noise Reduction mode (or Idle mode). The ADC will start a conversion once the CPU has been halted.

c.

If no other interrupts occur before the ADC conversion completes, the ADC interrupt will wake up the CPU and execute the ADC Conversion Complete interrupt routine. If another interrupt wakes up the CPU before the ADC conversion is complete, that interrupt will be executed, and an ADC Conversion Complete interrupt request will be generated when the ADC conversion completes. The CPU will remain in active mode until a new sleep command is executed.

Note that the ADC will not be automatically turned off when entering other sleep modes than Idle mode and ADC Noise Reduction mode. The user is advised to write zero to ADEN before entering such sleep modes to avoid excessive power consumption. If the ADC is enabled in such sleep modes and the user wants to perform differential conversions, the user is advised to switch the ADC off and on after waking up from sleep to prompt an extended conversion to get a valid result.

Analog Input Circuitry

The Analog Input Circuitry for single ended channels is illustrated in

Figure 23-8 on page 252 An

analog source applied to ADCn is subjected to the pin capacitance and input leakage of that pin, regardless of whether that channel is selected as input for the ADC. When the channel is selected, the source must drive the S/H capacitor through the series resistance (combined resistance in the input path).

The ADC is optimized for analog signals with an output impedance of approximately 10kΩ or less. If such a source is used, the sampling time will be negligible. If a source with higher impedance is used, the sampling time will depend on how long time the source needs to charge the

S/H capacitor, with can vary widely. The user is recommended to only use low impedant sources with slowly varying signals, since this minimizes the required charge transfer to the S/H capacitor.

If differential gain channels are used, the input circuitry looks somewhat different, although source impedances of a few hundred kΩ or less is recommended.

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Signal components higher than the Nyquist frequency (f

ADC

/2) should not be present for either kind of channels, to avoid distortion from unpredictable signal convolution. The user is advised to remove high frequency components with a low-pass filter before applying the signals as inputs to the ADC.

Figure 23-8.

Analog input circuitry.

ADCn

I

IH

I

IL

1..100 kΩ

C

S/H

= 14 pF

V

CC

/2

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ATmega164A/PA/324A/PA/644A/PA/1284/P

23.7.2

Analog Noise Canceling Techniques

Digital circuitry inside and outside the device generates EMI which might affect the accuracy of analog measurements. If conversion accuracy is critical, the noise level can be reduced by applying the following techniques: a. Keep analog signal paths as short as possible. Make sure analog tracks run over the analog ground plane, and keep them well away from high-speed switching digital tracks.

b.

The AVCC pin on the device should be connected to the digital V

CC via an LC network as shown in

Figure 23-9

.

supply voltage c.

Use the ADC noise canceler function to reduce induced noise from the CPU.

d. If any ADC port pins are used as digital outputs, it is essential that these do not switch while a conversion is in progress.

Figure 23-9.

ADC Power Connections

PA4 (ADC4)

PA5 (ADC5)

PA6 (ADC6)

PA7 (ADC7)

AREF

GND

AVCC

PC7

23.7.3

Offset Compensation Schemes

The gain stage has a built-in offset cancellation circuitry that nulls the offset of differential measurements as much as possible. The remaining offset in the analog path can be measured directly by selecting the same channel for both differential inputs. This offset residue can be then subtracted in software from the measurement results. Using this kind of software based offset correction, offset on any channel can be reduced below one LSB.

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23.7.4

ADC Accuracy Definitions

An n-bit single-ended ADC converts a voltage linearly between GND and V

REF

in 2 n

steps

(LSBs). The lowest code is read as 0, and the highest code is read as 2 n

-1.

Several parameters describe the deviation from the ideal behavior:

• Offset: The deviation of the first transition (0x000 to 0x001) compared to the ideal transition (at

0.5LSB). Ideal value: 0LSB

Figure 23-10.

Offset error.

Output Code

Ideal ADC

Actual ADC

Offset

Error

V

REF

Input Voltage

• Gain Error: After adjusting for offset, the Gain Error is found as the deviation of the last transition (0x3FE to 0x3FF) compared to the ideal transition (at 1.5LSB below maximum). Ideal value: 0LSB

Figure 23-11.

Gain error.

Output Code

Gain

Error

8272D–AVR–05/12

Ideal ADC

Actual ADC

V

REF

Input Voltage

• Integral Non-linearity (INL): After adjusting for offset and gain error, the INL is the maximum deviation of an actual transition compared to an ideal transition for any code. Ideal value: 0

LSB

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Figure 23-12.

Integral non-linearity (INL).

Output Code

Ideal ADC

Actual ADC

V

REF

Input Voltage

• Differential Non-linearity (DNL): The maximum deviation of the actual code width (the interval between two adjacent transitions) from the ideal code width (1LSB). Ideal value: 0LSB

Figure 23-13.

Differential non-linearity (DNL).

Output Code

0x3FF

1 LSB

DNL

0x000

0

V

REF

Input Voltage

• Quantization Error: Due to the quantization of the input voltage into a finite number of codes, a range of input voltages (1LSB wide) will code to the same value. Always ±0.5LSB

• Absolute Accuracy: The maximum deviation of an actual (unadjusted) transition compared to an ideal transition for any code. This is the compound effect of Offset, Gain Error, Differential

Error, Non-linearity, and Quantization Error. Ideal value: ±0.5LSB

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23.8

ADC Conversion Result

After the conversion is complete (ADIF is high), the conversion result can be found in the ADC

Result Registers (ADCL, ADCH).

For single ended conversion, the result is

ADC

=

V

IN

1024

--------------------------

V

REF

where V

IN

is the voltage on the selected input pin and V

REF

the selected voltage reference (see

Table 23-3 on page 258 and

Table 23-4 on page 259

). 0x000 represents analog ground, and

0x3FF represents the selected reference voltage minus one LSB.

If differential channels are used, the result is

ADC

=

(

V

POS

V

NEG

------------------------------------------------------------------------

V

REF

where V

POS

is the voltage on the positive input pin, V

NEG

the voltage on the negative input pin,

GAIN the selected gain factor, and V

REF

the selected voltage reference. The result is presented in two’s complement form, from 0x200 (-512d) through 0x1FF (+511d). Note that if the user wants to perform a quick polarity check of the results, it is sufficient to read the MSB of the result

(ADC9 in ADCH). If this bit is one, the result is negative, and if this bit is zero, the result is posi-

tive. Figure 23-14 on page 257 shows the decoding of the differential input range.

Table 23-2 on page 257 shows the resulting output codes if the differential input channel pair

(ADCn - ADCm) is selected with a gain of GAIN and a reference voltage of V

REF

.

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Figure 23-14.

Differential measurement range.

Output Code

0x1FF

- V

REF

/GAIN

0x000

0x3FF

0

V

REF

/GAIN

Differential Input

Voltage (Volts)

0x200

Table 23-2.

Correlation between input voltage and output codes.

V

ADCn

V

ADCm

+ V

REF

/GAIN

V

ADCm

+ 0.999V

REF

/GAIN

V

ADCm

+ 0.998V

REF

/GAIN

...

V

ADCm

+ 0.001V

REF

/GAIN

V

ADCm

V

ADCm

- 0.001V

REF

/GAIN

...

V

ADCm

- 0.999V

REF

/GAIN

V

ADCm

- V

REF

/GAIN

Read code

0x1FF

0x1FF

0x1FE

...

0x001

0x000

0x3FF

...

0x201

0x200

...

1

Corresponding decimal value

511

511

510

0

-1

...

-511

-512

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Example:

ADMUX = 0xED (ADC3 - ADC2, 10× gain, 2.56V reference, left adjusted result)

Voltage on ADC3 is 300mV, voltage on ADC2 is 500mV.

ADCR = 512 × 10 × (300 - 500) / 2560 = -400 = 0x270

ADCL will thus read 0x00, and ADCH will read 0x9C. Writing zero to ADLAR right adjusts the result: ADCL = 0x70, ADCH = 0x02.

23.9

Register description

23.9.1

ADMUX – ADC Multiplexer Selection Register

Bit

(0x7C)

Read/Write

Initial Value

7

REFS1

R/W

0

6

REFS0

R/W

0

5

ADLAR

R/W

0

4

MUX4

R/W

0

3

MUX3

R/W

0

2

MUX2

R/W

0

1

MUX1

R/W

0

0

MUX0

R/W

0

ADMUX

• Bit 7:6 – REFS1:0: Reference Selection Bits

These bits select the voltage reference for the ADC, as shown in

Table 23-3 . If these bits are

changed during a conversion, the change will not go in effect until this conversion is complete

(ADIF in ADCSRA is set). The internal voltage reference options may not be used if an external reference voltage is being applied to the AREF pin.

Table 23-3.

Voltage Reference Selections for ADC

REFS1

0

0

1

1

REFS0 Voltage Reference Selection

0 AREF, Internal Vref turned off

1

0

1

AVCC with external capacitor at AREF pin

Internal 1.1V Voltage Reference with external capacitor at AREF pin

Internal 2.56V Voltage Reference with external capacitor at AREF pin

Note: If differential channels are selected, only 2.56V should be used as Internal Voltage Reference.

• Bit 5 – ADLAR: ADC Left Adjust Result

The ADLAR bit affects the presentation of the ADC conversion result in the ADC Data Register.

Write one to ADLAR to left adjust the result. Otherwise, the result is right adjusted. Changing the

ADLAR bit will affect the ADC Data Register immediately, regardless of any ongoing conversions. For a complete description of this bit, see

”ADCL and ADCH – The ADC Data Register” on page 261

.

• Bits 4:0 – MUX4:0: Analog Channel and Gain Selection Bits

The value of these bits selects which combination of analog inputs are connected to the ADC.

These bits also select the gain for the differential channels. See

Table 23-4 on page 259 for

details.

If these bits are changed during a conversion, the change will not go in effect until this conversion is complete (ADIF in ADCSRA is set).

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10100

10101

10110

10111

11000

11001

11010

11011

01100

01101

01110

(1)

01111

(1)

10000

10001

10010

10011

11100

11101

11110

11111

MUX4..0

00000

00001

00010

00011

00100

00101

00110

00111

01000

01001

01010

(1)

01011

(1)

Table 23-4.

Input channel and gain selections.

Single ended input

ADC0

ADC1

ADC2

ADC3

ADC4

ADC5

ADC6

ADC7

Positive differential input Negative differential input Gain

N/A

N/A

1.1V (V

BG

)

0 V (GND)

ADC0

ADC1

ADC2

ADC3

ADC4

ADC5

ADC6

ADC7

ADC0

ADC1

ADC0

ADC1

ADC2

ADC3

ADC2

ADC3

ADC0

ADC1

ADC2

ADC3

ADC4

ADC5

N/A

ADC1

ADC1

ADC1

ADC1

ADC1

ADC1

ADC1

ADC1

ADC0

ADC0

ADC0

ADC0

ADC2

ADC2

ADC2

ADC2

ADC2

ADC2

ADC2

ADC2

ADC2

ADC2

10×

10×

200×

200×

10×

10×

200×

200×

Note: 1. The differential input channels are not tested for devices in PDIP Package. This feature is only guaranteed to work for devices in TQFP and VQFN/QFN/MLF Packages.

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ATmega164A/PA/324A/PA/644A/PA/1284/P

23.9.2

ADCSRA – ADC Control and Status Register A

Bit

(0x7A)

Read/Write

Initial Value

7

ADEN

R/W

0

6

ADSC

R/W

0

5

ADATE

R/W

0

4

ADIF

R/W

0

3

ADIE

R/W

0

2

ADPS2

R/W

0

1

ADPS1

R/W

0

0

ADPS0

R/W

0

ADCSRA

• Bit 7 – ADEN: ADC Enable

Writing this bit to one enables the ADC. By writing it to zero, the ADC is turned off. Turning the

ADC off while a conversion is in progress, will terminate this conversion.

• Bit 6 – ADSC: ADC Start Conversion

In Single Conversion mode, write this bit to one to start each conversion. In Free Running Mode, write this bit to one to start the first conversion. The first conversion after ADSC has been written after the ADC has been enabled, or if ADSC is written at the same time as the ADC is enabled, will take 25 ADC clock cycles instead of the normal 13. This first conversion performs initialization of the ADC.

ADSC will read as one as long as a conversion is in progress. When the conversion is complete, it returns to zero. Writing zero to this bit has no effect.

• Bit 5 – ADATE: ADC Auto Trigger Enable

When this bit is written to one, Auto Triggering of the ADC is enabled. The ADC will start a conversion on a positive edge of the selected trigger signal. The trigger source is selected by setting the ADC Trigger Select bits, ADTS in ADCSRB.

• Bit 4 – ADIF: ADC Interrupt Flag

This bit is set when an ADC conversion completes and the Data Registers are updated. The

ADC Conversion Complete Interrupt is executed if the ADIE bit and the I-bit in SREG are set.

ADIF is cleared by hardware when executing the corresponding interrupt handling vector. Alternatively, ADIF is cleared by writing a logical one to the flag. Beware that if doing a Read-Modify-

Write on ADCSRA, a pending interrupt can be disabled. This also applies if the SBI and CBI instructions are used.

• Bit 3 – ADIE: ADC Interrupt Enable

When this bit is written to one and the I-bit in SREG is set, the ADC Conversion Complete Interrupt is activated.

• Bits 2:0 – ADPS2:0: ADC Prescaler Select Bits

These bits determine the division factor between the XTAL frequency and the input clock to the

ADC.

Table 23-5.

ADC prescaler selections.

ADPS2

0

0

0

0

ADPS1

0

0

1

1

ADPS0

0

1

0

1

Division factor

2

2

4

8

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23.9.3

ADLAR = 0

Table 23-5.

ADC prescaler selections. (Continued)

ADPS2

1

1

1

1

ADPS1

0

0

1

1

ADPS0

0

1

0

1

ADCL and ADCH – The ADC Data Register

Bit

(0x79)

(0x78)

Read/Write

Initial Value 0

0

R

R

15

ADC7

7

0

0

R

R

14

ADC6

6

0

0

R

R

13

ADC5

5

0

0

R

R

12

ADC4

4

0

0

R

R

11

ADC3

3

ADLAR = 1

0

0

R

R

10

ADC2

2

0

0

R

R

9

ADC9

ADC1

1

Division factor

16

32

64

128

0

0

R

R

8

ADC8

ADC0

0

ADCH

ADCL

Bit

(0x79)

(0x78)

Read/Write

Initial Value 0

0

R

R

15

ADC9

ADC1

7

0

0

R

R

14

ADC8

ADC0

6

0

0

R

R

13

ADC7

5

0

0

R

R

12

ADC6

4

0

0

R

R

11

ADC5

3

0

0

R

R

10

ADC4

2

0

0

R

R

9

ADC3

1

0

0

R

R

8

ADC2

0

ADCH

ADCL

When an ADC conversion is complete, the result is found in these two registers. If differential channels are used, the result is presented in two’s complement form.

When ADCL is read, the ADC Data Register is not updated until ADCH is read. Consequently, if the result is left adjusted and no more than 8-bit precision is required, it is sufficient to read

ADCH. Otherwise, ADCL must be read first, then ADCH.

The ADLAR bit in ADMUX, and the MUXn bits in ADMUX affect the way the result is read from the registers. If ADLAR is set, the result is left adjusted. If ADLAR is cleared (default), the result is right adjusted.

23.9.4

• ADC9:0: ADC Conversion Result

These bits represent the result from the conversion, as detailed in

”ADC Conversion Result” on page 256

.

ADCSRB – ADC Control and Status Register B

Bit

(0x7B)

Read/Write

Initial Value

R

0

7

6

ACME

R/W

0

R

0

5

R

0

4

R

0

3

2

ADTS2

R/W

0

1

ADTS1

R/W

0

0

ADTS0

R/W

0

ADCSRB

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23.9.5

• Bit 7, 5:3 – Reserved

T h e s e b i t s a r e r e s e r v e d f o r f u t u r e u s e i n t h e A t m e l

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P. For ensuring compability with future devices, these bits must be written zero when ADCSRB is written.

• Bit 2:0 – ADTS2:0: ADC Auto Trigger Source

If ADATE in ADCSRA is written to one, the value of these bits selects which source will trigger an ADC conversion. If ADATE is cleared, the ADTS[2:0] settings will have no effect. A conversion will be triggered by the rising edge of the selected Interrupt Flag. Note that switching from a trigger source that is cleared to a trigger source that is set, will generate a positive edge on the trigger signal. If ADEN in ADCSRA is set, this will start a conversion. Switching to Free Running mode (ADTS[2:0]=0) will not cause a trigger event, even if the ADC Interrupt Flag is set .

Table 23-6.

ADC auto trigger source selections.

1

1

0

1

1

ADTS2

0

0

0

0

1

1

0

1

ADTS1

0

0

1

ADTS0

0

1

0

1

0

1

0

1

Trigger source

Free Running mode

Analog Comparator

External Interrupt Request 0

Timer/Counter0 Compare Match

Timer/Counter0 Overflow

Timer/Counter1 Compare Match B

Timer/Counter1 Overflow

Timer/Counter1 Capture Event

DIDR0 – Digital Input Disable Register 0

Bit

(0x7E)

Read/Write

Initial Value

7

ADC7D

R/W

0

6

ADC6D

R/W

0

5

ADC5D

R/W

0

4

ADC4D

R/W

0

3

ADC3D

R/W

0

2

ADC2D

R/W

0

1

ADC1D

R/W

0

0

ADC0D

R/W

0

DIDR0

• Bit 7:0 – ADC7D..ADC0D: ADC7:0 Digital Input Disable

When this bit is written logic one, the digital input buffer on the corresponding ADC pin is disabled. The corresponding PIN Register bit will always read as zero when this bit is set. When an analog signal is applied to the ADC7:0 pin and the digital input from this pin is not needed, this bit should be written logic one to reduce power consumption in the digital input buffer.

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24. JTAG interface and on-chip debug system

24.1

Features

JTAG (IEEE std. 1149.1 Compliant) interface

Boundary-scan capabilities according to the IEEE std. 1149.1 (JTAG) standard

Debugger access to:

– All internal peripheral units

– Internal and external RAM

– The internal register file

– Program counter

– EEPROM and flash memories

Extensive on-chip debug support for break conditions, including:

– AVR break instruction

– Break on change of program memory flow

– Single step break

– Program memory break points on single address or address range

– Data memory break points on single address or address range

Programming of Flash, EEPROM, Fuses, and Lock Bits through the JTAG Interface

On-chip Debugging Supported by Atmel AVR Studio

®

24.2

Overview

The AVR IEEE std. 1149.1 compliant JTAG interface can be used for

• Testing PCBs by using the JTAG Boundary-scan capability

• Programming the non-volatile memories, Fuses and Lock bits

• On-chip debugging

A brief description is given in the following sections. Detailed descriptions for Programming via the JTAG interface, and using the Boundary-scan Chain can be found in the sections

”Programming via the JTAG Interface” on page 316 and

”IEEE 1149.1 (JTAG) Boundary-scan” on page

269

,

respectively. The On-chip Debug support is considered being private JTAG instructions, and distributed within Atmel and to selected third party vendors only.

Figure 24-1

shows a block diagram of the JTAG interface and the On-chip Debug system. The

TAP Controller is a state machine controlled by the TCK and TMS signals. The TAP Controller selects either the JTAG Instruction Register or one of several Data Registers as the scan chain

(Shift Register) between the TDI – input and TDO – output. The Instruction Register holds JTAG instructions controlling the behavior of a Data Register.

The ID-Register, Bypass Register, and the Boundary-scan Chain are the Data Registers used for board-level testing. The JTAG Programming Interface (actually consisting of several physical and virtual Data Registers) is used for serial programming via the JTAG interface. The Internal

Scan Chain and Break Point Scan Chain are used for On-chip debugging only.

24.3

TAP – Test Access Port

The JTAG interface is accessed through four of the AVR’s pins. In JTAG terminology, these pins constitute the Test Access Port – TAP. These pins are:

• TMS: Test mode select. This pin is used for navigating through the TAP-controller state machine

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• TCK: Test Clock. JTAG operation is synchronous to TCK

• TDI: Test Data In. Serial input data to be shifted in to the Instruction Register or Data Register

(Scan Chains)

• TDO: Test Data Out. Serial output data from Instruction Register or Data Register

The IEEE std. 1149.1 also specifies an optional TAP signal; TRST – Test ReSeT – which is not provided.

When the JTAGEN Fuse is unprogrammed, these four TAP pins are normal port pins, and the

TAP controller is in reset. When programmed, the input TAP signals are internally pulled high and the JTAG is enabled for Boundary-scan and programming. The device is shipped with this fuse programmed.

For the On-chip Debug system, in addition to the JTAG interface pins, the RESET pin is monitored by the debugger to be able to detect external reset sources. The debugger can also pull the RESET pin low to reset the whole system, assuming only open collectors on the reset line are used in the application.

Figure 24-1.

Block diagram.

I/O PORT 0

DEVICE BOUNDARY

BOUNDARY SCAN CHAIN

TDI

TDO

TCK

TMS

TAP

CONTROLLER

M

U

X

INSTRUCTION

REGISTER

ID

REGISTER

BYPASS

REGISTER

BREAKPOINT

SCAN CHAIN

ADDRESS

DECODER

JTAG PROGRAMMING

INTERFACE

FLASH

MEMORY

Address

Data

BREAKPOINT

UNIT

INTERNAL

SCAN

CHAIN

FLOW CONTROL

UNIT

DIGITAL

PERIPHERAL

UNITS

JTAG / AVR CORE

COMMUNICATION

INTERFACE

OCD STATUS

AND CONTROL

AVR CPU

PC

Instruction

ANALOG

PERIPHERIAL

UNITS

Analog inputs

Control & Clock lines

I/O PORT n

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Figure 24-2.

TAP controller state diagram.

1 Test-Logic-Reset

0

0

Run-Test/Idle

1

Select-DR Scan

1

0

1

Capture-DR

0

0

Shift-DR

1

Exit1-DR

0

Pause-DR

1

Exit2-DR

1

Update-DR

1 0

1

0

0

1

0

Select-IR Scan

1

0

Capture-IR

0

Shift-IR

1

0

Exit1-IR

0

Pause-IR

1

Exit2-IR

1

Update-IR

1 0

1

0

24.4

TAP controller

The TAP controller is a 16-state finite state machine that controls the operation of the Boundaryscan circuitry, JTAG programming circuitry, or On-chip Debug system. The state transitions

depicted in Figure 24-2 depend on the signal present on TMS (shown adjacent to each state

transition) at the time of the rising edge at TCK. The initial state after a Power-on Reset is Test-

Logic-Reset.

As a definition in this document, the LSB is shifted in and out first for all Shift Registers.

Assuming Run-Test/Idle is the present state, a typical scenario for using the JTAG interface is:

• At the TMS input, apply the sequence 1, 1, 0, 0 at the rising edges of TCK to enter the Shift

Instruction Register – Shift-IR state. While in this state, shift the four bits of the JTAG instructions into the JTAG Instruction Register from the TDI input at the rising edge of TCK.

The TMS input must be held low during input of the three LSBs in order to remain in the Shift-

IR state. The MSB of the instruction is shifted in when this state is left by setting TMS high.

While the instruction is shifted in from the TDI pin, the captured IR-state 0x01 is shifted out on the TDO pin. The JTAG Instruction selects a particular Data Register as path between TDI and

TDO and controls the circuitry surrounding the selected Data Register.

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• Apply the TMS sequence 1, 1, 0 to re-enter the Run-Test/Idle state. The instruction is latched onto the parallel output from the Shift Register path in the Update-IR state. The Exit-IR, Pause-

IR, and Exit2-IR states are only used for navigating the state machine

• At the TMS input, apply the sequence 1, 0, 0 at the rising edges of TCK to enter the Shift Data

Register – Shift-DR state. While in this state, upload the selected Data Register (selected by the present JTAG instruction in the JTAG Instruction Register) from the TDI input at the rising edge of TCK. In order to remain in the Shift-DR state, the TMS input must be held low during input of all bits except the MSB. The MSB of the data is shifted in when this state is left by setting TMS high. While the Data Register is shifted in from the TDI pin, the parallel inputs to the Data Register captured in the Capture-DR state is shifted out on the TDO pin

• Apply the TMS sequence 1, 1, 0 to re-enter the Run-Test/Idle state. If the selected Data

Register has a latched parallel-output, the latching takes place in the Update-DR state. The

Exit-DR, Pause-DR, and Exit2-DR states are only used for navigating the state machine

As shown in the state diagram, the Run-Test/Idle state need not be entered between selecting

JTAG instruction and using Data Registers, and some JTAG instructions may select certain functions to be performed in the Run-Test/Idle, making it unsuitable as an Idle state.

Note: Independent of the initial state of the TAP Controller, the Test-Logic-Reset state can always be entered by holding TMS high for five TCK clock periods.

For detailed information on the JTAG specification, refer to the literature listed in ”Bibliography” on page 268 .

24.5

Using the Boundary-scan Chain

A complete description of the Boundary-scan capabilities are given in the section ”IEEE 1149.1

(JTAG) Boundary-scan” on page 269

.

24.6

Using the On-chip Debug System

As shown in

Figure 24-1 on page 264 , the hardware support for On-chip Debugging consists

mainly of

• A scan chain on the interface between the internal AVR CPU and the internal peripheral units

• Break Point unit

• Communication interface between the CPU and JTAG system

All read or modify/write operations needed for implementing the Debugger are done by applying

AVR instructions via the internal AVR CPU Scan Chain. The CPU sends the result to an I/O memory mapped location which is part of the communication interface between the CPU and the

JTAG system.

The Break Point Unit implements Break on Change of Program Flow, Single Step Break, two

Program Memory Break Points, and two combined Break Points. Together, the four Break

Points can be configured as either:

• Four single Program Memory Break Points

• Three single Program Memory Break Point + one single Data Memory Break Point

• Two single Program Memory Break Points + two single Data Memory Break Points

• Two single Program Memory Break Points + one Program Memory Break Point with mask

(“range Break Point”)

• Two single Program Memory Break Points + one Data Memory Break Point with mask (“range

Break Point”)

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A debugger, like the Atmel AVR Studio, may however use one or more of these resources for its internal purpose, leaving less flexibility to the end-user.

A list of the On-chip Debug specific JTAG instructions is given in ”On-chip Debug Specific JTAG

Instructions” on page 267 .

The JTAGEN Fuse must be programmed to enable the JTAG Test Access Port. In addition, the

OCDEN Fuse must be programmed and no Lock bits must be set for the On-chip debug system to work. As a security feature, the On-chip debug system is disabled when either of the LB1 or

LB2 Lock bits are set. Otherwise, the On-chip debug system would have provided a back-door into a secured device.

The AVR Studio enables the user to fully control execution of programs on an AVR device with

On-chip Debug capability, AVR In-Circuit Emulator, or the built-in AVR Instruction Set Simulator.

AVR Studio

®

supports source level execution of Assembly programs assembled with Atmel Corporation’s AVR Assembler and C programs compiled with third party vendors’ compilers.

AVR Studio runs under Microsoft

®

Windows

®

95/98/2000 and Microsoft Windows NT

®

.

For a full description of the AVR Studio, please refer to the AVR Studio User Guide. Only highlights are presented in this document.

All necessary execution commands are available in AVR Studio, both on source level and on disassembly level. The user can execute the program, single step through the code either by tracing into or stepping over functions, step out of functions, place the cursor on a statement and execute until the statement is reached, stop the execution, and reset the execution target. In addition, the user can have an unlimited number of code Break Points (using the BREAK instruction) and up to two data memory Break Points, alternatively combined as a mask (range)

Break Point.

24.7

On-chip Debug Specific JTAG Instructions

24.7.1

PRIVATE0; 0x8

The On-chip debug support is considered being private JTAG instructions, and distributed within

Atmel

®

and to selected third party vendors only. Instruction opcodes are listed for reference.

24.7.2

24.7.3

PRIVATE1; 0x9

Private JTAG instruction for accessing On-chip debug system.

PRIVATE2; 0xA

Private JTAG instruction for accessing On-chip debug system.

PRIVATE3; 0xB

Private JTAG instruction for accessing On-chip debug system.

24.7.4

Private JTAG instruction for accessing On-chip debug system.

24.8

Using the JTAG Programming Capabilities

Programming of AVR parts via JTAG is performed via the 4-pin JTAG port, TCK, TMS, TDI, and

TDO. These are the only pins that need to be controlled/observed to perform JTAG programming (in addition to power pins). It is not required to apply 12V externally. The JTAGEN Fuse must be programmed and the JTD bit in the MCUCR Register must be cleared to enable the

JTAG Test Access Port.

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The JTAG programming capability supports:

• Flash programming and verifying

• EEPROM programming and verifying

• Fuse programming and verifying

• Lock bit programming and verifying

The Lock bit security is exactly as in parallel programming mode. If the Lock bits LB1 or LB2 are programmed, the OCDEN Fuse cannot be programmed unless first doing a chip erase. This is a security feature that ensures no back-door exists for reading out the content of a secured device.

The details on programming through the JTAG interface and programming specific JTAG instructions are given in the section

”Programming via the JTAG Interface” on page 316 .

24.9

Bibliography

For more information about general Boundary-scan, the following literature can be consulted:

• IEEE: IEEE Std. 1149.1-1990. IEEE Standard Test Access Port and Boundary-scan

Architecture, IEEE, 1993

• Colin Maunder: The Board Designers Guide to Testable Logic Circuits, Addison-Wesley, 1992

24.10 Register description

24.10.1

OCDR – On-chip Debug Register

Bit

0x31 (0x51)

Read/Write

Initial Value

7

MSB/IDRD

R/W

0

6

R/W

0

5

R/W

0

4

R/W

0

3

R/W

0

2

R/W

0

1

R/W

0

0

LSB

R/W

0

OCDR

The OCDR Register provides a communication channel from the running program in the microcontroller to the debugger. The CPU can transfer a byte to the debugger by writing to this location. At the same time, an internal flag; I/O Debug Register Dirty – IDRD – is set to indicate to the debugger that the register has been written. When the CPU reads the OCDR Register the seven LSB will be from the OCDR Register, while the MSB is the IDRD bit. The debugger clears the IDRD bit when it has read the information.

In some AVR devices, this register is shared with a standard I/O location. In this case, the OCDR

Register can only be accessed if the OCDEN Fuse is programmed, and the debugger enables access to the OCDR Register. In all other cases, the standard I/O location is accessed.

Refer to the debugger documentation for further information on how to use this register.

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25. IEEE 1149.1 (JTAG) Boundary-scan

25.1

Features

JTAG (IEEE std. 1149.1 compliant) interface

Boundary-scan capabilities according to the JTAG standard

Full scan of all port functions as well as analog circuitry having off-chip connections

Supports the optional IDCODE instruction

Additional public AVR_RESET instruction to reset the AVR

25.2

Overview

The Boundary-scan chain has the capability of driving and observing the logic levels on the digital I/O pins, as well as the boundary between digital and analog logic for analog circuitry having off-chip connections. At system level, all ICs having JTAG capabilities are connected serially by the TDI/TDO signals to form a long Shift Register. An external controller sets up the devices to drive values at their output pins, and observe the input values received from other devices. The controller compares the received data with the expected result. In this way, Boundary-scan provides a mechanism for testing interconnections and integrity of components on Printed Circuits

Boards by using the four TAP signals only.

The four IEEE 1149.1 defined mandatory JTAG instructions IDCODE, BYPASS, SAMPLE/PRE-

LOAD, and EXTEST, as well as the AVR specific public JTAG instruction AVR_RESET can be used for testing the Printed Circuit Board. Initial scanning of the Data Register path will show the

ID-Code of the device, since IDCODE is the default JTAG instruction. It may be desirable to have the AVR device in reset during test mode. If not reset, inputs to the device may be determined by the scan operations, and the internal software may be in an undetermined state when exiting the test mode. Entering reset, the outputs of any port pin will instantly enter the high impedance state, making the HIGHZ instruction redundant. If needed, the BYPASS instruction can be issued to make the shortest possible scan chain through the device. The device can be set in the reset state either by pulling the external RESET pin low, or issuing the AVR_RESET instruction with appropriate setting of the Reset Data Register.

The EXTEST instruction is used for sampling external pins and loading output pins with data.

The data from the output latch will be driven out on the pins as soon as the EXTEST instruction is loaded into the JTAG IR-Register. Therefore, the SAMPLE/PRELOAD should also be used for setting initial values to the scan ring, to avoid damaging the board when issuing the EXTEST instruction for the first time. SAMPLE/PRELOAD can also be used for taking a snapshot of the external pins during normal operation of the part.

The JTAGEN Fuse must be programmed and the JTD bit in the I/O Register MCUCR must be cleared to enable the JTAG Test Access Port.

When using the JTAG interface for Boundary-scan, using a JTAG TCK clock frequency higher than the internal chip frequency is possible. The chip clock is not required to run.

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25.3

Data Registers

25.3.1

The Data Registers relevant for Boundary-scan operations are:

• Bypass Register

• Device Identification Register

• Reset Register

• Boundary-scan Chain

Bypass Register

25.3.2

The Bypass Register consists of a single Shift Register stage. When the Bypass Register is selected as path between TDI and TDO, the register is reset to 0 when leaving the Capture-DR controller state. The Bypass Register can be used to shorten the scan chain on a system when the other devices are to be tested.

Device Identification Register

Figure 25-1

shows the structure of the Device Identification Register.

Figure 25-1.

The format of the device identification register.

Bit

Device ID

MSB

31

Version

4 bits

28 27

Part Number

16 bits

12 11

Manufacturer ID

11 bits

1

LSB

0

1

1-bit

Version

Part Number

Manufacturer ID

25.3.3

Reset Register

Version is a 4-bit number identifying the revision of the component. The JTAG version number follows the revision of the device. Revision A is 0x0, revision B is 0x1 and so on.

The part number is a 16-bit code identifying the component. The JTAG Part Number for Atmel

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P is listed in

Table 27-6 on page

300 .

The Manufacturer ID is a 11-bit code identifying the manufacturer. The JTAG manufacturer ID

for ATMEL is listed in Table 27-6 on page 300 .

The Reset Register is a test Data Register used to reset the part. Since the AVR tri-states Port

Pins when reset, the Reset Register can also replace the function of the unimplemented optional

JTAG instruction HIGHZ.

A high value in the Reset Register corresponds to pulling the external Reset low. The part is reset as long as there is a high value present in the Reset Register. Depending on the fuse set-

tings for the clock options, the part will remain reset for a reset time-out period (refer to ”Clock

Sources” on page 31 ) after releasing the Reset Register. The output from this Data Register is

not latched, so the reset will take place immediately, as shown in

Figure 25-2 on page 271

.

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Figure 25-2.

Reset register.

To

TDO

From Other Internal and

External Reset Sources

From

TDI

D Q

Internal reset

ClockDR · AVR_RESET

25.3.4

Boundary-scan Chain

The Boundary-scan Chain has the capability of driving and observing the logic levels on the digital I/O pins, as well as the boundary between digital and analog logic for analog circuitry having off-chip connections.

See ”Boundary-scan Chain” on page 272

for a complete description.

25.4

Boundary-scan Specific JTAG Instructions

The Instruction Register is 4-bit wide, supporting up to 16 instructions. Listed below are the

JTAG instructions useful for Boundary-scan operation. Note that the optional HIGHZ instruction is not implemented, but all outputs with tri-state capability can be set in high-impedant state by using the AVR_RESET instruction, since the initial state for all port pins is tri-state.

As a definition in this datasheet, the LSB is shifted in and out first for all Shift Registers.

The OPCODE for each instruction is shown behind the instruction name in hex format. The text describes which Data Register is selected as path between TDI and TDO for each instruction.

25.4.1

EXTEST; 0x0

Mandatory JTAG instruction for selecting the Boundary-scan Chain as Data Register for testing circuitry external to the AVR package. For port-pins, Pull-up Disable, Output Control, Output

Data, and Input Data are all accessible in the scan chain. For Analog circuits having off-chip connections, the interface between the analog and the digital logic is in the scan chain. The contents of the latched outputs of the Boundary-scan chain is driven out as soon as the JTAG IR-

Register is loaded with the EXTEST instruction.

The active states are:

• Capture-DR: Data on the external pins are sampled into the Boundary-scan Chain

• Shift-DR: The Internal Scan Chain is shifted by the TCK input

• Update-DR: Data from the scan chain is applied to output pins

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25.4.2

25.4.3

25.4.4

IDCODE; 0x1

Optional JTAG instruction selecting the 32-bit ID-Register as Data Register. The ID-Register consists of a version number, a device number and the manufacturer code chosen by JEDEC.

This is the default instruction after power-up.

The active states are:

• Capture-DR: Data in the IDCODE Register is sampled into the Boundary-scan Chain

• Shift-DR: The IDCODE scan chain is shifted by the TCK input

SAMPLE_PRELOAD; 0x2

Mandatory JTAG instruction for pre-loading the output latches and taking a snap-shot of the input/output pins without affecting the system operation. However, the output latches are not connected to the pins. The Boundary-scan Chain is selected as Data Register.

The active states are:

• Capture-DR: Data on the external pins are sampled into the Boundary-scan Chain

• Shift-DR: The Boundary-scan Chain is shifted by the TCK input

• Update-DR: Data from the Boundary-scan chain is applied to the output latches. However, the output latches are not connected to the pins

AVR_RESET; 0xC

The AVR specific public JTAG instruction for forcing the AVR device into the Reset mode or releasing the JTAG reset source. The TAP controller is not reset by this instruction. The one bit

Reset Register is selected as Data Register. Note that the reset will be active as long as there is a logic “one” in the Reset Chain. The output from this chain is not latched.

The active states are:

• Shift-DR: The Reset Register is shifted by the TCK input

25.4.5

BYPASS; 0xF

Mandatory JTAG instruction selecting the Bypass Register for Data Register.

The active states are:

• Capture-DR: Loads a logic “0” into the Bypass Register

• Shift-DR: The Bypass Register cell between TDI and TDO is shifted

25.5

Boundary-scan Chain

25.5.1

The Boundary-scan chain has the capability of driving and observing the logic levels on the digital I/O pins, as well as the boundary between digital and analog logic for analog circuitry having off-chip connection.

Scanning the Digital Port Pins

Figure 25-3 on page 273

shows the Boundary-scan Cell for a bi-directional port pin. The pull-up function is disabled during Boundary-scan when the JTAG IC contains EXTEST or

SAMPLE_PRELOAD. The cell consists of a bi-directional pin cell that combines the three signals Output Control - OCxn, Output Data - ODxn, and Input Data - IDxn, into only a two-stage

Shift Register. The port and pin indexes are not used in the following description:

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The Boundary-scan logic is not included in the figures in the datasheet. Figure 25-4

shows a

simple digital port pin as described in the section ”I/O-Ports” on page 72

. The Boundary-scan

details from Figure 25-3

replaces the dashed box in Figure 25-4 on page 274 .

When no alternate port function is present, the Input Data - ID - corresponds to the PINxn Register value (but ID has no synchronizer), Output Data corresponds to the PORT Register, Output

Control corresponds to the Data Direction - DD Register, and the Pull-up Enable - PUExn - corresponds to logic expression PUD · DDxn · PORTxn.

Digital alternate port functions are connected outside the dotted box in

Figure 25-4 on page 274

to make the scan chain read the actual pin value. For analog function, there is a direct connection from the external pin to the analog circuit. There is no scan chain on the interface between the digital and the analog circuitry, but some digital control signal to analog circuitry are turned off to avoid driving contention on the pads.

When JTAG IR contains EXTEST or SAMPLE_PRELOAD the clock is not sent out on the port pins even if the CKOUT fuse is programmed. Even though the clock is output when the JTAG IR contains SAMPLE_PRELOAD, the clock is not sampled by the boundary scan.

Figure 25-3.

Boundary-scan cell for bi-directional port pin with pull-up function.

ShiftDR

To Next Cell

EXTEST Vcc

Pull-up Enable (PUE)

0

1

Output Control (OC)

0

1

FF1

D Q

LD1

D Q

G

0

1

Output Data (OD)

0

1

0

1

FF0

D Q

LD0

D Q

G

0

1

Input Data (ID)

From Last Cell ClockDR UpdateDR

273

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Figure 25-4.

General Port Pin schematic diagram.

See Boundary-scan

Description for Details!

PUExn

PUD

OCxn

Q D

DDxn

Q

CLR

RESET

WDx

RDx

25.5.2

Pxn

IDxn

SLEEP

ODxn

Q D

PORTxn

Q

CLR

RESET

WRx

RRx

SYNCHRONIZER

D Q

L Q

D Q

PINxn

Q

RPx

CLK

I/O

PUD:

PUExn:

OCxn:

ODxn:

IDxn:

SLEEP:

PULLUP DISABLE

PULLUP ENABLE for pin Pxn

OUTPUT CONTROL for pin Pxn

OUTPUT DATA to pin Pxn

INPUT DATA from pin Pxn

SLEEP CONTROL

WDx:

RDx:

WRx:

RRx:

RPx:

CLK :

WRITE DDRx

READ DDRx

WRITE PORTx

READ PORTx REGISTER

READ PORTx PIN

I/O CLOCK

Scanning the RESET Pin

The RESET pin accepts 5V active low logic for standard reset operation, and 12V active high logic for High Voltage Parallel programming. An observe-only cell as shown in

Figure 25-5 is

inserted for the 5V reset signal.

Figure 25-5.

Observe-only cell.

ShiftDR

To

Next

Cell

From System Pin To System Logic

0

1

FF1

D Q

From

Previous

Cell

ClockDR

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25.6

Atmel ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P Boundary-scan order

Table 25-1

shows the Scan order between TDI and TDO when the Boundary-scan chain is selected as data path. Bit 0 is the LSB; the first bit scanned in, and the first bit scanned out. The scan order follows the pin-out order as far as possible. Therefore, the bits of Port A and Port K is scanned in the opposite bit order of the other ports. Exceptions from the rules are the Scan chains for the analog circuits, which constitute the most significant bits of the scan chain regardless of which physical pin they are connected to. In

Figure 25-3 on page 273

, PXn. Data corresponds to FF0, PXn. Control corresponds to FF1, PXn. Bit 4, 5, 6, and 7 of Port F is not in the scan chain, since these pins constitute the TAP pins when the JTAG is enabled.

Table 25-1.

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P Boundary-scan order.

Module

46

45

44

43

50

49

48

47

42

41

40

54

53

52

51

Bit number

56

55

Signal name

PB0.Data

PB0.Control

PB1.Data

PB1.Control

PB2.Data

PB2.Control

PB3.Data

PB3.Control

PB4.Data

PB4.Control

PB5.Data

PB5.Control

PB6.Data

PB6.Control

PB7.Data

PB7.Control

RSTT

Port B

Reset Logic (Observe Only)

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Table 25-1.

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P Boundary-scan order. (Continued)

Module

22

21

20

19

26

25

24

23

18

17

16

15

30

29

28

27

34

33

32

31

37

36

35

Bit number

39

38

PD6.Control

PD7.Data

PD7.Control

PC0.Data

PC0.Control

PC1.Data

PC1.Control

PC6.Data

PC6.Control

PC7.Data

PC7.Control

PA7.Data

Signal name

PD0.Data

PD0.Control

PD1.Data

PD1.Control

PD2.Data

PD2.Control

PD3.Data

PD3.Control

PD4.Data

PD4.Control

PD5.Data

PD5.Control

PD6.Data

Port D

Port C

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Table 25-1.

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P Boundary-scan order. (Continued)

Module

3

2

5

4

1

0

7

6

9

8

12

11

10

Bit number

14

13

Signal name

PA7.Control

PA6.Data

PA6.Control

PA5.Data

PA5.Control

PA4.Data

PA4.Control

PA3.Data

PA3.Control

PA2.Data

PA2.Control

PA1.Data

PA1.Control

PA0.Data

PA0.Control

Port A

25.7

Boundary-scan Description Language Files

Boundary-scan Description Language (BSDL) files describe Boundary-scan capable devices in a standard format used by automated test-generation software. The order and function of bits in the Boundary-scan Data Register are included in this description. BSDL files are available for

Atmel ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P.

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25.8

Register description

25.8.1

MCUCR – MCU Control Register

The MCU Control Register contains control bits for general MCU functions.

Bit

0x35 (0x55)

Read/Write

Initial Value

7

JTD

R/W

0

6

BODS

(1)

R/W

0

5

BODSE

(1)

R/W

0

4

PUD

R/W

0

3

R

0

2

R

0

1

IVSEL

R/W

0

Note: 1. Only available in the Atmel ATmega164PA/324PA/644PA/1284P.

25.8.2

0

IVCE

R/W

0

MCUCR

• Bits 7 – JTD: JTAG Interface Disable

When this bit is zero, the JTAG interface is enabled if the JTAGEN Fuse is programmed. If this bit is one, the JTAG interface is disabled. In order to avoid unintentional disabling or enabling of the JTAG interface, a timed sequence must be followed when changing this bit: The application software must write this bit to the desired value twice within four cycles to change its value. Note that this bit must not be altered when using the On-chip Debug system.

MCUSR – MCU Status Register

The MCU Status Register provides information on which reset source caused an MCU reset.

Bit

0x34 (0x54)

Read/Write

Initial Value

R

0

7

R

0

6

R

0

5

4

JTRF

R/W

3

WDRF

2

BORF

1

EXTRF

R/W R/W

See Bit Description

R/W

0

PORF

R/W

MCUSR

• Bit 4 – JTRF: JTAG Reset Flag

This bit is set if a reset is being caused by a logic one in the JTAG Reset Register selected by the JTAG instruction AVR_RESET. This bit is reset by a Power-on Reset, or by writing a logic zero to the flag.

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26. Boot loader support – read-while-write self-programming

26.1

Features

Read-while-write self-programming

Flexible boot memory size

High security (separate Boot Lock bits for a flexible protection)

Separate fuse to select reset vector

Optimized page

(1)

size

Code efficient algorithm

Efficient read-modify-write support

Note: 1. A page is a section in the Flash consisting of several bytes (see

Table 27-7 on page 300 ) used

during programming. The page organization does not affect normal operation.

26.2

Overview

The Boot Loader Support provides a real Read-While-Write Self-Programming mechanism for downloading and uploading program code by the MCU itself. This feature allows flexible application software updates controlled by the MCU using a Flash-resident Boot Loader program. The

Boot Loader program can use any available data interface and associated protocol to read code and write (program) that code into the Flash memory, or read the code from the program memory. The program code within the Boot Loader section has the capability to write into the entire

Flash, including the Boot Loader memory. The Boot Loader can thus even modify itself, and it can also erase itself from the code if the feature is not needed anymore. The size of the Boot

Loader memory is configurable with fuses and the Boot Loader has two separate sets of Boot

Lock bits which can be set independently. This gives the user a unique flexibility to select different levels of protection.

26.3

Application and Boot Loader Flash Sections

26.3.1

26.3.2

The Flash memory is organized in two main sections, the Application section and the Boot

Loader section (see

Figure 26-2 on page 282 ). The size of the different sections is configured by

the BOOTSZ Fuses as shown in

Table 26-10 on page 292

and

Figure 26-2 on page 282

. These two sections can have different level of protection since they have different sets of Lock bits.

Application Section

The Application section is the section of the Flash that is used for storing the application code.

The protection level for the Application section can be selected by the application Boot Lock bits

(Boot Lock bits 0), see Table 26-2 on page 283 . The Application section can never store any

Boot Loader code since the SPM instruction is disabled when executed from the Application section.

BLS – Boot Loader Section

While the Application section is used for storing the application code, the The Boot Loader software must be located in the BLS since the SPM instruction can initiate a programming when executing from the BLS only. The SPM instruction can access the entire Flash, including the

BLS itself. The protection level for the Boot Loader section can be selected by the Boot Loader

Lock bits (Boot Lock bits 1), see Table 26-3 on page 283

.

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26.4

Read-While-Write and No Read-While-Write Flash Sections

26.4.1

26.4.2

Whether the CPU supports Read-While-Write or if the CPU is halted during a Boot Loader software update is dependent on which address that is being programmed. In addition to the two sections that are configurable by the BOOTSZ Fuses as described above, the Flash is also divided into two fixed sections, the Read-While-Write (RWW) section and the No Read-While-

Write (NRWW) section. The limit between the RWW- and NRWW sections is given in Table 26-

1

and Figure 26-1 on page 281

. The main difference between the two sections is:

• When erasing or writing a page located inside the RWW section, the NRWW section can be read during the operation

• When erasing or writing a page located inside the NRWW section, the CPU is halted during the entire operation

Note that the user software can never read any code that is located inside the RWW section during a Boot Loader software operation. The syntax “Read-While-Write section” refers to which section that is being programmed (erased or written), not which section that actually is being read during a Boot Loader software update.

RWW – Read-While-Write Section

If a Boot Loader software update is programming a page inside the RWW section, it is possible to read code from the Flash, but only code that is located in the NRWW section. During an ongoing programming, the software must ensure that the RWW section never is being read. If the user software is trying to read code that is located inside the RWW section (that is, by load program memory, call, or jump instructions or an interrupt) during programming, the software might end up in an unknown state. To avoid this, the interrupts should either be disabled or moved to the Boot Loader section. The Boot Loader section is always located in the NRWW section. The

RWW Section Busy bit (RWWSB) in the Store Program Memory Control and Status Register

(SPMCSR) will be read as logical one as long as the RWW section is blocked for reading. After a programming is completed, the RWWSB must be cleared by software before reading code located in the RWW section.

See Section “26.9.1” on page 295 for details on how to clear

RWWSB.

NRWW – No Read-While-Write Section

The code located in the NRWW section can be read when the Boot Loader software is updating a page in the RWW section. When the Boot Loader code updates the NRWW section, the CPU is halted during the entire Page Erase or Page Write operation.

Table 26-1.

Read-while-write features.

Which section does the Z-pointer address during the programming?

RWW Section

NRWW Section

Which section can be read during programming?

NRWW Section

None

Is the CPU halted?

No

Yes

Read-while-write supported?

Yes

No

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Figure 26-1.

Read-While-Write vs. No Read-While-Write.

Read-While-Write

(RWW) Section

Z-pointer

Addresses RWW

Section

Code Located in

NRWW Section

Can be Read During the Operation

No Read-While-Write

(NRWW) Section

Z-pointer

Addresses NRWW

Section

CPU is Halted

During the Operation

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Figure 26-2.

Memory sections.

Program Memory

BOOTSZ = '11'

0x0000

Program Memory

BOOTSZ = '10'

0x0000

Application Flash Section Application Flash Section

End RWW

Start NRWW

Application Flash Section

Boot Loader Flash Section

Program Memory

BOOTSZ = '01'

End Application

Start Boot Loader

Flashend

0x0000

Application Flash Section

End RWW

Start NRWW

Application Flash Section

Boot Loader Flash Section

End Application

Start Boot Loader

Flashend

Program Memory

BOOTSZ = '00'

0x0000

Application Flash Section

Application Flash Section

Boot Loader Flash Section

End RWW

Start NRWW

End Application

Start Boot Loader

Flashend

Boot Loader Flash Section

End RWW, End Application

Start NRWW, Start Boot Loader

Flashend

Note: 1. The parameters in the figure above are given in

Table 26-10 on page 292 .

26.5

Boot Loader Lock Bits

If no Boot Loader capability is needed, the entire Flash is available for application code. The

Boot Loader has two separate sets of Boot Lock bits which can be set independently. This gives the user a unique flexibility to select different levels of protection.

The user can select:

• To protect the entire Flash from a software update by the MCU

• To protect only the Boot Loader Flash section from a software update by the MCU

• To protect only the Application Flash section from a software update by the MCU

• Allow software update in the entire Flash

See Table 26-2 on page 283

and

Table 26-3 on page 283 for further details. The Boot Lock bits

can be set in software and in Serial or Parallel Programming mode, but they can be cleared by a

Chip Erase command only. The general Write Lock (Lock Bit mode 2) does not allow the programming of the Flash memory by SPM instruction. Similarly, the general Read/Write Lock

(Lock Bit mode 3) does not allow reading nor writing by (E)LPM/SPM, if it is attempted.

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Table 26-2.

Boot Lock Bit0 protection modes (application section)

(1)

.

BLB0 Mode

1

2

3

4

BLB02 BLB01 Protection

1

1

1

0

No restrictions for SPM or (E)LPM accessing the Application section.

SPM is not allowed to write to the Application section.

0

0

0

1

SPM is not allowed to write to the Application section, and

(E)LPM executing from the Boot Loader section is not allowed to read from the Application section. If Interrupt Vectors are placed in the Boot Loader section, interrupts are disabled while executing from the Application section.

(E)LPM executing from the Boot Loader section is not allowed to read from the Application section. If Interrupt Vectors are placed in the Boot Loader section, interrupts are disabled while executing from the Application section.

Note: 1. “1” means unprogrammed, “0” means programmed

.

Table 26-3.

Boot Lock Bit1 protection modes (boot loader section)

(1)

.

BLB1 Mode

1

2

3

4

BLB12 BLB11 Protection

1

1

1

0

No restrictions for SPM or (E)LPM accessing the Boot Loader section.

SPM is not allowed to write to the Boot Loader section.

0

0

0

1

SPM is not allowed to write to the Boot Loader section, and

(E)LPM executing from the Application section is not allowed to read from the Boot Loader section. If Interrupt Vectors are placed in the Application section, interrupts are disabled while executing from the Boot Loader section.

(E)LPM executing from the Application section is not allowed to read from the Boot Loader section. If Interrupt Vectors are placed in the Application section, interrupts are disabled while executing from the Boot Loader section.

Note: 1. “1” means unprogrammed, “0” means programmed.

26.6

Entering the Boot Loader Program

Entering the Boot Loader takes place by a jump or call from the application program. This may be initiated by a trigger such as a command received via USART, or SPI interface. Alternatively, the Boot Reset Fuse can be programmed so that the Reset Vector is pointing to the Boot Flash start address after a reset. In this case, the Boot Loader is started after a reset. After the application code is loaded, the program can start executing the application code. Note that the fuses cannot be changed by the MCU itself. This means that once the Boot Reset Fuse is programmed, the Reset Vector will always point to the Boot Loader Reset and the fuse can only be changed through the serial or parallel programming interface.

Table 26-4.

Boot Reset fuse

(1)

.

BOOTRST

1

0

Reset address

Reset Vector = Application Reset (address 0x0000)

Reset Vector = Boot Loader Reset (see Table 26-10 on page 292 )

Note: 1. “1” means unprogrammed, “0” means programmed.

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26.7

Addressing the Flash During Self-Programming

The Z-pointer is used to address the SPM commands. The Z pointer consists of the Z-registers

ZL and ZH in the register file, and RAMPZ in the I/O space. The number of bits actually used is implementation dependent. Note that the RAMPZ register is only implemented when the program space is larger than 64K bytes.

Bit

RAMPZ

ZH (R31)

ZL (R30)

23

15

RAMPZ7

Z15

Z7

7

22

14

RAMPZ6

Z14

Z6

6

21

13

RAMPZ5

Z13

Z5

5

20

12

RAMPZ4

Z12

Z4

4

19

11

RAMPZ3

Z11

Z3

3

18

10

RAMPZ2

Z10

Z2

2

17

9

RAMPZ1

Z9

Z1

1

16

8

RAMPZ0

Z8

Z0

0

Since the Flash is organized in pages (see

Table 27-7 on page 300 ), the Program Counter can

be treated as having two different sections. One section, consisting of the least significant bits, is addressing the words within a page, while the most significant bits are addressing the pages.

This is shown in

Figure 26-3 . Note that the Page Erase and Page Write operations are

addressed independently. Therefore it is of major importance that the Boot Loader software addresses the same page in both the Page Erase and Page Write operation. Once a programming operation is initiated, the address is latched and the Z-pointer can be used for other operations.

The LPM instruction use the Z-pointer to store the address. Since this instruction addresses the

Flash byte-by-byte, also bit Z0 of the Z-pointer is used.

Figure 26-3.

Addressing the flash during SPM

(1)

.

BIT

Z - REGISTER

15 ZPCMSB ZPAGEMSB 1 0

0

PROGRAM

COUNTER

PCMSB

PCPAGE

PAGE ADDRESS

WITHIN THE FLASH

PROGRAM MEMORY

PAGE

PAGEMSB

PCWORD

WORD ADDRESS

WITHIN A PAGE

PAGE

INSTRUCTION WORD

PCWORD[PAGEMSB:0]:

00

01

02

PAGEEND

Note: 1. The different variables used in

Figure 26-3

are listed in

Table 26-12 on page 292 .

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26.8

Self-Programming the Flash

26.8.1

The program memory is updated in a page by page fashion. Before programming a page with the data stored in the temporary page buffer, the page must be erased. The temporary page buffer is filled one word at a time using SPM and the buffer can be filled either before the Page

Erase command or between a Page Erase and a Page Write operation:

Alternative 1, fill the buffer before a Page Erase

• Fill temporary page buffer

• Perform a Page Erase

• Perform a Page Write

Alternative 2, fill the buffer after Page Erase

• Perform a Page Erase

• Fill temporary page buffer

• Perform a Page Write

If only a part of the page needs to be changed, the rest of the page must be stored (for example in the temporary page buffer) before the erase, and then be rewritten. When using alternative 1, the Boot Loader provides an effective Read-Modify-Write feature which allows the user software to first read the page, do the necessary changes, and then write back the modified data. If alternative 2 is used, it is not possible to read the old data while loading since the page is already erased. The temporary page buffer can be accessed in a random sequence. It is essential that the page address used in both the Page Erase and Page Write operation is addressing the same page. See

”Simple Assembly Code Example for a Boot Loader” on page 289 for an assembly

code example.

Performing Page Erase by SPM

26.8.2

To execute Page Erase, set up the address in the Z-pointer, write “X0000011” to SPMCSR and execute SPM within four clock cycles after writing SPMCSR. The data in R1 and R0 is ignored.

The page address must be written to PCPAGE in the Z-register. Other bits in the Z-pointer will be ignored during this operation.

• Page Erase to the RWW section: The NRWW section can be read during the Page Erase

• Page Erase to the NRWW section: The CPU is halted during the operation

Note: If an interrupt accurs in the time sequence, the four cycle access cannot be guaranteed. In order to ensure atomic operation, you should disable interrupts before writing to SPMCSR.

Filling the Temporary Buffer (Page Loading)

To write an instruction word, set up the address in the Z-pointer and data in R1:R0, write

“00000001” to SPMCSR and execute SPM within four clock cycles after writing SPMCSR. The content of PCWORD in the Z-register is used to address the data in the temporary buffer. The temporary buffer will auto-erase after a Page Write operation or by writing the RWWSRE bit in

SPMCSR. It is also erased after a system reset. Note that it is not possible to write more than one time to each address without erasing the temporary buffer.

If the EEPROM is written in the middle of an SPM Page Load operation, all data loaded will be lost.

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26.8.3

26.8.4

26.8.5

26.8.6

26.8.7

Performing a Page Write

To execute Page Write, set up the address in the Z-pointer, write “X0000101” to SPMCSR and execute SPM within four clock cycles after writing SPMCSR. The data in R1 and R0 is ignored.

The page address must be written to PCPAGE. Other bits in the Z-pointer must be written to zero during this operation.

• Page Write to the RWW section: The NRWW section can be read during the Page Write

• Page Write to the NRWW section: The CPU is halted during the operation

Using the SPM Interrupt

If the SPM interrupt is enabled, the SPM interrupt will generate a constant interrupt when the

SPMEN bit in SPMCSR is cleared. This means that the interrupt can be used instead of polling the SPMCSR Register in software. When using the SPM interrupt, the Interrupt Vectors should be moved to the BLS section to avoid that an interrupt is accessing the RWW section when it is blocked for reading. How to move the interrupts is described in

”Interrupts” on page 61

.

Consideration While Updating BLS

Special care must be taken if the user allows the Boot Loader section to be updated by leaving

Boot Lock bit11 unprogrammed. An accidental write to the Boot Loader itself can corrupt the entire Boot Loader, and further software updates might be impossible. If it is not necessary to change the Boot Loader software itself, it is recommended to program the Boot Lock bit11 to protect the Boot Loader software from any internal software changes.

Prevent Reading the RWW Section During Self-Programming

During Self-Programming (either Page Erase or Page Write), the RWW section is always blocked for reading. The user software itself must prevent that this section is addressed during the self programming operation. The RWWSB in the SPMCSR will be set as long as the RWW section is busy. During Self-Programming the Interrupt Vector table should be moved to the BLS as described in

”Interrupts” on page 61 , or the interrupts must be disabled. Before addressing

the RWW section after the programming is completed, the user software must clear the

RWWSB by writing the RWWSRE. See

”Simple Assembly Code Example for a Boot Loader” on page 289

for an example.

Setting the Boot Loader Lock Bits by SPM

To set the Boot Loader Lock bits and general lock bits, write the desired data to R0, write

“X0001001” to SPMCSR and execute SPM within four clock cycles after writing SPMCSR.

Bit

R0

7

1

6

1

5

BLB12

4

BLB11

3

BLB02

2

BLB01

1

LB2

0

LB1

See

Table 26-2 and Table 26-3 for how the different settings of the Boot Loader bits affect the

Flash access.

If bits 5..0 in R0 are cleared (zero), the corresponding Boot Lock bit will be programmed if an

SPM instruction is executed within four cycles after BLBSET and SPMEN are set in SPMCSR.

The Z-pointer is don’t care during this operation, but for future compatibility it is recommended to load the Z-pointer with 0x0001 (same as used for reading the lO ck

bits). For future compatibility it is also recommended to set bits 7 and 6 in R0 to “1” when writing the Lock bits. When programming the Lock bits the entire Flash can be read during the operation.

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26.8.8

EEPROM Write Prevents Writing to SPMCSR

Note that an EEPROM write operation will block all software programming to Flash. Reading the

Fuses and Lock bits from software will also be prevented during the EEPROM write operation. It is recommended that the user checks the status bit (EEPE) in the EECR Register and verifies that the bit is cleared before writing to the SPMCSR Register.

Reading the Fuse and Lock Bits from Software 26.8.9

It is possible to read both the Fuse and Lock bits from software. To read the Lock bits, load the

Z-pointer with 0x0001 and set the BLBSET and SPMEN bits in SPMCSR. When an (E)LPM instruction is executed within three CPU cycles after the BLBSET and SPMEN bits are set in

SPMCSR, the value of the Lock bits will be loaded in the destination register. The BLBSET and

SPMEN bits will auto-clear upon completion of reading the Lock bits or if no (E)LPM instruction is executed within three CPU cycles or no SPM instruction is executed within four CPU cycles.

When BLBSET and SPMEN are cleared, (E)LPM will work as described in the Instruction set

Manual.

Bit

Rd

7

6

5

BLB12

4

BLB11

3

BLB02

2

BLB01

1

LB2

0

LB1

The algorithm for reading the Fuse Low byte is similar to the one described above for reading the Lock bits. To read the Fuse Low byte, load the Z-pointer with 0x0000 and set the BLBSET and SPMEN bits in SPMCSR. When an (E)LPM instruction is executed within three cycles after the BLBSET and SPMEN bits are set in the SPMCSR, the value of the Fuse Low byte (FLB) will be loaded in the destination register as shown below. Refer to

Table 27-5 on page 299 for a

detailed description and mapping of the Fuse Low byte.

Bit

Rd

7

FLB7

6

FLB6

5

FLB5

4

FLB4

3

FLB3

2

FLB2

1

FLB1

0

FLB0

Similarly, when reading the Fuse High byte, load 0x0003 in the Z-pointer. When an (E)LPM instruction is executed within three cycles after the BLBSET and SPMEN bits are set in the

SPMCSR, the value of the Fuse High byte (FHB) will be loaded in the destination register as

shown below. Refer to Table 27-4 on page 299

for detailed description and mapping of the Fuse

High byte.

Bit

Rd

7

FHB7

6

FHB6

5

FHB5

4

FHB4

3

FHB3

2

FHB2

1

FHB1

0

FHB0

When reading the Extended Fuse byte, load 0x0002 in the Z-pointer. When an (E)LPM instruction is executed within three cycles after the BLBSET and SPMEN bits are set in the SPMCSR, the value of the Extended Fuse byte (EFB) will be loaded in the destination register as shown

below. Refer to Table 27-3 on page 298

for detailed description and mapping of the Extended

Fuse byte.

Bit

Rd

7

6

5

4

3

2

EFB2

1

EFB1

0

EFB0

Fuse and Lock bits that are programmed, will be read as zero. Fuse and Lock bits that are unprogrammed, will be read as one.

26.8.10

Reading the Signature Row from Software

To read the Signature Row from software, load the Z-pointer with the signature byte address given in

Table 26-5 on page 288 and set the SIGRD and SPMEN bits in SPMCSR. When an

LPM instruction is executed within three CPU cycles after the SIGRD and SPMEN bits are set in

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SPMCSR, the signature byte value will be loaded in the destination register. The SIGRD and

SPMEN bits will auto-clear upon completion of reading the Signature Row Lock bits or if no LPM instruction is executed within three CPU cycles. When SIGRD and SPMEN are cleared, LPM will work as described in the Instruction set Manual.

Table 26-5.

Signature Row addressing.

Signature byte

Device Signature Byte 1

Device Signature Byte 2

Device Signature Byte 3

RC Oscillator Calibration Byte

Z-Pointer address

0x0000

0x0002

0x0004

0x0001

Note: All other addresses are reserved for future use.

26.8.11

Preventing Flash Corruption

During periods of low V

CC

, the Flash program can be corrupted because the supply voltage is too low for the CPU and the Flash to operate properly. These issues are the same as for board level systems using the Flash, and the same design solutions should be applied.

A Flash program corruption can be caused by two situations when the voltage is too low. First, a regular write sequence to the Flash requires a minimum voltage to operate correctly. Secondly, the CPU itself can execute instructions incorrectly, if the supply voltage for executing instructions is too low.

Flash corruption can easily be avoided by following these design recommendations (one is sufficient):

1. If there is no need for a Boot Loader update in the system, program the Boot Loader Lock bits to prevent any Boot Loader software updates.

2. Keep the AVR RESET active (low) during periods of insufficient power supply voltage.

This can be done by enabling the internal Brown-out Detector (BOD) if the operating voltage matches the detection level. If not, an external low V

CC

reset protection circuit can be used. If a reset occurs while a write operation is in progress, the write operation will be completed provided that the power supply voltage is sufficient.

3. Keep the AVR core in Power-down sleep mode during periods of low V

CC

. This will prevent the CPU from attempting to decode and execute instructions, effectively protecting the SPMCSR Register and thus the Flash from unintentional writes.

26.8.12

Programming Time for Flash when Using SPM

The calibrated RC Oscillator is used to time Flash accesses. Table 26-6 on page 288

shows the typical programming time for Flash accesses from the CPU.

Table 26-6.

SPM programming time

(1)

.

Symbol

Flash write (Page Erase, Page Write, and write Lock bits by SPM)

Min. programming time

3.7ms

Max. programming time

4.5ms

Note: 1. Minimum and maximum programming times is per individual operation.

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26.8.13

Simple Assembly Code Example for a Boot Loader

;-the routine writes one page of data from RAM to Flash

; the first data location in RAM is pointed to by the Y pointer

; the first data location in Flash is pointed to by the Z-pointer

;-error handling is not included

;-the routine must be placed inside the Boot space

; (at least the Do_spm sub routine). Only code inside NRWW section can

; be read during Self-Programming (Page Erase and Page Write).

;-registers used: r0, r1, temp1 (r16), temp2 (r17), looplo (r24),

; loophi (r25), spmcrval (r20)

; storing and restoring of registers is not included in the routine

; register usage can be optimized at the expense of code size

;-It is assumed that either the interrupt table is moved to the Boot

; loader section or that the interrupts are disabled.

.equ PAGESIZEB = PAGESIZE*2 ;PAGESIZEB is page size in BYTES, not words

.org SMALLBOOTSTART

Write_page:

; Page Erase ldi spmcrval, (1<<PGERS) | (1<<SPMEN) call Do_spm

; re-enable the RWW section ldi spmcrval, (1<<RWWSRE) | (1<<SPMEN) call Do_spm

; transfer data from RAM to Flash page buffer ldi looplo, low(PAGESIZEB) ;init loop variable ldi loophi, high(PAGESIZEB) ;not required for PAGESIZEB<=256

Wrloop: ld r0, Y+ ld r1, Y+ ldi spmcrval, (1<<SPMEN) call Do_spm adiw ZH:ZL, 2 sbiw loophi:looplo, 2 brne Wrloop

;use subi for PAGESIZEB<=256

; execute Page Write subi ZL, low(PAGESIZEB) ;restore pointer sbci ZH, high(PAGESIZEB) ;not required for PAGESIZEB<=256 ldi spmcrval, (1<<PGWRT) | (1<<SPMEN) call Do_spm

; re-enable the RWW section ldi spmcrval, (1<<RWWSRE) | (1<<SPMEN) call Do_spm

; read back and check, optional ldi looplo, low(PAGESIZEB) ;init loop variable ldi loophi, high(PAGESIZEB) ;not required for PAGESIZEB<=256 subi YL, low(PAGESIZEB) ;restore pointer sbci YH, high(PAGESIZEB)

Rdloop: lpm r0, Z+ ld r1, Y+ cpse r0, r1 jmp Error

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sbiw loophi:looplo, 1 brne Rdloop

;use subi for PAGESIZEB<=256

; return to RWW section

; verify that RWW section is safe to read

Return: in temp1, SPMCSR sbrs temp1, RWWSB ; If RWWSB is set, the RWW section is not ready yet ret

; re-enable the RWW section ldi spmcrval, (1<<RWWSRE) | (1<<SPMEN) call Do_spm rjmp Return

Do_spm:

; check for previous SPM complete

Wait_spm: in temp1, SPMCSR sbrc temp1, SPMEN rjmp Wait_spm

; input: spmcrval determines SPM action

; disable interrupts if enabled, store status in temp2, SREG cli

; check that no EEPROM write access is present

Wait_ee: sbic EECR, EEPE rjmp Wait_ee

; SPM timed sequence out SPMCSR, spmcrval spm

; restore SREG (to enable interrupts if originally enabled) out SREG, temp2 ret

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26.8.14

Atmel ATmega164A/ATmega164PA Boot Loader Parameters

In Table 26-7 through Table 26-9 , the parameters used in the description of the Self-Programming are given.

Table 26-7.

Boot size configuration

(1)

.

BOOTSZ1 BOOTSZ0 Boot size

1 1 128 words

1 0 256 words

0

0

1

0

512 words

1024 words

Pages

2

4

8

16

Application flash section

0x0000 - 0x1F7F

0x0000 - 0x1EFF

0x0000 - 0x1DFF

0x0000 - 0x1BFF

Boot loader flash section

0x1F80 - 0x1FFF

0x1F00 - 0x1FFF

0x1E00 - 0x1FFF

0x1C00 - 0x1FFF

End application section

0x1F7F

0x1EFF

0x1DFF

0x1BFF

Boot reset address

(start boot loader section)

0x1F80

0x1F00

0x1E00

0x1C00

Note:

1. The different BOOTSZ Fuse configurations are shown in Figure 26-2 on page 282 .

Table 26-8.

Read-While-Write limit

(1)

.

Section

Read-While-Write section (RWW)

No Read-While-Write section (NRWW)

Pages

112

16

Address

0x0000 - 0x1BFF

0x1C00 - 0x1FFF

Note:

1. For details about these two section, see ”NRWW – No Read-While-Write Section” on page 280 and ”RWW – Read-While-

Write Section” on page 280 .

Table 26-9.

Explanation of different variables used in Figure 26-3 on page 284 and the mapping to the Z-pointer.

Variable

Corresponding

Z-value

PCMSB

PAGEMSB

ZPCMSB

ZPAGEMSB

PCPAGE

PCWORD

12

5

PC[12:6]

PC[5:0]

Z13

Z6

Z14:Z7

Z6:Z1

Description

(1)

Most significant bit in the Program Counter. (The Program Counter is 13 bits

PC[12:0])

Most significant bit which is used to address the words within one page (128 words in a page requires seven bits PC [5:0]).

Bit in Z-pointer that is mapped to PCMSB. Because Z0 is not used, the

ZPCMSB equals PCMSB + 1.

Bit in Z-pointer that is mapped to PCMSB. Because Z0 is not used, the

ZPAGEMSB equals PAGEMSB + 1.

Program Counter page address: Page select, for Page Erase and Page Write

Program Counter word address: Word select, for filling temporary buffer (must be zero during Page Write operation)

Note: 1. Z0: should be zero for all SPM commands, byte select for the (E)LPM instruction.

See

”Addressing the Flash During Self-Programming” on page 284

for details about the use of Z-pointer during Self-

Programming.

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26.8.15

Atmel ATmega324A/ATmega324PA Boot Loader Parameters

In

Table 26-10 through Table 26-12 , the parameters used in the description of the Self-Programming are given.

Table 26-10.

Boot size configuration

(1)

.

BOOTSZ1 BOOTSZ0 Boot size

1 1 256 words

1 0 512 words

0

0

1

0

1024 words

2048 words

Pages

4

8

16

32

Application flash section

0x0000 - 0x3EFF

0x0000 - 0x1DFF

0x0000 - 0x1BFF

0x0000 - 0x37FF

Boot loader flash section

0x3F00 - 0x3FFF

0x3E00 - 0x3FFF

0x3C00 - 0x3FFF

0x3800 - 0x3FFF

End application section

0x3EFF

0x3DFF

0x3BFF

0x37FF

Boot reset address

(start boot loader section)

0x3F00

0x3E00

0x3C00

0x3800

Note:

1. The different BOOTSZ Fuse configurations are shown in Figure 26-2 on page 282 .

Table 26-11.

Read-While-Write limit

(1)

.

Section

Read-While-Write section (RWW)

No Read-While-Write section (NRWW)

Pages

224

32

Address

0x0000 - 0x37FF

0x3800 - 0x3FFF

Note:

1. For details about these two section, see ”NRWW – No Read-While-Write Section” on page 280 and ”RWW – Read-While-

Write Section” on page 280 .

Table 26-12.

Explanation of different variables used in Figure 26-3 on page 284 and the mapping to the Z-pointer.

Variable

Corresponding

Z-value

PCMSB

PAGEMSB

ZPCMSB

ZPAGEMSB

PCPAGE

PCWORD

13

6

PC[13:6]

PC[5:0]

Z14

Z7

Z14:Z7

Z6:Z1

Description

(1)

Most significant bit in the Program Counter. (The Program Counter is 14 bits

PC[13:0])

Most significant bit which is used to address the words within one page (128 words in a page requires seven bits PC [5:0]).

Bit in Z-pointer that is mapped to PCMSB. Because Z0 is not used, the

ZPCMSB equals PCMSB + 1.

Bit in Z-pointer that is mapped to PCMSB. Because Z0 is not used, the

ZPAGEMSB equals PAGEMSB + 1.

Program Counter page address: Page select, for Page Erase and Page Write

Program Counter word address: Word select, for filling temporary buffer (must be zero during Page Write operation)

Note: 1. Z0: should be zero for all SPM commands, byte select for the (E)LPM instruction.

See

”Addressing the Flash During Self-Programming” on page 284

for details about the use of Z-pointer during Self-

Programming.

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26.8.16

Atmel ATmega644A/ATmega644PA Boot Loader parameters

In

Table 26-13 through Table 26-15 , the parameters used in the description of the Self-Programming are given.

Table 26-13.

Boot size configuration

(1)

.

BOOTSZ1 BOOTSZ0 Boot size

1 1 512 words

1 0 1024 words

0

0

1

0

2048 words

4096 words

Pages

4

8

16

32

Application flash section

0x0000 - 0x7DFF

0x0000 - 0x7BFF

0x0000 - 0x77FF

0x0000 - 0x6FFF

Boot loader flash section

0x7E00 - 0x7FFF

0x7C00 - 0x7FFF

0x7800 - 0x7FFF

0x7000 - 0x7FFF

End application section

0x7DFF

0x7BFF

0x77FF

0x6FFF

Boot reset address

(start boot loader section)

0x7E00

0x7C00

0x7800

0x7000

Note:

1. The different BOOTSZ Fuse configurations are shown in Figure 26-2 on page 282 .

Table 26-14.

Read-While-Write limit

(1)

.

Section

Read-While-Write section (RWW)

No Read-While-Write section (NRWW)

Pages

224

32

Address

0x0000 - 0x6FFF

0x7000 - 0x7FFF

Note:

1. For details about these two section, see ”NRWW – No Read-While-Write Section” on page 280 and ”RWW – Read-While-

Write Section” on page 280 .

Table 26-15.

Explanation of different variables used in Figure 26-3 on page 284 and the mapping to the Z-pointer.

Variable

Corresponding

Z-value

PCMSB

PAGEMSB

ZPCMSB

ZPAGEMSB

PCPAGE

PCWORD

14

7

PC[14:7]

PC[6:0]

Z15

Z8

Z15:Z7

Z7:Z1

Description

(1)

Most significant bit in the Program Counter. (The Program Counter is 14 bits

PC[14:0])

Most significant bit which is used to address the words within one page (128 words in a page requires seven bits PC [6:0]).

Bit in Z-pointer that is mapped to PCMSB. Because Z0 is not used, the

ZPCMSB equals PCMSB + 1.

Bit in Z-pointer that is mapped to PCMSB. Because Z0 is not used, the

ZPAGEMSB equals PAGEMSB + 1.

Program Counter page address: Page select, for Page Erase and Page Write

Program Counter word address: Word select, for filling temporary buffer (must be zero during Page Write operation)

Note: 1. Z0: should be zero for all SPM commands, byte select for the (E)LPM instruction.

See

”Addressing the Flash During Self-Programming” on page 284

for details about the use of Z-pointer during Self-

Programming.

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26.8.17

Atmel ATmega1284/ATmega1284P Boot Loader parameters

In Table 26-16 through Table 26-18 , the parameters used in the description of the Self-Programming are given.

Table 26-16.

Boot size configuration

(1)

.

BOOTSZ1 BOOTSZ0 Boot size

1 1 512 words

1 0 1024 words

0

0

1

0

2048 words

4096 words

Pages

4

8

16

32

Application flash section

Boot loader flash section

End application section

0x0000 - 0xFDFF 0xFE00 - 0xFFFF 0xFDFF

0x0000 - 0xFBFF 0xFC00 - 0xFFFF 0xFBFF

0x0000 - 0xF7FF 0xF800 - 0xFFFF 0xF7FF

0x0000 - 0xEFFF 0xF000 - 0xFFFF 0xEFFF

Boot reset address

(start boot loader section)

0xFE00

0xFC00

0xF800

0xF000

Note:

1. The different BOOTSZ Fuse configurations are shown in Figure 26-2 on page 282 .

Table 26-17.

Read-While-Write limit

(1)

.

Section

Read-While-Write section (RWW)

No Read-While-Write section (NRWW)

Pages

480

32

Address

0x0000 - 0xEFFF

0xF000 - 0xFFFF

Note:

1. For details about these two section, see ”NRWW – No Read-While-Write Section” on page 280 and ”RWW – Read-While-

Write Section” on page 280 .

Table 26-18.

Explanation of different variables used in Figure 26-3 on page 284 and the mapping to the Z-pointer.

Variable

Corresponding

Z-value

PCMSB

PAGEMSB

ZPCMSB

ZPAGEMSB

PCPAGE

PCWORD

15

6

PC[15:7]

PC[6:0]

Z16

Z7

Z16:Z8

Z7:Z1

Description

(1)

Most significant bit in the Program Counter. (The Program Counter is 16 bits

PC[15:0])

Most significant bit which is used to address the words within one page (128 words in a page requires seven bits PC [6:0]).

Bit in Z-pointer that is mapped to PCMSB. Because Z0 is not used, the ZPCMSB equals PCMSB + 1.

Bit in Z-pointer that is mapped to PCMSB. Because Z0 is not used, the

ZPAGEMSB equals PAGEMSB + 1.

Program Counter page address: Page select, for Page Erase and Page Write

Program Counter word address: Word select, for filling temporary buffer (must be zero during Page Write operation)

Note: 1. Z0: should be zero for all SPM commands, byte select for the (E)LPM instruction.

See

”Addressing the Flash During Self-Programming” on page 284 for details about the use of Z-pointer during Self-

Programming.

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26.9

Register description

26.9.1

SPMCSR – Store Program Memory Control and Status Register

The Store Program Memory Control and Status Register contains the control bits needed to control the Boot Loader operations.

Bit

0x37 (0x57)

Read/Write

Initial Value

7

SPMIE

R/W

0

6

RWWSB

R

0

5

SIGRD

R/W

0

4

RWWSRE

R/W

0

3

BLBSET

R/W

0

2

PGWRT

R/W

0

1

PGERS

R/W

0

0

SPMEN

R/W

0

SPMCSR

• Bit 7 – SPMIE: SPM Interrupt Enable

When the SPMIE bit is written to one, and the I-bit in the Status Register is set (one), the SPM ready interrupt will be enabled. The SPM ready Interrupt will be executed as long as the SPMEN bit in the SPMCSR Register is cleared.

• Bit 6 – RWWSB: Read-While-Write Section Busy

When a Self-Programming (Page Erase or Page Write) operation to the RWW section is initiated, the RWWSB will be set (one) by hardware. When the RWWSB bit is set, the RWW section cannot be accessed. The RWWSB bit will be cleared if the RWWSRE bit is written to one after a

Self-Programming operation is completed. Alternatively the RWWSB bit will automatically be cleared if a page load operation is initiated.

• Bit 5 – SIGRD: Signature Row Read

If this bit is written to one at the same time as SPMEN, the next LPM instruction within three

clock cycles will read a byte from the signature row into the destination register. see ”Reading the Signature Row from Software” on page 287 for details. An SPM instruction within four cycles

after SIGRD and SPMEN are set will have no effect. This operation is reserved for future use and should not be used.

• Bit 4 – RWWSRE: Read-While-Write Section Read Enable

When programming (Page Erase or Page Write) to the RWW section, the RWW section is blocked for reading (the RWWSB will be set by hardware). To re-enable the RWW section, the user software must wait until the programming is completed (SPMEN will be cleared). Then, if the RWWSRE bit is written to one at the same time as SPMEN, the next SPM instruction within four clock cycles re-enables the RWW section. The RWW section cannot be re-enabled while the Flash is busy with a Page Erase or a Page Write (SPMEN is set). If the RWWSRE bit is written while the Flash is being loaded, the Flash load operation will abort and the data loaded will be lost.

• Bit 3 – BLBSET: Boot Lock Bit Set

If this bit is written to one at the same time as SPMEN, the next SPM instruction within four clock cycles sets Boot Lock bits, according to the data in R0. The data in R1 and the address in the Zpointer are ignored. The BLBSET bit will automatically be cleared upon completion of the Lock bit set, or if no SPM instruction is executed within four clock cycles.

An (E)LPM instruction within three cycles after BLBSET and SPMEN are set in the SPMCSR

Register, will read either the Lock bits or the Fuse bits (depending on Z0 in the Z-pointer) into the

destination register. See ”Reading the Fuse and Lock Bits from Software” on page 287

for details.

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• Bit 2 – PGWRT: Page Write

If this bit is written to one at the same time as SPMEN, the next SPM instruction within four clock cycles executes Page Write, with the data stored in the temporary buffer. The page address is taken from the high part of the Z-pointer. The data in R1 and R0 are ignored. The PGWRT bit will auto-clear upon completion of a Page Write, or if no SPM instruction is executed within four clock cycles. The CPU is halted during the entire Page Write operation if the NRWW section is addressed.

• Bit 1 – PGERS: Page Erase

If this bit is written to one at the same time as SPMEN, the next SPM instruction within four clock cycles executes Page Erase. The page address is taken from the high part of the Z-pointer. The data in R1 and R0 are ignored. The PGERS bit will auto-clear upon completion of a Page Erase, or if no SPM instruction is executed within four clock cycles. The CPU is halted during the entire

Page Write operation if the NRWW section is addressed.

• Bit 0 – SPMEN: Store Program Memory Enable

This bit enables the SPM instruction for the next four clock cycles. If written to one together with either RWWSRE, BLBSET, PGWRT’ or PGERS, the following SPM instruction will have a special meaning, see description above. If only SPMEN is written, the following SPM instruction will store the value in R1:R0 in the temporary page buffer addressed by the Z-pointer. The LSB of the Z-pointer is ignored. The SPMEN bit will auto-clear upon completion of an SPM instruction, or if no SPM instruction is executed within four clock cycles. During Page Erase and Page Write, the SPMEN bit remains high until the operation is completed.

Writing any other combination than “10001”, “01001”, “00101”, “00011”, or “00001” in the lower five bits will have no effect.

Note: Only one SPM instruction should be active at any time.

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ATmega164A/PA/324A/PA/644A/PA/1284/P

27. Memory programming

27.1

Program And Data Memory Lock Bits

The Atmel ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P provides six Lock bits which can be left unprogrammed (“1”) or can be programmed (“0”) to obtain the additional fea-

tures listed in Table 27-2

. The Lock bits can only be erased to “1” with the Chip Erase command.

Table 27-1.

Lock Bit byte

(1)

.

Lock Bit byte

BLB12

BLB11

BLB02

BLB01

LB2

LB1

Bit no.

7

6

3

2

5

4

1

0

Description

Boot Lock bit

Boot Lock bit

Boot Lock bit

Boot Lock bit

Lock bit

Lock bit

Default value

1 (unprogrammed)

1 (unprogrammed)

1 (unprogrammed)

1 (unprogrammed)

1 (unprogrammed)

1 (unprogrammed)

1 (unprogrammed)

1 (unprogrammed)

Note: 1. “1” means unprogrammed, “0” means programmed

.

Table 27-2.

Lock Bit protection modes

(1)(2)

.

Memory Lock bits

LB Mode

1

LB2

1

LB1

1

Protection type

2

3

1

0

0

0

No memory lock features enabled.

Further programming of the Flash and EEPROM is disabled in

Parallel and Serial Programming mode. The Fuse bits are

locked in both Serial and Parallel Programming mode.

(1)

Further programming and verification of the Flash and EEPROM is disabled in Parallel, JTAG and Serial Programming mode. The

Boot Lock bits and Fuse bits are locked in both Serial and

Parallel Programming mode.

(1)

BLB0 Mode BLB02 BLB01

1

2

3

4

1

1

0

0

1

0

0

1

No restrictions for SPM or (E)LPM accessing the Application section.

SPM is not allowed to write to the Application section.

SPM is not allowed to write to the Application section, and

(E)LPM executing from the Boot Loader section is not allowed to read from the Application section. If Interrupt Vectors are placed in the Boot Loader section, interrupts are disabled while executing from the Application section.

(E)LPM executing from the Boot Loader section is not allowed to read from the Application section. If Interrupt Vectors are placed in the Boot Loader section, interrupts are disabled while executing from the Application section.

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Fuse bits

ATmega164A/PA/324A/PA/644A/PA/1284/P

Table 27-2.

Lock Bit protection modes

(1)(2)

. (Continued)

Memory Lock bits

BLB1 Mode BLB12 BLB11

Protection type

1

2

3

1

1

0

1

0

0

No restrictions for SPM or (E)LPM accessing the Boot Loader section.

SPM is not allowed to write to the Boot Loader section.

SPM is not allowed to write to the Boot Loader section, and

(E)LPM executing from the Application section is not allowed to read from the Boot Loader section. If Interrupt Vectors are placed in the Application section, interrupts are disabled while executing from the Boot Loader section.

4 0 1

(E)LPM executing from the Application section is not allowed to read from the Boot Loader section. If Interrupt Vectors are placed in the Application section, interrupts are disabled while executing from the Boot Loader section.

Notes: 1. Program the Fuse bits and Boot Lock bits before programming the LB1 and LB2.

2. “1” means unprogrammed, “0” means programmed.

The Atmel ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P has four Fuse bytes.

Table 27-3 -

Table 27-5 describe briefly the functionality of all the fuses and how they are

mapped into the Fuse bytes. Note that the fuses are read as logical zero, “0”, if they are programmed.

Table 27-3.

Extended Fuse byte

Fuse low byte

BODLEVEL2

(1)

BODLEVEL1

(1)

BODLEVEL0

(1)

3

2

5

4

1

0

7

Bit no.

Description

6 –

Brown-out Detector trigger level

Brown-out Detector trigger level

Brown-out Detector trigger level

Note: 1. See

”” on page 336

for BODLEVEL Fuse decoding.

Default value

1

1

1

1

1

1 (unprogrammed)

1 (unprogrammed)

1 (unprogrammed)

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Table 27-4.

Fuse High byte.

Fuse High byte

OCDEN

JTAGEN

SPIEN

WDTON

EESAVE

(4)

(1)

(3)

BOOTSZ1

BOOTSZ0

Bit no.

Description

7

6

5

4

3

2

1

Enable OCD

Enable JTAG

Enable Serial Program and Data

Downloading

Watchdog Timer always on

EEPROM memory is preserved through the Chip Erase

Select Boot Size (see Table 27-9 on page 302 for details)

Select Boot Size (see Table 27-9 on page 302 for details)

Select Reset Vector

Default value

1 (unprogrammed, OCD disabled)

0 (programmed, JTAG enabled)

0 (programmed, SPI prog. enabled)

1 (unprogrammed)

1 (unprogrammed, EEPROM not preserved)

0 (programmed)

0 (programmed)

(2)

(2)

BOOTRST 0 1 (unprogrammed)

Note: 1. The SPIEN Fuse is not accessible in serial programming mode.

2. The default value of BOOTSZ1..0 results in maximum Boot Size. See

Table 26-10 on page

292 for details.

3. See

”WDTCSR – Watchdog Timer Control Register” on page 59

for details.

4. Never ship a product with the OCDEN Fuse programmed regardless of the setting of Lock bits and JTAGEN Fuse. A programmed OCDEN Fuse enables some parts of the clock system to be running in all sleep modes. This may increase the power consumption.

Table 27-5.

Fuse Low byte.

Fuse Low byte

CKDIV8

(4)

CKOUT

(3)

SUT1

SUT0

CKSEL3

CKSEL2

CKSEL1

CKSEL0

2

1

4

3

0

Bit no.

Description

7 Divide clock by 8

6

5

Clock output

Select start-up time

Select start-up time

Select Clock source

Select Clock source

Select Clock source

Select Clock source

Default value

0 (programmed)

1 (unprogrammed)

1 (unprogrammed)

(1)

0 (programmed)

(1)

0 (programmed)

(2)

0 (programmed)

(2)

1 (unprogrammed)

(2)

0 (programmed)

(2)

Note: 1. The default value of SUT1..0 results in maximum start-up time for the default clock source.

See

”” on page 336

for details.

2. The default setting of CKSEL3..0 results in internal RC Oscillator @ 8MHz. See

Table 9-1 on page 31 for details.

3. The CKOUT Fuse allow the system clock to be output on PORTB1. See

”Clock Output Buffer” on page 39

for details.

4. See

”System Clock Prescaler” on page 39 for details.

The status of the Fuse bits is not affected by Chip Erase. Note that the Fuse bits are locked if

Lock bit1 (LB1) is programmed. Program the Fuse bits before programming the Lock bits.

299

ATmega164A/PA/324A/PA/644A/PA/1284/P

27.2.1

Latching of Fuses

The fuse values are latched when the device enters programming mode and changes of the fuse values will have no effect until the part leaves Programming mode. This does not apply to the EESAVE Fuse which will take effect once it is programmed. The fuses are also latched on

Power-up in Normal mode.

27.3

Signature Bytes

All Atmel microcontrollers have a three-byte signature code which identifies the device. This code can be read in both serial and parallel mode, also when the device is locked. The three bytes reside in a separate address space.

For the Atmel ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P the signature bytes

are given in Table 27-6 .

Table 27-6.

Device and JTAG ID.

Part

ATmega164A

ATmega164PA

ATmega324A

ATmega324PA

ATmega644A

ATmega644PA

ATmega1284

ATmega1284P

Signature bytes address

0x000

0x1E

0x1E

0x001

0x94

0x94

0x002

0x0F

0x0A

0x1E

0x1E

0x1E

0x1E

0x1E

0x1E

0x95

0x95

0x96

0x96

0x97

0x97

0x15

0x11

0x09

0x0A

0x06

0x05

Part number

940A

940A

9511

9511

960A

960A

9705

9705

JTAG

Manufacture ID

0x1F

0x1F

0x1F

0x1F

0x1F

0x1F

0x1F

0x1F

27.4

Calibration byte

The ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P has a byte calibration value for the internal RC Oscillator. This byte resides in the high byte of address 0x000 in the signature address space. During reset, this byte is automatically written into the OSCCAL Register to ensure correct frequency of the calibrated RC Oscillator.

27.5

Page Size

Table 27-7.

Number of words in a page and number of pages in the flash.

Device

ATmega164A/ATmega164PA

ATmega324A/ATmega324PA

ATmega644A/ATmega644PA

ATmega1284/ATmega1284P

Flash size

8K words (16KBytes)

16K words (32KBytes)

32K words (64KBytes)

64K words (128KBytes)

Page size

64 words

64 words

128 words

128 words

PCWORD No. of pages

PC[5:0] 128

PC[5:0]

PC[6:0]

PC[6:0]

256

256

512

PCPAGE

PC[12:6]

PC[13:6]

PC[14:6]

PC[15:7]

PCMSB

12

13

14

15

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Table 27-8.

Number of words in a page and number of pages in the EEPROM.

Device EEPROM size Page size PCWORD No. of pages

ATmega164A/ATmega164PA

ATmega324A/ATmega324PA

ATmega644A/ATmega644PA

ATmega1284/ATmega1284P

512bytes

1KBytes

2KBytes

4KBytes

4 bytes

4 bytes

8 bytes

8 bytes

EEA[1:0]

EEA[1:0]

EEA[2:0]

EEA[2:0]

128

256

256

512

PCPAGE

EEA[8:2]

EEA[9:2]

EEA[10:2]

EEA[11:3]

EEAMSB

8

9

10

11

27.6

Parallel Programming Parameters, Pin Mapping, and Commands

This section describes how to parallel program and verify Flash Program memory, EEPROM

Data memory, Memory Lock bits, and Fuse bits in the Atmel

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P. Pulses are assumed to be at least

250ns unless otherwise noted.

27.6.1

Signal Names

In this section, some pins of the ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P are referenced by signal names describing their functionality during parallel programming, see

Figure 27-1

and Figure 27-9 on page 302

. Pins not described in the following table are referenced by pin names.

The XA1/XA0 pins determine the action executed when the XTAL1 pin is given a positive pulse.

The bit coding is shown in Table 27-12 on page 302 .

When pulsing WR or OE, the command loaded determines the action executed. The different

commands are shown in Table 27-13 on page 303 .

Figure 27-1.

Parallel programming

(1)

.

+5V

RDY/BSY

OE

WR

BS1

XA0

XA1

PAGEL

+12 V

BS2

PD1

PD2

PD3

PD4

PD5

PD6

PD7

RESET

PA0

XTAL1

GND

VCC

AVCC

PB7 - PB0

+5V

DATA

Note: 1. Unused Pins should be left floating.

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Table 27-9.

Pin name mapping.

Signal name in programming mode Pin name

RDY/BSY

OE

WR

BS1

XA0

XA1

PAGEL

BS2

DATA

PD1

PD2

PD3

PD4

PD5

PD6

PD7

PA0

PB7-0

I

I

I

I

I/O Function

O

0: Device is busy programming, 1: Device is ready for new command.

Output Enable (Active low).

Write Pulse (Active low).

Byte Select 1.

XTAL Action Bit 0

I

I XTAL Action Bit 1

Program Memory and EEPROM data Page Load.

I Byte Select 2.

I/O Bi-directional Data bus (Output when OE is low).

Table 27-10.

BS2 and BS1 encoding.

BS2

0

0

1

BS1

0

1

0

Flash / EEPROM address

Low Byte

High Byte

Extended High

Byte

Flash data loading / reading

Low Byte

High Byte

Reserved

1 1 Reserved Reserved Reserved

,

Table 27-11.

Pin values used to enter Programming mode.

Pin

PAGEL

XA1

XA0

BS1

Symbol

Prog_enable[3]

Prog_enable[2]

Prog_enable[1]

Prog_enable[0]

Fuse programming

Low Byte

High Byte

Extended Byte

Reading fuse and lock bits

Fuse Low Byte

Lockbits

Extended Fuse

Byte

Fuse High Byte

Value

0

0

0

0

Table 27-12.

XA1 and XA0 enoding.

XA1

0

0

1

1

XA0

0

1

0

1

Action when XTAL1 is pulsed

Load Flash or EEPROM Address (High or low address byte determined by BS2 and BS1)

Load Data (High or Low data byte for Flash determined by BS1)

Load Command

No Action, Idle

302

ATmega164A/PA/324A/PA/644A/PA/1284/P

Table 27-13.

Command byte bit encoding.

Command byte

1000 0000

0100 0000

0010 0000

0001 0000

0001 0001

0000 1000

0000 0100

0000 0010

0000 0011

Command executed

Chip Erase

Write Fuse bits

Write Lock bits

Write Flash

Write EEPROM

Read Signature Bytes and Calibration byte

Read Fuse and Lock bits

Read Flash

Read EEPROM

27.7

Parallel programming

27.7.1

27.7.2

27.7.3

Enter Programming mode

The following algorithm puts the device in parallel programming mode:

1. Apply 4.5 - 5.5V between V

CC

and GND.

2. Set RESET to “0” and toggle XTAL1 at least six times.

3. Set the Prog_enable pins listed in

Table 27-11 on page 302

to “0000” and wait at least

100ns.

4. Apply 11.5 - 12.5V to RESET. Any activity on Prog_enable pins within 100ns after +12V has been applied to RESET, will cause the device to fail entering programming mode.

5. Wait at least 50µs before sending a new command.

Considerations for Efficient Programming

The loaded command and address are retained in the device during programming. For efficient programming, the following should be considered.

• The command needs only be loaded once when writing or reading multiple memory locations

• Skip writing the data value 0xFF, that is the contents of the entire EEPROM (unless the

EESAVE Fuse is programmed) and Flash after a Chip Erase

• Address high byte needs only be loaded before programming or reading a new 256 word window in Flash or 256 byte EEPROM. This consideration also applies to Signature bytes reading

Chip Erase

The Chip Erase will erase the Flash and EEPROM

(1)

memories plus Lock bits. The Lock bits are not reset until the program memory has been completely erased. The Fuse bits are not changed. A Chip Erase must be performed before the Flash and/or EEPROM are reprogrammed.

Note: 1. The EEPRPOM memory is preserved during Chip Erase if the EESAVE Fuse is programmed.

Load Command “Chip Erase”

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27.7.4

1. Set XA1, XA0 to “10”. This enables command loading.

2. Set BS1 to “0”.

3. Set DATA to “1000 0000”. This is the command for Chip Erase.

4. Give XTAL1 a positive pulse. This loads the command.

5. Give WR a negative pulse. This starts the Chip Erase. RDY/BSY goes low.

6. Wait until RDY/BSY goes high before loading a new command.

Programming the Flash

The Flash is organized in pages, see

Table 27-7 on page 300 . When programming the Flash,

the program data is latched into a page buffer. This allows one page of program data to be programmed simultaneously. The following procedure describes how to program the entire Flash memory:

A. Load Command “Write Flash”

1. Set XA1, XA0 to “10”. This enables command loading.

2. Set BS1 to “0”.

3. Set DATA to “0001 0000”. This is the command for Write Flash.

4. Give XTAL1 a positive pulse. This loads the command.

B. Load Address Low byte (Address bits 7..0)

1. Set XA1, XA0 to “00”. This enables address loading.

2. Set BS2, BS1 to “00”. This selects the address low byte.

3. Set DATA = Address low byte (0x00 - 0xFF).

4. Give XTAL1 a positive pulse. This loads the address low byte.

C. Load Data Low Byte

1. Set XA1, XA0 to “01”. This enables data loading.

2. Set DATA = Data low byte (0x00 - 0xFF).

3. Give XTAL1 a positive pulse. This loads the data byte.

D. Load Data High Byte

1. Set BS1 to “1”. This selects high data byte.

2. Set XA1, XA0 to “01”. This enables data loading.

3. Set DATA = Data high byte (0x00 - 0xFF).

4. Give XTAL1 a positive pulse. This loads the data byte.

E. Latch Data

1. Set BS1 to “1”. This selects high data byte.

2. Give PAGEL a positive pulse. This latches the data bytes. (See

Figure 27-3 on page 306

for signal waveforms)

F. Repeat B through E until the entire buffer is filled or until all data within the page is loaded.

While the lower bits in the address are mapped to words within the page, the higher bits address the pages within the FLASH. This is illustrated in

Figure 27-2 on page 305

. Note that if less than eight bits are required to address words in the page (pagesize < 256), the most significant bit(s) in the address low byte are used to address the page when performing a Page Write.

G. Load Address High byte (Address bits15..8)

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1. Set XA1, XA0 to “00”. This enables address loading.

2. Set BS2, BS1 to “01”. This selects the address high byte.

3. Set DATA = Address high byte (0x00 - 0xFF).

4. Give XTAL1 a positive pulse. This loads the address high byte.

H. Load Address Extended High byte (Address bits 23..16)

1. Set XA1, XA0 to “00”. This enables address loading.

2. Set BS2, BS1 to “10”. This selects the address extended high byte.

3. Set DATA = Address extended high byte (0x00 - 0xFF).

4. Give XTAL1 a positive pulse. This loads the address high byte.

I. Program Page

1. Set BS2, BS1 to “00”.

2. Give WR a negative pulse. This starts programming of the entire page of data. RDY/BSY goes low.

3. Wait until RDY/BSY goes high (See Figure 27-3 on page 306 for signal waveforms).

J. Repeat B through I until the entire Flash is programmed or until all data has been programmed.

K. End Page Programming

1. 1. Set XA1, XA0 to “10”. This enables command loading.

2. Set DATA to “0000 0000”. This is the command for No Operation.

3. Give XTAL1 a positive pulse. This loads the command, and the internal write signals are reset.

Figure 27-2.

Addressing the flash, which is organized in pages

(1)

.

PROGRAM

COUNTER

PCMSB

PCPAGE

PAGEMSB

PCWORD

PAGE ADDRESS

WITHIN THE FLASH

WORD ADDRESS

WITHIN A PAGE

PROGRAM MEMORY

PAGE

PAGE

INSTRUCTION WORD

PCWORD[PAGEMSB:0]:

00

01

02

PAGEEND

Note: 1. PCPAGE and PCWORD are listed in

Table 27-7 on page 300 .

305

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 27-3.

Programming the flash waveforms

(1)

.

F

A

0x10

B

ADDR. LOW

C

DATA LOW

D

DATA HIGH

E

XX

B C

ADDR. LOW DATA LOW

D

DATA HIGH

E

XX

G H

ADDR. HIGH ADDR. EXT.H

I

XX

BS2

XTAL1

WR

RDY/BSY

RESET +12V

OE

PAGEL

DATA

XA1

XA0

BS1

Note: 1. “XX” is don’t care. The letters refer to the programming description above.

27.7.5

Programming the EEPROM

The EEPROM is organized in pages, see Table 27-8 on page 301

. When programming the

EEPROM, the program data is latched into a page buffer. This allows one page of data to be programmed simultaneously. The programming algorithm for the EEPROM data memory is as follows (refer to

”Programming the Flash” on page 304

for details on Command, Address and

Data loading):

1. A: Load Command “0001 0001”.

2. G: Load Address High Byte (0x00 - 0xFF).

3. B: Load Address Low Byte (0x00 - 0xFF).

4. C: Load Data (0x00 - 0xFF).

5. E: Latch data (give PAGEL a positive pulse).

K: Repeat 3 through 5 until the entire buffer is filled.

L: Program EEPROM page.

1. Set BS2, BS1 to “00”.

2. Give WR a negative pulse. This starts programming of the EEPROM page. RDY/BSY goes low.

3. Wait until to RDY/BSY goes high before programming the next page (See

Figure 27-4 on page 307

for signal waveforms).

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27.7.6

27.7.7

27.7.8

Figure 27-4.

Programming the EEPROM waveforms.

K

A

0x11

G

ADDR. HIGH

B

ADDR. LOW

C

DATA

E

XX

B

ADDR. LOW

C

DATA

E

XX

L

Reading the Flash

XTAL1

WR

RDY/BSY

RESET +12V

OE

PAGEL

BS2

DATA

XA1

XA0

BS1

The algorithm for reading the Flash memory is as follows (refer to

”Programming the Flash” on page 304

for details on Command and Address loading):

1. A: Load Command “0000 0010”.

2. H: Load Address Extended Byte (0x00- 0xFF).

3. G: Load Address High Byte (0x00 - 0xFF).

4. B: Load Address Low Byte (0x00 - 0xFF).

5. Set OE to “0”, and BS1 to “0”. The Flash word low byte can now be read at DATA.

6. Set BS to “1”. The Flash word high byte can now be read at DATA.

7. Set OE to “1”.

Reading the EEPROM

The algorithm for reading the EEPROM memory is as follows (refer to

”Programming the Flash” on page 304 for details on Command and Address loading):

1. A: Load Command “0000 0011”.

2. G: Load Address High Byte (0x00 - 0xFF).

3. B: Load Address Low Byte (0x00 - 0xFF).

4. Set OE to “0”, and BS1 to “0”. The EEPROM Data byte can now be read at DATA.

5. Set OE to “1”.

Programming the Fuse Low Bits

The algorithm for programming the Fuse Low bits is as follows (refer to

”Programming the Flash” on page 304 for details on Command and Data loading):

1. A: Load Command “0100 0000”.

2. C: Load Data Low Byte. Bit n = “0” programs and bit n = “1” erases the Fuse bit.

3. Give WR a negative pulse and wait for RDY/BSY to go high.

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27.7.9

Programming the Fuse High Bits

The algorithm for programming the Fuse High bits is as follows (refer to

”Programming the

Flash” on page 304 for details on Command and Data loading):

1. A: Load Command “0100 0000”.

2. C: Load Data Low Byte. Bit n = “0” programs and bit n = “1” erases the Fuse bit.

3. Set BS2, BS1 to “01”. This selects high data byte.

4. Give WR a negative pulse and wait for RDY/BSY to go high.

5. Set BS2, BS1 to “00”. This selects low data byte.

27.7.10

Programming the Extended Fuse Bits

The algorithm for programming the Extended Fuse bits is as follows (refer to

”Programming the

Flash” on page 304 for details on Command and Data loading):

1. 1. A: Load Command “0100 0000”.

2. 2. C: Load Data Low Byte. Bit n = “0” programs and bit n = “1” erases the Fuse bit.

3. 3. Set BS2, BS1 to “10”. This selects extended data byte.

4. 4. Give WR a negative pulse and wait for RDY/BSY to go high.

5. 5. Set BS2, BS1 to “00”. This selects low data byte.

Figure 27-5.

Programming the FUSES waveforms.

Write Fuse Low byte Write Fuse high byte

A

0x40

C

DATA

A

0x40

C

DATA

DATA

XX XX

XA1

XTAL1

WR

RDY/BSY

RESET +12V

OE

PAGEL

XA0

BS1

BS2

A

0x40

C

DATA

Write Extended Fuse byte

XX

27.7.11

Programming the Lock Bits

The algorithm for programming the Lock bits is as follows (refer to

”Programming the Flash” on page 304

for details on Command and Data loading):

1. A: Load Command “0010 0000”.

2. C: Load Data Low Byte. Bit n = “0” programs the Lock bit. If LB mode 3 is programmed

(LB1 and LB2 is programmed), it is not possible to program the Boot Lock bits by any

External Programming mode.

3. Give WR a negative pulse and wait for RDY/BSY to go high.

The Lock bits can only be cleared by executing Chip Erase.

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27.7.12

Reading the Fuse and Lock Bits

The algorithm for reading the Fuse and Lock bits is as follows (refer to ”Programming the Flash” on page 304 for details on Command loading):

1. A: Load Command “0000 0100”.

2. Set OE to “0”, and BS2, BS1 to “00”. The status of the Fuse Low bits can now be read at

DATA (“0” means programmed).

3. Set OE to “0”, and BS2, BS1 to “11”. The status of the Fuse High bits can now be read at

DATA (“0” means programmed).

4. Set OE to “0”, and BS2, BS1 to “10”. The status of the Extended Fuse bits can now be read at DATA (“0” means programmed).

5. Set OE to “0”, and BS2, BS1 to “01”. The status of the Lock bits can now be read at DATA

(“0” means programmed).

6. Set OE to “1”.

Figure 27-6.

Mapping between BS1, BS2 and the Fuse and Lock bits during read.

Fuse Low Byte

0

0

Extended Fuse Byte

1

DATA

BS2

Lock Bits

0

1

BS1

Fuse High Byte

1

BS2

27.7.13

Reading the Signature Bytes

The algorithm for reading the Signature bytes is as follows (refer to ”Programming the Flash” on page 304

for details on Command and Address loading):

1. A: Load Command “0000 1000”.

2. B: Load Address Low Byte (0x00 - 0x02).

3. Set OE to “0”, and BS to “0”. The selected Signature byte can now be read at DATA.

4. Set OE to “1”.

27.7.14

Reading the Calibration Byte

The algorithm for reading the Calibration byte is as follows (refer to ”Programming the Flash” on page 304

for details on Command and Address loading):

1. A: Load Command “0000 1000”.

2. B: Load Address Low Byte, 0x00.

3. Set OE to “0”, and BS1 to “1”. The Calibration byte can now be read at DATA.

4. Set OE to “1”.

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27.7.15

Parallel Programming Characteristics

Table 27-14.

Parallel programming characteristics, V

CC

= 5V ±10%.

Symbol Parameter Min.

Typ.

Max.

t

XLPH t

PLXH t

BVPH t

PHPL t

PLBX t

WLBX t

PLWL t

BVWL

V

PP

I

PP t

DVXH t

XLXH t

XHXL t

XLDX t

XLWL t

WLWH t

WLRL t

WLRH t

WLRH_CE t

XLOL t

BVDV t

OLDV t

OHDZ

Programming Enable Voltage

Programming Enable Current

Data and Control Valid before XTAL1 High

XTAL1 Low to XTAL1 High

XTAL1 Pulse Width High

Data and Control Hold after XTAL1 Low

XTAL1 Low to WR Low

XTAL1 Low to PAGEL high

PAGEL low to XTAL1 high

BS1 Valid before PAGEL High

PAGEL Pulse Width High

BS1 Hold after PAGEL Low

BS2/1 Hold after WR Low

PAGEL Low to WR Low

BS2/1 Valid to WR Low

WR Pulse Width Low

WR Low to RDY/BSY Low

WR Low to RDY/BSY High

(1)

WR Low to RDY/BSY High for Chip Erase

(2)

XTAL1 Low to OE Low

BS1 Valid to DATA valid

OE Low to DATA Valid

OE High to DATA Tri-stated

11.5

67

200

150

0

150

67

150

150

0

3.7

7.5

0

0

67

0

67

67

67

67

12.5

250

1

4.5

9

250

250

250

Notes: 1. t

WLRH is valid for the Write Flash, Write EEPROM, Write Fuse bits and Write Lock bits commands.

2. t

WLRH_CE is valid for the Chip Erase command.

Units

V

μA ns

μs ms ns

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Figure 27-7.

Parallel programming timing, including some general timing requirements.

t

XLWL

XTAL1 t

XHXL t

DVXH t

XLDX

Data & Contol

(DATA, XA0/1, BS1, BS2) t

BVPH t

PLBX t

BVWL t

WLBX

PAGEL t

PHPL t

WLWH

WR t

PLWL

WLRL

RDY/BSY t

WLRH

Figure 27-8.

Parallel programming timing, loading sequence with timing requirements

(1)

.

LOAD ADDRESS

(LOW BYTE)

LOAD DATA

(LOW BYTE) t

XLXH

LOAD DATA

(HIGH BYTE)

LOAD DATA t

XLPH t

PLXH

LOAD ADDRESS

(LOW BYTE)

XTAL1

BS1

PAGEL

DATA

ADDR0 (Low Byte) DATA (Low Byte) DATA (High Byte) ADDR1 (Low Byte)

XA0

XA1

Note: 1. The timing requirements shown in

Figure 27-7 (that is, t

DVXH loading operation.

, t

XHXL

, and t

XLDX

) also apply to

Figure 27-9.

Parallel programming timing, reading sequence (within the same page) with timing requirements

(1)

.

LOAD ADDRESS

(LOW BYTE) t

XLOL

READ DATA

(LOW BYTE)

READ DATA

(HIGH BYTE)

LOAD ADDRESS

(LOW BYTE)

XTAL1 t

BVDV

BS1 t

OLDV

OE

DATA ADDR0 (Low Byte) DATA (Low Byte) t

OHDZ

DATA (High Byte)

ADDR1 (Low Byte)

XA0

XA1

Note: 1. The timing requirements shown in

Figure 27-7 (that is, t

DVXH reading operation.

, t

XHXL

, and t

XLDX

) also apply to

311

ATmega164A/PA/324A/PA/644A/PA/1284/P

27.8

Serial downloading

27.8.1

Both the Flash and EEPROM memory arrays can be programmed using a serial programming bus while RESET is pulled to GND. The serial programming interface consists of pins SCK,

MOSI (input) and MISO (output). After RESET is set low, the Programming Enable instruction needs to be executed first before program/erase operations can be executed. NOTE, in

Table

27-15 , the pin mapping for serial programming is listed. Not all packages use the SPI pins dedi-

cated for the internal Serial Peripheral Interface - SPI.

Serial Programming Pin Mapping

Table 27-15.

Pin mapping serial programming.

Symbol

MOSI

MISO

SCK

Pins

(PDIP-40)

PB5

PB6

PB7

Pins

(TQFP/MLF-44)

PB5

PB6

PB7

Figure 27-10.

Serial programming and verify

(1)

.

I/O

I

O

I

Description

Serial Data in

Serial Data out

Serial Clock

+1.8 - 5.5V

VCC

+1.8 - 5.5V

(2)

MOSI

MISO

SCK

AVCC

XTAL1

RESET

GND

Notes: 1. If the device is clocked by the internal oscillator, it is no need to connect a clock source to the

XTAL1 pin.

2. V

CC

- 0.3V < AVCC < V

CC

+ 0.3V, however, AVCC should always be within 1.8 - 5.5V.

When programming the EEPROM, an auto-erase cycle is built into the self-timed programming operation (in the Serial mode ONLY) and there is no need to first execute the Chip Erase instruction. The Chip Erase operation turns the content of every memory location in both the

Program and EEPROM arrays into 0xFF.

Depending on CKSEL Fuses, a valid clock must be present. The minimum low and high periods for the serial clock (SCK) input are defined as follows:

Low: >2 CPU clock cycles for f ck

<12MHz, 3 CPU clock cycles for f ck

≥12MHz.

High: >2 CPU clock cycles for f ck

<12MHz, 3 CPU clock cycles for f ck

≥12MHz.

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27.8.2

Serial Programming Algorithm

When writing serial data to the Atmel

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P, data is clocked on the rising edge of SCK.

When reading data from the ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P, data is clocked on the falling edge of SCK. See

Figure 27-12 for timing details.

To program and verify the ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P in the serial programming mode, the following sequence is recommended (see four byte instruction formats in

Table 27-17

):

1. Power-up sequence:

Apply power between V

CC

and GND while RESET and SCK are set to “0”. In some systems, the programmer can not guarantee that SCK is held low during power-up. In this case, RESET must be given a positive pulse of at least two CPU clock cycles duration after SCK has been set to “0”.

2. Wait for at least 20ms and enable serial programming by sending the Programming

Enable serial instruction to pin MOSI.

3. The serial programming instructions will not work if the communication is out of synchronization. When in sync. the second byte (0x53), will echo back when issuing the third byte of the Programming Enable instruction. Whether the echo is correct or not, all four bytes of the instruction must be transmitted. If the 0x53 did not echo back, give RESET a positive pulse and issue a new Programming Enable command.

4. The Flash is programmed one page at a time. The memory page is loaded one byte at a time by supplying the seven LSB of the address and data together with the Load Program

Memory Page instruction. To ensure correct loading of the page, the data low byte must be loaded before data high byte is applied for a given address. The Program Memory

Page is stored by loading the Write Program Memory Page instruction with the address lines 15..8. Before issuing this command, make sure the instruction Load Extended

Address Byte has been used to define the MSB of the address. The extended address byte is stored until the command is re-issued, that is, the command needs only be issued for the first page, and when crossing the 64KWord boundary. If polling (

RDY/BSY

) is not used, the user must wait at least t

WD_FLASH

before issuing the next page. (See Table 27-

16

.) Accessing the serial programming interface before the Flash write operation completes can result in incorrect programming.

5. The EEPROM array is programmed one byte at a time by supplying the address and data together with the appropriate Write instruction. An EEPROM memory location is first automatically erased before new data is written. If polling is not used, the user must wait at least t

WD_EEPROM before issuing the next byte. (See

Table 27-16

device, no 0xFFs in the data file(s) need to be programmed.

.) In a chip erased

6. Any memory location can be verified by using the Read instruction which returns the content at the selected address at serial output MISO. When reading the Flash memory, use the instruction Load Extended Address Byte to define the upper address byte, which is not included in the Read Program Memory instruction. The extended address byte is stored until the command is re-issued, that is, the command needs only be issued for the first page, and when crossing the 64KWord boundary.

7. At the end of the programming session, RESET can be set high to commence normal operation.

8. Power-off sequence (if needed):

Set RESET to “1”.

Turn V

CC

power off.

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Table 27-16.

Minimum wait delay before writing the next flash or EEPROM location.

Symbol

t

WD_FLASH t

WD_EEPROM t

WD_ERASE

Minimum wait delay

4.5ms

3.6ms

9.0ms

27.9

Serial Programming Instruction set

Table 27-17 and

Figure 27-11 on page 315

describes the Instruction set.

Table 27-17.

Serial programming instruction set (hexadecimal values).

Instruction/operation

Programming Enable

Chip Erase (Program Memory/EEPROM)

Poll RDY/BSY

Load Instructions

Load Extended Address byte

(1)

Load Program Memory Page, High byte

Load Program Memory Page, Low byte

Load EEPROM Memory Page (page access)

Read Instructions

(5)

Read Program Memory, High byte

Read Program Memory, Low byte

Read EEPROM Memory

Read Lock bits

(3)

Read Signature Byte

Read Fuse bits

(3)

Read Fuse High bits

(3)

Read Extended Fuse Bits

(3)

Read Calibration Byte

Write Instructions

(5)

Write Program Memory Page

(6)

Write EEPROM Memory

Write EEPROM Memory Page (page access)

Write Lock bits

(3)(4)

Write Fuse bits

(3)(4)

Write Fuse High bits

(3)(4)

Write Extended Fuse Bits

(3)(4)

Byte 1

$AC

$AC

$F0

$4C

$C0

$C2

$AC

$AC

$AC

$AC

$28

$20

$A0

$58

$30

$50

$58

$50

$38

$4D

$48

$40

$C1

Instruction format

Byte 2

$53

$80

$00

Byte 3

$00

$00

$00

$00

$00

$00

$00 adr MSB adr MSB

0000 00aa

(2)

$00

$00

$00

$08

$08

$00 adr MSB

0000 00aa

(2)

0000 00aa

(2)

$E0

$A0

$A8

$A4

Extended adr adr LSB adr LSB

0000 000aa

(2)

adr LSB adr LSB

aaaa aaaa

(2)

$00

0000 000aa

(2)

$00

$00

$00

$00 adr LSB

aaaa aaaa

(2) aaaa aa00

(2)

$00

$00

$00

$00

Byte 4

$00

$00 data byte out

$00 high data byte in low data byte in data byte in high data byte out low data byte out data byte out data byte out data byte out data byte out data byte out data byte out data byte out

$00 data byte in

$00 data byte in data byte in data byte in data byte in

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Notes: 1. Not all instructions are applicable for all parts.

2. a = address.

3. Bits are programmed ‘0’, unprogrammed ‘1’.

4. To ensure future compatibility, unused Fuses and Lock bits should be unprogrammed (‘1’) .

5. Refer to the correspondig section for Fuse and Lock bits, Calibration and Signature bytes and

Page size.

6. Instructions accessing program memory use a word address. This address may be random within the page range.

Note: See http://www.atmel.com/avr for Application Notes regarding programming and programmers.

If the LSB in RDY/BSY data byte out is ‘1’, a programming operation is still pending. Wait until this bit returns ‘0’ before the next instruction is carried out.

Within the same page, the low data byte must be loaded prior to the high data byte.

After data is loaded to the page buffer, program the EEPROM page, see

Figure 27-11 .

Figure 27-11.

Serial programming instruction example.

Serial Programming Instruction

Load Program Memory Page (High/Low Byte)/

Load EEPROM Memory Page (page access)

Byte 1 Byte 2

Bit 15 B

A SB

Byte 3

Adr LSB

0

Byte 4

Write Program Memory Page/

Write EEPROM Memory Page

Byte 3 Byte 1 Byte 2

Bit 15 B

Adr MSB

0

Page Buffer

Byte 4

Page Offset

Page 0

Page 1

Page 2

Page Number

Page N-1

Program Memory/

EEPROM Memory

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27.9.1

Serial Programming Characteristics

For characteristics of the Serial Programming module see “SPI timing characteristics” on page

338 .

Figure 27-12.

Serial programming waveforms.

SERIAL DATA INPUT

(MOSI)

MSB LSB

SERIAL DATA OUTPUT

(MISO)

SERIAL CLOCK INPUT

(SCK)

SAMPLE

MSB LSB

27.10 Programming via the JTAG Interface

Programming through the JTAG interface requires control of the four JTAG specific pins: TCK,

TMS, TDI, and TDO. Control of the reset and clock pins is not required.

To be able to use the JTAG interface, the JTAGEN Fuse must be programmed. The device is default shipped with the fuse programmed. In addition, the JTD bit in MCUCR must be cleared.

Alternatively, if the JTD bit is set, the external reset can be forced low. Then, the JTD bit will be cleared after two chip clocks, and the JTAG pins are available for programming. This provides a means of using the JTAG pins as normal port pins in Running mode while still allowing In-System Programming via the JTAG interface. Note that this technique can not be used when using the JTAG pins for Boundary-scan or On-chip Debug. In these cases the JTAG pins must be dedicated for this purpose.

During programming the clock frequency of the TCK Input must be less than the maximum frequency of the chip. The System Clock Prescaler can not be used to divide the TCK Clock Input into a sufficiently low frequency.

As a definition in this datasheet, the LSB is shifted in and out first of all Shift Registers.

27.10.1

Programming Specific JTAG Instructions

The Instruction Register is 4-bit wide, supporting up to 16 instructions. The JTAG instructions useful for programming are listed below.

The OPCODE for each instruction is shown behind the instruction name in hex format. The text describes which Data Register is selected as path between TDI and TDO for each instruction.

The Run-Test/Idle state of the TAP controller is used to generate internal clocks. It can also be used as an idle state between JTAG sequences. The state machine sequence for changing the

instruction word is shown in Figure 27-13 on page 317 .

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Figure 27-13.

State machine sequence for changing the instruction word.

1 Test-Logic-Reset

0

0

Run-Test/Idle

1

Select-DR Scan

1

Select-IR Scan

1

0 0

1 1

Capture-DR

0

Shift-DR 0

Capture-IR

0

Shift-IR

0

0

1

Exit1-DR

0

Pause-DR

1

Exit2-DR

1

Update-DR

1

0

1

0

0

1

Exit1-IR

0

Pause-IR

1

Exit2-IR

1

Update-IR

1

0

1

0

27.10.2

AVR_RESET (0xC)

The AVR specific public JTAG instruction for setting the AVR device in the Reset mode or taking the device out from the Reset mode. The TAP controller is not reset by this instruction. The one bit Reset Register is selected as Data Register. Note that the reset will be active as long as there is a logic “one” in the Reset Chain. The output from this chain is not latched.

The active states are:

• Shift-DR: The Reset Register is shifted by the TCK input

27.10.3

PROG_ENABLE (0x4)

The AVR specific public JTAG instruction for enabling programming via the JTAG port. The 16bit Programming Enable Register is selected as Data Register. The active states are the following:

• Shift-DR: The programming enable signature is shifted into the Data Register

• Update-DR: The programming enable signature is compared to the correct value, and

Programming mode is entered if the signature is valid

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27.10.4

PROG_COMMANDS (0x5)

The AVR specific public JTAG instruction for entering programming commands via the JTAG port. The 15-bit Programming Command Register is selected as Data Register. The active states are the following:

• Capture-DR: The result of the previous command is loaded into the Data Register

• Shift-DR: The Data Register is shifted by the TCK input, shifting out the result of the previous command and shifting in the new command

• Update-DR: The programming command is applied to the Flash inputs

• Run-Test/Idle: One clock cycle is generated, executing the applied command

27.10.5

PROG_PAGELOAD (0x6)

The AVR specific public JTAG instruction to directly load the Flash data page via the JTAG port.

An 8-bit Flash Data Byte Register is selected as the Data Register. This is physically the eight

LSBs of the Programming Command Register. The active states are the following:

• Shift-DR: The Flash Data Byte Register is shifted by the TCK input

• Update-DR: The content of the Flash Data Byte Register is copied into a temporary register. A write sequence is initiated that within 11 TCK cycles loads the content of the temporary register into the Flash page buffer. The AVR automatically alternates between writing the low and the high byte for each new Update-DR state, starting with the low byte for the first Update-

DR encountered after entering the PROG_PAGELOAD command. The Program Counter is pre-incremented before writing the low byte, except for the first written byte. This ensures that the first data is written to the address set up by PROG_COMMANDS, and loading the last location in the page buffer does not make the program counter increment into the next page

27.10.6

PROG_PAGEREAD (0x7)

The AVR specific public JTAG instruction to directly capture the Flash content via the JTAG port.

An 8-bit Flash Data Byte Register is selected as the Data Register. This is physically the eight

LSBs of the Programming Command Register. The active states are the following:

27.10.7

Data Registers

• Capture-DR: The content of the selected Flash byte is captured into the Flash Data Byte

Register. The AVR automatically alternates between reading the low and the high byte for each new Capture-DR state, starting with the low byte for the first Capture-DR encountered after entering the PROG_PAGEREAD command. The Program Counter is post-incremented after reading each high byte, including the first read byte. This ensures that the first data is captured from the first address set up by PROG_COMMANDS, and reading the last location in the page makes the program counter increment into the next page

• Shift-DR: The Flash Data Byte Register is shifted by the TCK input

The Data Registers are selected by the JTAG instruction registers described in section

”Programming Specific JTAG Instructions” on page 316

. The Data Registers relevant for programming operations are:

• Reset Register

• Programming Enable Register

• Programming Command Register

• Flash Data Byte Register

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27.10.8

Reset Register

The Reset Register is a Test Data Register used to reset the part during programming. It is required to reset the part before entering Programming mode.

A high value in the Reset Register corresponds to pulling the external reset low. The part is reset as long as there is a high value present in the Reset Register. Depending on the Fuse settings

for the clock options, the part will remain reset for a Reset Time-out period (refer to ”Clock

Sources” on page 31 ) after releasing the Reset Register. The output from this Data Register is

not latched, so the reset will take place immediately, as shown in

Figure 25-2 on page 271

.

27.10.9

Programming Enable Register

The Programming Enable Register is a 16-bit register. The contents of this register is compared to the programming enable signature, binary code 0b1010_0011_0111_0000. When the contents of the register is equal to the programming enable signature, programming via the JTAG port is enabled. The register is reset to 0 on Power-on Reset, and should always be reset when leaving Programming mode.

Figure 27-14.

Programming enable register.

TDI

TDO

T

A

D

A

0xA370

=

D Q

Programming Enable

ClockDR & PROG_ENABLE

27.10.10 Programming Command Register

The Programming Command Register is a 15-bit register. This register is used to serially shift in programming commands, and to serially shift out the result of the previous command, if any. The

JTAG Programming Instruction Set is shown in

Table 27-18 on page 321

. The state sequence

when shifting in the programming commands is illustrated in Figure 27-16 on page 324 .

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Figure 27-15.

Programming command register.

TDI

R

E

S

S

/

A

D

D

D

A

T

A

S

T

R

O

B

E

S

Flash

EEPROM

Fuses

Lock Bits

TDO

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Table 27-18.

JTAG programming instruction.

Set

a

= address high bits, b = address low bits, c = address extended bits, H = 0 - Low byte, 1 - High Byte, o = data out,

i

= data in, x = don’t care.

Instruction Notes

1a. Chip Erase

1b. Poll for Chip Erase Complete

2a. Enter Flash Write

2b. Load Address Extended High Byte

2c. Load Address High Byte

2d. Load Address Low Byte

2e. Load Data Low Byte

2f. Load Data High Byte

2g. Latch Data

2h. Write Flash Page

2i. Poll for Page Write Complete

3a. Enter Flash Read

3b. Load Address Extended High Byte

3c. Load Address High Byte

3d. Load Address Low Byte

3e. Read Data Low and High Byte

4a. Enter EEPROM Write

4b. Load Address High Byte

4c. Load Address Low Byte

4d. Load Data Byte

4e. Latch Data

4f. Write EEPROM Page

4g. Poll for Page Write Complete

TDI sequence

0100011_10000000

0110001_10000000

0110011_10000000

0110011_10000000

0110011_10000000

0100011_00010000

0001011_cccccccc

0000111_aaaaaaaa

0000011_bbbbbbbb

0010011_iiiiiiii

0010111_iiiiiiii

0110111_00000000

1110111_00000000

0110111_00000000

0110111_00000000

0110101_00000000

0110111_00000000

0110111_00000000

0110111_00000000

0100011_00000010

0001011_cccccccc

0000111_aaaaaaaa

0000011_bbbbbbbb

0110010_00000000

0110110_00000000

0110111_00000000

0100011_00010001

0000111_aaaaaaaa

0000011_bbbbbbbb

0010011_iiiiiiii

0110111_00000000

1110111_00000000

0110111_00000000

0110011_00000000

0110001_00000000

0110011_00000000

0110011_00000000

0110011_00000000

TDO sequence

xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxox_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxox_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_oooooooo xxxxxxx_oooooooo xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxox_xxxxxxxx

(2)

(10)

(1)

(1)

(2)

(10)

Low byte

High byte

(10)

(1)

(1)

(2)

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Table 27-18.

JTAG programming instruction. (Continued)

Set (Continued)

a

= address high bits, b = address low bits, c = address extended bits, H = 0 - Low byte, 1 - High Byte,

o

= data out, i = data in, x = don’t care.

Notes Instruction

5a. Enter EEPROM Read

5b. Load Address High Byte

5c. Load Address Low Byte

5d. Read Data Byte

6a. Enter Fuse Write

6b. Load Data Low Byte

(6)

6c. Write Fuse Extended Byte

6d. Poll for Fuse Write Complete

6e. Load Data Low Byte

(7)

6f. Write Fuse High Byte

6g. Poll for Fuse Write Complete

6h. Load Data Low Byte

(7)

6i. Write Fuse Low Byte

6j. Poll for Fuse Write Complete

7a. Enter Lock Bit Write

7b. Load Data Byte

(9)

7c. Write Lock Bits

7d. Poll for Lock Bit Write complete

8a. Enter Fuse/Lock Bit Read

8b. Read Extended Fuse Byte

(6)

8c. Read Fuse High Byte

(7)

8d. Read Fuse Low Byte

(8)

TDI sequence

0100011_00000011

0000111_aaaaaaaa

0000011_bbbbbbbb

0110011_bbbbbbbb

0110010_00000000

0110011_00000000

0100011_01000000

0010011_iiiiiiii

0111011_00000000

0111001_00000000

0111011_00000000

0111011_00000000

0110111_00000000

0010011_iiiiiiii

0110111_00000000

0110101_00000000

0110111_00000000

0110111_00000000

0110111_00000000

0010011_iiiiiiii

0110011_00000000

0110001_00000000

0110011_00000000

0110011_00000000

0110011_00000000

0100011_00100000

0010011_11iiiiii

0110011_00000000

0110001_00000000

0110011_00000000

0110011_00000000

0110011_00000000

0100011_00000100

0111010_00000000

0111011_00000000

0111110_00000000

0111111_00000000

0110010_00000000

0110011_00000000

TDO sequence

xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_oooooooo xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxox_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxox_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxox_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxox_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_oooooooo xxxxxxx_xxxxxxxx xxxxxxx_oooooooo xxxxxxx_xxxxxxxx xxxxxxx_oooooooo

(10)

(3)

(1)

(2)

(3)

(1)

(2)

(3)

(1)

(2)

(4)

(1)

(2)

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Table 27-18.

JTAG programming instruction. (Continued)

Set (Continued)

a

= address high bits, b = address low bits, c = address extended bits, H = 0 - Low byte, 1 - High Byte,

o

= data out, i = data in, x = don’t care.

Instruction

8e. Read Lock Bits

(9)

8f. Read Fuses and Lock Bits

9a. Enter Signature Byte Read

9b. Load Address Byte

9c. Read Signature Byte

TDI sequence

0110110_00000000

0110111_00000000

0111010_00000000

0111110_00000000

0110010_00000000

0110110_00000000

0110111_00000000

0100011_00001000

0000011_bbbbbbbb

0110010_00000000

0110011_00000000

TDO sequence

xxxxxxx_xxxxxxxx xxxxxxx_xxoooooo xxxxxxx_xxxxxxxx xxxxxxx_oooooooo xxxxxxx_oooooooo xxxxxxx_oooooooo xxxxxxx_oooooooo xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx xxxxxxx_oooooooo

Notes

(5)

(5)

Fuse Ext. byte

Fuse High byte

Fuse Low byte

Lock bits

10a. Enter Calibration Byte Read

10b. Load Address Byte

0100011_00001000

0000011_bbbbbbbb xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx

10c. Read Calibration Byte

11a. Load No Operation Command

0110110_00000000

0110111_00000000

0100011_00000000

0110011_00000000 xxxxxxx_xxxxxxxx xxxxxxx_oooooooo xxxxxxx_xxxxxxxx xxxxxxx_xxxxxxxx

Notes: 1. This command sequence is not required if the seven MSB are correctly set by the previous command sequence (which is normally the case).

2. Repeat until o = “1”.

3. Set bits to “0” to program the corresponding Fuse, “1” to unprogram the Fuse.

4. Set bits to “0” to program the corresponding Lock bit, “1” to leave the Lock bit unchanged.

5. “0” = programmed, “1” = unprogrammed.

6. The bit mapping for Fuses Extended byte is listed in

Table 27-3 on page 298

.

7. The bit mapping for Fuses High byte is listed in

Table 27-4 on page 299 .

8. The bit mapping for Fuses Low byte is listed in

Table 27-5 on page 299 .

9. The bit mapping for Lock bits byte is listed in

Table 27-1 on page 297 .

10. Address bits exceeding PCMSB and EEAMSB (

Table 27-7 and

Table 27-8

) are don’t care.

11. All TDI and TDO sequences are represented by binary digits (0b...).

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Figure 27-16.

State machine sequence for changing/reading the data word.

1 Test-Logic-Reset

0

0

Run-Test/Idle

1

Select-DR Scan

1

0

Select-IR Scan

1

0

1

Capture-DR

1

0

Capture-IR

0

0

Shift-DR

1

Exit1-DR

0

Pause-DR

1

Exit2-DR

1

Update-DR

1 0

1

0

0

0

Shift-IR

1

Exit1-IR

0

Pause-IR

1

Exit2-IR

1

Update-IR

1 0

1

0

0

27.10.11 Flash Data Byte Register

The Flash Data Byte Register provides an efficient way to load the entire Flash page buffer before executing Page Write, or to read out/verify the content of the Flash. A state machine sets up the control signals to the Flash and senses the strobe signals from the Flash, thus only the data words need to be shifted in/out.

The Flash Data Byte Register actually consists of the 8-bit scan chain and a 8-bit temporary register. During page load, the Update-DR state copies the content of the scan chain over to the temporary register and initiates a write sequence that within 11 TCK cycles loads the content of the temporary register into the Flash page buffer. The AVR automatically alternates between writing the low and the high byte for each new Update-DR state, starting with the low byte for the first Update-DR encountered after entering the PROG_PAGELOAD command. The Program

Counter is pre-incremented before writing the low byte, except for the first written byte. This ensures that the first data is written to the address set up by PROG_COMMANDS, and loading the last location in the page buffer does not make the Program Counter increment into the next page.

During Page Read, the content of the selected Flash byte is captured into the Flash Data Byte

Register during the Capture-DR state. The AVR automatically alternates between reading the low and the high byte for each new Capture-DR state, starting with the low byte for the first Cap-

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ture-DR encountered after entering the PROG_PAGEREAD command. The Program Counter is post-incremented after reading each high byte, including the first read byte. This ensures that the first data is captured from the first address set up by PROG_COMMANDS, and reading the last location in the page makes the program counter increment into the next page.

Figure 27-17.

Flash data byte register.

STROBES

State

Machine

TDI

ADDRESS

Flash

EEPROM

Fuses

Lock Bits

D

A

T

A

TDO

The state machine controlling the Flash Data Byte Register is clocked by TCK. During normal operation in which eight bits are shifted for each Flash byte, the clock cycles needed to navigate through the TAP controller automatically feeds the state machine for the Flash Data Byte Register with sufficient number of clock pulses to complete its operation transparently for the user.

However, if too few bits are shifted between each Update-DR state during page load, the TAP controller should stay in the Run-Test/Idle state for some TCK cycles to ensure that there are at least 11 TCK cycles between each Update-DR state.

27.10.12 Programming Algorithm

All references below of type “1a”, “1b”, and so on, refer to

Table 27-18 on page 321

.

27.10.13 Entering Programming Mode

1. Enter JTAG instruction AVR_RESET and shift 1 in the Reset Register.

2. Enter instruction PROG_ENABLE and shift 0b1010_0011_0111_0000 in the Programming Enable Register.

27.10.14 Leaving Programming Mode

1. Enter JTAG instruction PROG_COMMANDS.

2. Disable all programming instructions by using no operation instruction 11a.

3. Enter instruction PROG_ENABLE and shift 0b0000_0000_0000_0000 in the programming Enable Register.

4. Enter JTAG instruction AVR_RESET and shift 0 in the Reset Register.

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27.10.15 Performing Chip Erase

1. Enter JTAG instruction PROG_COMMANDS.

2. Start Chip Erase using programming instruction 1a.

3. Poll for Chip Erase complete using programming instruction 1b, or wait for t

WLRH_CE

to Table 27-14 on page 310 ).

(refer

27.10.16 Programming the Flash

Before programming the Flash a Chip Erase must be performed,

see “Performing Chip Erase” on page 326 .

1. Enter JTAG instruction PROG_COMMANDS.

2. Enable Flash write using programming instruction 2a.

3. Load address Extended High byte using programming instruction 2b.

4. Load address High byte using programming instruction 2c.

5. Load address Low byte using programming instruction 2d.

6. Load data using programming instructions 2e, 2f, and 2g.

7. Repeat steps 5 and 6 for all instruction words in the page.

8. Write the page using programming instruction 2h.

9. Poll for Flash write complete using programming instruction 2i, or wait for t

WLRH

(refer to

Table 27-14 on page 310 ).

10. Repeat steps 3 to 9 until all data have been programmed.

A more efficient data transfer can be achieved using the PROG_PAGELOAD instruction:

1. Enter JTAG instruction PROG_COMMANDS.

2. Enable Flash write using programming instruction 2a.

3. Load the page address using programming instructions 2b, 2c, and 2d. PCWORD (refer

to Table 27-7 on page 300 ) is used to address within one page and must be written as 0.

4. Enter JTAG instruction PROG_PAGELOAD.

5. Load the entire page by shifting in all instruction words in the page byte-by-byte, starting with the LSB of the first instruction in the page and ending with the MSB of the last instruction in the page. Use Update-DR to copy the contents of the Flash Data Byte Register into the Flash page location and to auto-increment the Program Counter before each new word.

6. Enter JTAG instruction PROG_COMMANDS.

7. Write the page using programming instruction 2h.

8. Poll for Flash write complete using programming instruction 2i, or wait for t

WLRH

(refer to

Table 27-14 on page 310 ).

9. Repeat steps 3 to 8 until all data have been programmed.

27.10.17 Reading the Flash

1. Enter JTAG instruction PROG_COMMANDS.

2. Enable Flash read using programming instruction 3a.

3. Load address using programming instructions 3b, 3c, and 3d.

4. Read data using programming instruction 3e.

5. Repeat steps 3 and 4 until all data have been read.

A more efficient data transfer can be achieved using the PROG_PAGEREAD instruction:

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1. Enter JTAG instruction PROG_COMMANDS.

2. Enable Flash read using programming instruction 3a.

3. Load the page address using programming instructions 3b, 3c, and 3d. PCWORD (refer

to Table 27-7 on page 300 ) is used to address within one page and must be written as 0.

4. Enter JTAG instruction PROG_PAGEREAD.

5. Read the entire page (or Flash) by shifting out all instruction words in the page (or Flash), starting with the LSB of the first instruction in the page (Flash) and ending with the MSB of the last instruction in the page (Flash). The Capture-DR state both captures the data from the Flash, and also auto-increments the program counter after each word is read.

Note that Capture-DR comes before the shift-DR state. Hence, the first byte which is shifted out contains valid data.

6. Enter JTAG instruction PROG_COMMANDS.

7. Repeat steps 3 to 6 until all data have been read.

27.10.18 Programming the EEPROM

Before programming the EEPROM a Chip Erase must be performed,

See “Performing Chip

Erase” on page 326

.

1. Enter JTAG instruction PROG_COMMANDS.

2. Enable EEPROM write using programming instruction 4a.

3. Load address High byte using programming instruction 4b.

4. Load address Low byte using programming instruction 4c.

5. Load data using programming instructions 4d and 4e.

6. Repeat steps 4 and 5 for all data bytes in the page.

7. Write the data using programming instruction 4f.

8. Poll for EEPROM write complete using programming instruction 4g, or wait for t

WLRH

(refer to

Table 27-14 on page 310

).

9. Repeat steps 3 to 8 until all data have been programmed.

Note that the PROG_PAGELOAD instruction can not be used when programming the EEPROM.

27.10.19 Reading the EEPROM

1. Enter JTAG instruction PROG_COMMANDS.

2. Enable EEPROM read using programming instruction 5a.

3. Load address using programming instructions 5b and 5c.

4. Read data using programming instruction 5d.

5. Repeat steps 3 and 4 until all data have been read.

Note that the PROG_PAGEREAD instruction can not be used when reading the EEPROM.

27.10.20 Programming the Fuses

1. Enter JTAG instruction PROG_COMMANDS.

2. Enable Fuse write using programming instruction 6a.

3. Load data high byte using programming instructions 6b. A bit value of “0” will program the corresponding fuse, a “1” will unprogram the fuse.

4. Write Fuse High byte using programming instruction 6c.

5. Poll for Fuse write complete using programming instruction 6d, or wait for t

WLRH

(refer to

Table 27-14 on page 310 ).

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6. Load data low byte using programming instructions 6e. A “0” will program the fuse, a “1” will unprogram the fuse.

7. Write Fuse low byte using programming instruction 6f.

8. Poll for Fuse write complete using programming instruction 6g, or wait for t

WLRH

Table 27-14 on page 310 ).

(refer to

27.10.21 Programming the Lock Bits

1. Enter JTAG instruction PROG_COMMANDS.

2. Enable Lock bit write using programming instruction 7a.

3. Load data using programming instructions 7b. A bit value of “0” will program the corresponding lock bit, a “1” will leave the lock bit unchanged.

4. Write Lock bits using programming instruction 7c.

5. Poll for Lock bit write complete using programming instruction 7d, or wait for t

WLRH

(refer

to Table 27-14 on page 310 ).

27.10.22 Reading the Fuses and Lock Bits

1. Enter JTAG instruction PROG_COMMANDS.

2. Enable Fuse/Lock bit read using programming instruction 8a.

3. To read all Fuses and Lock bits, use programming instruction 8e.

To only read Fuse High byte, use programming instruction 8b.

To only read Fuse Low byte, use programming instruction 8c.

To only read Lock bits, use programming instruction 8d.

27.10.23 Reading the Signature Bytes

1. Enter JTAG instruction PROG_COMMANDS.

2. Enable Signature byte read using programming instruction 9a.

3. Load address 0x00 using programming instruction 9b.

4. Read first signature byte using programming instruction 9c.

5. Repeat steps 3 and 4 with address 0x01 and address 0x02 to read the second and third signature bytes, respectively.

27.10.24 Reading the Calibration Byte

1. Enter JTAG instruction PROG_COMMANDS.

2. Enable Calibration byte read using programming instruction 10a.

3. Load address 0x00 using programming instruction 10b.

4. Read the calibration byte using programming instruction 10c.

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28. Electrical characteristics

Absolute maximum ratings*

Operating temperature................................... -55°C to +125°C

Storage temperature...................................... -65°C to +150°C

Voltage on any pin except RESET with respect to ground ............................... -0.5V to V

CC

+ 0.5V

Voltage on RESET with respect to ground ......-0.5V to +13.0V

*NOTICE: Stresses beyond those listed under “Absolute

Maximum Ratings” may cause permanent damage to the device. This is a stress rating only and functional operation of the device at these or other conditions beyond those indicated in the operational sections of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability.

Maximum operating voltage.............................................. 6.0V

DC current per I/O pin.................................................. 40.0mA

DC current

V

CC

and GND pins .................................. 200.0mA

28.1

DC Characteristics

Table 28-1.

T

A

= -40°C to 85°C, V

CC

= 1.8V to 5.5V (unless otherwise noted).

Symbol Parameter Condition Min.

V

IL

V

IL1

V

IL2

V

IH

Input Low Voltage,Except

XTAL1 and Reset pin

Input Low Voltage,

XTAL1 pin

Input Low Voltage,

RESET pin

Input High Voltage,

Except XTAL1 and

RESET pins

V

CC

= 1.8V - 2.4V

V

CC

= 2.4V - 5.5V

V

CC

= 1.8V - 5.5V

V

CC

= 1.8V - 5.5V

V

CC

= 1.8V - 2.4V

V

CC

= 2.4V - 5.5V

-0.5

-0.5

-0.5

-0.5

0.7V

0.6V

CC

(2)

CC

(2)

V

IH1

Input High Voltage,

XTAL1 pin

V

CC

= 1.8V - 2.4V

V

CC

= 2.4V - 5.5V

0.8V

0.7V

CC

(2)

CC

(2)

V

IH2

Input High Voltage,

RESET pin

V

CC

= 1.8V - 5.5V

0.9V

CC

(2)

V

OL

V

OH

I

IL

I

IH

R

RST

R

PU

Output Low Voltage

(3)

Output High Voltage

(4)

Input Leakage

Current I/O Pin

Input Leakage

Current I/O Pin

Reset Pull-up Resistor

I/O Pin Pull-up Resistor

I

OL

= 20mA, V

CC

I

OL

= 10mA, V

CC

= 5V

= 3V

I

OH

= -20mA, V

CC

I

OH

= -10mA, V

CC

= 5V

= 3V

V

CC

= 5.5V, pin low

(absolute value)

V

CC

= 5.5V, pin high

(absolute value)

4.2

2.3

30

20

Typ.

Max.

0.2V

0.3V

CC

(1)

CC

(1)

0.1V

CC

(1)

0.1V

CC

(1)

V

CC

+ 0.5

V

CC

+ 0.5

V

CC

+ 0.5

V

CC

+ 0.5

V

CC

+ 0.5

0.9

0.6

1

1

60

50

Units

V

µA kΩ

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Table 28-1.

T

A

= -40°C to 85°C, V

CC

= 1.8V to 5.5V (unless otherwise noted). (Continued)

Symbol Parameter Condition Min.

Typ.

Max.

Units

t

I

V

ACIO

ACLK

ACID

Analog Comparator

Input Offset Voltage

Analog Comparator

Input Leakage Current

Analog Comparator

Propagation Delay

V

CC

= 5V

V in

= V

CC

/2

V

CC

= 5V

V in

= V

CC

/2

V

CC

= 2.7V

V

CC

= 4.0V

-50

<10

750

500

40

50 mV nA ns

Notes: 1. "Max." means the highest value where the pin is guaranteed to be read as low.

2. "Min." means the lowest value where the pin is guaranteed to be read as high.

3. Although each I/O port can sink more than the test conditions (20mA at VCC = 5V, 10mA at V

CC

= 3V) under steady state conditions (non-transient), the following must be observed:

1.)The sum of all IOL, for ports PB0-PB7, XTAL2, PD0-PD7 should not exceed 100mA.

2.)The sum of all IOL, for ports PA0-PA3, PC0-PC7 should not exceed 100mA.

If IOL exceeds the test condition, VOL may exceed the related specification. Pins are not guaranteed to sink current greater than the listed test condition.

4. Although each I/O port can source more than the test conditions (20mA at VCC = 5V, 10mA at V

CC

= 3V) under steady state conditions (non-transient), the following must be observed:

1.)The sum of all IOH, for ports PB0-PB7, XTAL2, PD0-PD7 should not exceed 100mA.

2.)The sum of all IOH, for ports PA0-PA3, PC0-PC7 should not exceed 100mA.

If IOH exceeds the test condition, VOH may exceed the related specification. Pins are not guaranteed to source current greater than the listed test condition.

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28.1.1

Atmel ATmega164A DC characteristics

Table 28-2.

T

A

= -40°C to 85°C, V

CC

= 1.8V to 5.5V (unless otherwise noted).

Symbol Parameter Condition

I

CC

Power Supply Current

(1)

Power-save mode

(3)

Power-down mode

(3)

Active 1MHz, V

CC

= 2V

Active 4MHz, V

CC

= 3V

Active 8MHz, V

CC

= 5V

Idle 1MHz, V

CC

= 2V

Idle 4MHz, V

CC

= 3V

Idle 8MHz, V

CC

= 5V

32kHz TOSC enabled,

V

CC

= 1.8V

32kHz TOSC enabled,

V

CC

= 3V

WDT enabled, V

CC

= 3V

WDT disabled, V

CC

= 3V

Notes:

1. All bits set in the ”PRR0 – Power Reduction Register 0” on page 48

.

2. Typical values at 25°C. Maximum values are test limits in production.

3. The current consumption values include input leakage current.

28.1.2

Atmel ATmega164PA DC characteristics

Table 28-3.

T

A

= -40°C to 85°C, V

CC

= 1.8V to 5.5V (unless otherwise noted).

Symbol Parameter Condition

I

CC

Power Supply Current

(1)

Power-save mode

(3)

Power-down mode

(3)

Active 1MHz, V

CC

= 2V

Active 4MHz, V

CC

= 3V

Active 8MHz, V

CC

= 5V

Idle 1MHz, V

CC

= 2V

Idle 4MHz, V

CC

= 3V

Idle 8MHz, V

CC

= 5V)

32kHz TOSC enabled,

V

CC

= 1.8V

32kHz TOSC enabled,

V

CC

= 3V

WDT enabled, V

CC

= 3V

WDT disabled, V

CC

= 3V

Notes:

1. All bits set in the ”PRR0 – Power Reduction Register 0” on page 48

.

2. Typical values at 25°C. Maximum values are test limits in production.

3. The current consumption values include input leakage current.

Min.

Min.

Typ.

(2)

0.3

1.4

4.8

0.07

0.25

1.0

0.5

0.6

5.0

0.17

Max.

0.55

3.5

12

0.5

1.5

5.5

15

3.0

Typ.

(2)

0.3

1.4

4.8

0.07

0.25

1.0

0.5

0.6

5.0

0.17

Max.

0.5

2.7

9.0

0.15

0.7

5.0

8.0

2.0

Units

mA

µA

Units

mA

µA

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28.1.3

Atmel ATmega324A DC characteristics

Table 28-4.

T

A

= -40°C to 85°C, V

CC

= 1.8V to 5.5V (unless otherwise noted).

Symbol Parameter Condition

I

CC

Power Supply Current

(1)

Power-save mode

(3)

Power-down mode

(3)

Active 1MHz, V

CC

= 2V

Active 4MHz, V

CC

= 3V

Active 8MHz, V

CC

= 5V

Idle 1MHz, V

CC

= 2V

Idle 4MHz, V

CC

= 3V

Idle 8MHz, V

CC

= 5V

32kHz TOSC enabled,

V

CC

= 1.8V

32kHz TOSC enabled,

V

CC

= 3V

WDT enabled, V

CC

= 3V

WDT disabled, V

CC

= 3V

Notes:

1. All bits set in the ”PRR0 – Power Reduction Register 0” on page 48

.

2. Typical values at 25°C. Maximum values are test limits in production.

3. The current consumption values include input leakage current.

28.1.4

Atmel ATmega324PA DC characteristics

Table 28-5.

T

A

= -40°C to 85°C, V

CC

= 1.8V to 5.5V (unless otherwise noted)

Symbol Parameter Condition

I

CC

Power Supply Current

(1)

Power-save mode

(3)

Power-down mode

(3)

Active 1MHz, V

CC

= 2V

Active 4MHz, V

CC

= 3V

Active 8MHz, V

CC

= 5V

Idle 1MHz, V

CC

= 2V

Idle 4MHz, V

CC

= 3V

Idle 8MHz, V

CC

= 5V

32kHz TOSC enabled,

V

CC

= 1.8V

32kHz TOSC enabled,

V

CC

= 3V

WDT enabled, V

CC

= 3V

WDT disabled, V

CC

= 3V

Min.

Min.

Notes:

1. All bits set in the ”PRR0 – Power Reduction Register 0” on page 48

.

2. Typical values at 25°C. Maximum values are test limits in production.

3. The current consumption values include input leakage current.

Typ.

(2)

0.3

1.5

5.2

0.06

0.35

1.3

0.5

0.6

4.2

0.15

Max.

0.55

3.5

12

0.5

1.5

5.5

15

3.0

Typ.

(2)

0.3

1.5

5.2

0.06

0.35

1.3

0.5

0.6

4.2

0.15

Max.

0.5

2.7

9

0.15

0.7

5.0

8.0

2.0

Units

mA

µA

Units

mA

µA

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28.1.5

Atmel ATmega644A DC characteristics

Table 28-6.

T

A

= -40°C to 85°C, V

CC

= 1.8V to 5.5V (unless otherwise noted).

Symbol Parameter Condition

I

CC

Power Supply Current

(1)

Power-save mode

(3)

Power-down mode

(3)

Active 1MHz, V

CC

= 2V

Active 4MHz, V

CC

= 3V

Active 8MHz, V

CC

= 5V

Idle 1MHz, V

CC

= 2V

Idle 4MHz, V

CC

= 3V

Idle 8MHz, V

CC

= 5V

32kHz TOSC enabled,

V

CC

= 1.8V

32kHz TOSC enabled,

V

CC

= 3V

WDT enabled, V

CC

= 3V

WDT disabled, V

CC

= 3V

Notes:

1. All bits set in the ”PRR0 – Power Reduction Register 0” on page 48

.

2. Typical values at 25°C. Maximum values are test limits in production.

3. The current consumption values include input leakage current.

28.1.6

Atmel ATmega644PA DC characteristics

Table 28-7.

T

A

= -40°C to 85°C, V

CC

= 1.8V to 5.5V (unless otherwise noted).

Symbol Parameter Condition

I

CC

Power Supply Current

(1)

Power-save mode

(3)

Power-down mode

(3)

Active 1MHz, V

CC

= 2V

Active 4MHz, V

CC

= 3V

Active 8MHz, V

CC

= 5V

Idle 1MHz, V

CC

= 2V

Idle 4MHz, V

CC

= 3V

Idle 8MHz, V

CC

= 5V

32kHz TOSC enabled,

V

CC

= 1.8V

32kHz TOSC enabled,

V

CC

= 3V

WDT enabled, V

CC

= 3V

WDT disabled, V

CC

= 3V

Min.

Min.

Notes:

1. All bits set in the ”PRR0 – Power Reduction Register 0” on page 48

.

2. Typical values at 25°C. Maximum values are test limits in production.

3. The current consumption values include input leakage current.

Typ.

(2)

0.38

1.8

5.6

0.06

0.2

1.1

0.5

0.6

4.2

0.15

Max.

0.5

2.7

9.0

0.15

0.7

2.5

20

3.0

Typ.

(2)

0.38

1.8

5.6

0.06

0.2

1.1

0.5

0.6

4.2

0.15

Max.

0.5

2.7

9.0

0.15

0.7

4.0

8.0

2.0

Units

mA

µA

Units

mA

µA

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28.1.7

Atmel ATmega1284 DC characteristics

Table 28-8.

T

A

= -40°C to 85°C, V

CC

= 1.8V to 5.5V (unless otherwise noted).

Symbol Parameter Condition

I

CC

Power Supply Current

(1)

Power-save mode

(3)

Power-down mode

(3)

Active 1MHz, V

CC

= 2V

Active 4MHz, V

CC

= 3V

Active 8MHz, V

CC

= 5V

Idle 1MHz, V

CC

= 2V

Idle 4MHz, V

CC

= 3V

Idle 8MHz, V

CC

= 5V

32kHz TOSC enabled,

V

CC

= 1.8V

32kHz TOSC enabled,

V

CC

= 3V

WDT enabled, V

CC

= 3V

WDT disabled, V

CC

= 3V

Notes:

1. All bits set in the ”PRR0 – Power Reduction Register 0” on page 48

.

2. Typical values at 25°C. Maximum values are test limits in production.

3. The current consumption values include input leakage current.

28.1.8

Atmel ATmega1284P DC characteristics

Table 28-9.

T

A

= -40°C to 85°C, V

CC

= 1.8V to 5.5V (unless otherwise noted).

Symbol Parameter Condition

I

CC

Power Supply Current

(1)

Power-save mode

(3)

Power-down mode

(3)

Active 1MHz, V

CC

= 2V

Active 4MHz, V

CC

= 3V

Active 8MHz, V

CC

= 5V

Idle 1MHz, V

CC

= 2V

Idle 4MHz, V

CC

= 3V

Idle 8MHz, V

CC

= 5V

32kHz TOSC enabled,

V

CC

= 1.8V

32kHz TOSC enabled,

V

CC

= 3V

WDT enabled, V

CC

= 3V

WDT disabled, V

CC

= 3V

Min.

Min.

Notes:

1. All bits set in the ”PRR0 – Power Reduction Register 0” on page 48

.

2. Typical values at 25°C. Maximum values are test limits in production.

3. The current consumption values include input leakage current.

Typ.

(2)

0.38

1.8

5.6

0.06

0.2

1.1

0.5

0.6

4.2

0.15

Max.

0.55

3.5

12

0.5

1.5

5.5

15

3.0

Typ.

(2)

0.38

1.8

5.6

0.06

0.2

1.1

0.5

0.6

4.2

0.15

Max.

0.5

2.9

9.0

0.15

0.7

5.0

10

5

Units

mA

µA

Units

mA

µA

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28.2

Speed grades

Maximum frequency is depending on V

CC

. As shown in Figure 28-1 , the maximum frequency vs.

V

CC

curve is linear between 1.8V < V

CC

< 2.7V and between 2.7V < V

CC

< 4.5V.

Figure 28-1.

Maximum frequency vs. V

CC

,

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P

.

20MHz

10MHz

4MHz

1.8V

2.7V

Sa fe operating area

4.5V

5.5V

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28.3

Clock characteristics

Table 28-10.

Calibration accuracy of internal RC oscillator.

Factory calibration

User calibration

Frequency

8.0MHz

7.3 - 8.1MHz

V

CC

3V

1.8 - 5.5V

(1)

25°C

-40°C - 85°C

Notes: 1. Voltage range for Atmel ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P.

28.3.1

External clock drive waveforms

Figure 28-2.

External clock drive waveforms.

±10%

±1%

V

IL1

V

IH1

Symbol

1/t

CLCL t

CLCL t

CHCX t

CLCX t

CLCH t

CHCL

Δ t

CLCL

28.3.2

External clock drive

Table 28-11.

External clock drive.

Parameter

Oscillator Frequency

Clock Period

High Time

Low Time

Rise Time

Fall Time

Change in period from one clock cycle to the next

V

CC

= 1.8 - 5.5V

Min.

Max.

0 4

250

100

100

2.0

2.0

2

V

CC

= 2.7 - 5.5V

Min.

Max.

0 10

100

40

40

1.6

1.6

2

V

CC

= 4.5 - 5.5V

Min.

Max.

0 20

50

20

20

0.5

0.5

2

Units

MHz ns

μs

%

336

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28.4

System and reset characteristics

Table 28-12.

Reset, Brown-out and Internal Voltage Reference characteristics.

Symbol

V

POT

V

RST t

RST

V

HYST t

BOD

V

BG t

BG

I

BG

Parameter

Power-on Reset Threshold Voltage (rising)

Power-on Reset Threshold Voltage (falling)

(1)

RESET Pin Threshold Voltage

Minimum pulse width on RESET Pin

Brown-out Detector Hysteresis

Min Pulse Width on Brown-out Reset

Bandgap reference voltage

Bandgap reference start-up time

Bandgap reference current consumption

Condition

V

CC

= 2.7V, T

A

= 25°C

V

CC

= 2.7V, T

A

= 25°C

V

CC

= 2.7V, T

A

= 25°C

Min.

1.1

0.6

0.2V

CC

1.0

Typ.

1.4

1.3

50

2

1.1

40

10

Max.

1.6

1.6

0.9V

CC

2.5

1.2

70

Units

V

µs mV

µs

V

µs

µA

Notes: 1. The Power-on Reset will not work unless the supply voltage has been below V

POT

(falling).

Table 28-13.

BODLEVEL fuse coding

(1)

.

Min. V

BOT

BODLEVEL 2:0 Fuses

111

110

101

100

011

010

001

000

1.7

2.5

4.1

Typ. V

BOT

BOD disabled

1.8

2.7

4.3

Reserved

Max. V

BOT

2.0

2.9

4.5

Units

V

Note: 1. V

BOT

may be below nominal minimum operating voltage for some devices. For devices where this is the case, the device is tested down to V

CC

= V

BOT

during the production test. This guarantees that a Brown-Out Reset will occur before V

CC

drops to a voltage where correct operation of the microcontroller is no longer guaranteed. The test is performed using

BODLEVEL = 101 and BODLEVEL = 110.

28.5

External interrupts characteristics

Table 28-14.

Asynchronous external interrupt characteristics.

Symbol Parameter

t

INT

Minimum pulse width for asynchronous external interrupt

Condition Min.

Typ.

Max.

50

Units

ns

337

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28.6

SPI timing characteristics

See Figure 28-3 on page 338 and

Figure 28-4 on page 339

for details.

Table 28-15.

SPI timing parameters.

Description Mode Min.

1

14

15

16

17

18

10

11

12

13

8

9

6

7

4

5

2

3

SCK period

SCK high/low

Rise/Fall time

Setup

Hold

Out to SCK

SCK to out

SCK to out high

SS low to out

SCK period

SCK high/low

(1)

Rise/Fall time

Setup

Hold

SCK to out

SCK to SS high

SS high to tri-state

SS low to SCK

Master

Slave

Slave

Slave

Slave

Slave

Slave

Slave

Slave

Slave

Master

Master

Master

Master

Master

Master

Master

Slave

4 × t ck

2 × t ck

10 t ck

20

20

Typ.

See

Table 18-5 on page 172

50% duty cycle

3.6

10

10

0.5 × t sck

10

10

15

15

10

Note: 1. In SPI Programming mode the minimum SCK high/low period is:

- 2 t

CLCL

for f

CK

< 12MHz

- 3 t

CLCL

for f

CK

> 12MHz

Figure 28-3.

SPI interface timing requirements (Master mode).

SS

6

SCK

(CPOL = 0)

2

SCK

(CPOL = 1)

4 5

MI

SO

(Data Input)

MSB ...

7

MO

SI

(Data Output)

MSB ...

1

LSB

LSB

2

3

Max.

1600

8 ns

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Figure 28-4.

SPI interface timing requirements (Slave mode).

SS

9

SCK

(CPOL = 0)

11

SCK

(CPOL = 1)

13 14

MOSI

(Data Input)

MSB ...

15

MISO

(Data Output)

MSB ...

10

LSB

LSB

11

12

16

X

17

28.7

two-wire Serial Interface Characteristics

Ta ble 28 -16 descr ib es th e r equirem ents for d evice s con nected to the two-wire Se r ial Bus. T he Atm el

ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P two-wire Serial Interface meets or exceeds these requirements under the noted conditions.

Timing symbols refer to Figure 28-5

.

Table 28-16.

two-wire serial bus requirements.

Symbol Parameter

V

IL

V

IH

V

hys

(1)

V

OL

(1)

t r

(1)

t

of

(1)

t

SP

(1)

I i

C

i

(1)

f

SCL

Input Low-voltage

Input High-voltage

Hysteresis of Schmitt Trigger Inputs

Output Low-voltage

Rise Time for both SDA and SCL

Output Fall Time from V

IHmin

to V

ILmax

Spikes Suppressed by Input Filter

Input Current each I/O Pin

Capacitance for each I/O Pin

SCL Clock Frequency

Rp t

HD;STA t

LOW

Value of Pull-up resistor

Hold Time (repeated) START Condition

Low Period of the SCL Clock

Condition

3mA sink current

10pF < C b

< 400pF

(3)

0.1V

CC

< V i

< 0.9V

CC f

CK

(4)

> max(16f

SCL

, 250kHz)

(5)

f

SCL

≤ 100kHz f

SCL

> 100kHz f

SCL

≤ 100kHz f

SCL

> 100kHz f

SCL

≤ 100kHz

(6)

f

SCL

> 100kHz

(7)

Min.

-0.5

0.7 V

CC

0.05 V

CC

(2)

0

20 + 0.1C

b

(2)(3)

20 + 0.1C

b

(2)(3)

0

-10

0

V

CC

0.4V

3mA

V

CC

0.4V

3mA

4.0

0.6

4.7

1.3

Max.

0.3V

CC

V

CC

+ 0.5

0.4

300

250

50

(2)

10

10

400

1000ns

C b

300ns

C b

Units

V ns

µA pF kHz

Ω

µs

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Table 28-16.

two-wire serial bus requirements. (Continued)

Symbol Parameter Condition Min.

Max.

Units

t

HIGH

High period of the SCL clock f

SCL

≤ 100kHz f

SCL

> 100kHz

4.0

0.6

– t

SU;STA

Set-up time for a repeated START condition f

SCL

≤ 100kHz f

SCL

> 100kHz f

SCL

≤ 100kHz

4.7

0.6

µs t

HD;DAT

Data hold time f

SCL

> 100kHz f

SCL

≤ 100kHz

0

0

250

3.45

0.9

– t

SU;DAT

Data setup time

100 – ns f

SCL

> 100kHz f

SCL

≤ 100kHz 4.0

– t

SU;STO

Setup time for STOP condition f

SCL

> 100kHz 0.6

– f

SCL

≤ 100kHz –

µs t

BUF

Bus free time between a STOP and

START condition

4.7

f

SCL

> 100kHz 1.3

Notes: 1. In Atmel ATmega164A/164PA/324A/324PA/644A/644PA/1284/1284P, this parameter is characterized and not 100% tested.

2. Required only for f

SCL

> 100kHz.

3. Cb = capacitance of one bus line in pF.

4. f

CK

= CPU clock frequency.

5. This requirement applies to all Atmel ATmega32 two-wire Serial Interface operation. Other devices connected to the twowire Serial Bus need only obey the general f

SCL

requirement.

6. The actual low period generated by the ATmega32 two-wire Serial Interface is (1/f

SCL

- 2/f

CK

), thus f

CK

must be greater than

6MHz for the low time requirement to be strictly met at f

SCL

= 100kHz.

7. The actual low period generated by the ATmega32 Two-wire Serial Interface is (1/f

SCL

- 2/f

CK

), thus the low time requirement will not be strictly met for f

SCL

> 308kHz when f

CK

= 8MHz. Still, ATmega32 devices connected to the bus may communicate at full speed (400kHz) with other ATmega32 devices, as well as any other device with a proper t

LOW

acceptance margin.

Figure 28-5.

Two-wire serial bus timing.

t

HIGH t of t

LOW

SCL t

SU;STA t

HD;STA t

HD;DAT

SDA t

LOW t

SU;DAT t r t

SU;STO t

BUF

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28.8

ADC characteristics

Table 28-17.

ADC characteristics, single ended channel.

Symbol Parameter

Resolution

Absolute accuracy (Including

INL, DNL, quantization error, gain and offset error)

Integral Non-Linearity (INL)

Differential Non-Linearity (DNL)

Gain Error

Offset Error

Condition

Single Ended Conversion

Single Ended Conversion

V

REF

= 4V, V

CC

= 4V,

ADC clock = 200kHz

Single Ended Conversion

V

REF

= 4V, V

CC

= 4V,

ADC clock = 1MHz

Single Ended Conversion

V

REF

= 4V, V

CC

= 4V,

ADC clock = 200kHz

Noise Reduction Mode

Single Ended Conversion

V

REF

= 4V, V

CC

= 4V,

ADC clock = 1MHz

Noise Reduction Mode

Single Ended Conversion

V

REF

= 4V, V

CC

= 4V,

ADC clock = 200kHz

Single Ended Conversion

V

REF

= 4V, V

CC

= 4V,

ADC clock = 200kHz

Single Ended Conversion

V

REF

= 4V, V

CC

= 4V,

ADC clock = 200kHz

Single Ended Conversion

V

REF

= 4V, V

CC

= 4V,

ADC clock = 200kHz

Free Running Conversion

Single Ended Conversion

AVCC

V

REF

V

IN

V

INT1

V

INT2

R

REF

R

AIN

Conversion Time

Clock Frequency

Analog Supply Voltage

Reference Voltage

Input Voltage

Input Bandwidth

Internal Voltage Reference

Internal Voltage Reference

Reference Input Resistance

Analog Input Resistance

1.1V

2.56V, V

CC

> 2.7V

Notes: 1. Values are guidelines only.

Min.

(1)

13

50

V

CC

- 0.3

1.0

GND

1.0

2.33

Typ.

(1)

10

1.9

3.25

1.9

3.25

1.1

0.3

1.6

-1.5

38.5

1.1

2.56

32

100

Max.

(1)

260

1000

V

CC

+ 0.3

AVCC

V

REF

1.2

2.79

Units

Bits

LSB

µs kHz

V kHz

V kΩ

341

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Table 28-18.

ADC characteristics, differential channels.

Symbol Parameter

Resolution

Absolute Accuracy (Including INL,

DNL Quantization Error and Offset

Error)

Integral Non-linearity (INL)

Differential Non-linearity (DNL)

Condition

Gain = 1×

Gain = 10×

Gain = 200×

Gain = 1×

V

CC

= 5V, V

REF

= 4V

ADC clock = 200kHz

Gain = 10×

V

CC

= 5V, V

REF

= 4V

ADC clock = 200kHz

Gain = 200×

V

CC

= 5V, V

REF

= 4V

ADC clock = 200kHz

Gain = 1×

V

CC

= 5V, V

REF

= 4V

ADC clock = 200kHz

Gain = 10×

V

CC

= 5V, V

REF

= 4V

ADC clock = 200kHz

Gain = 200×

V

CC

= 5V, V

REF

= 4V

ADC clock = 200kHz

Gain = 1×

V

CC

= 5V, V

REF

= 4V

ADC clock = 200kHz

Gain = 10×

V

CC

= 5V, V

REF

= 4V

ADC clock = 200kHz

Gain = 200×

V

CC

= 5V, V

REF

= 4V

ADC clock = 200kHz

Min.

(1)

Typ.

(1)

10

10

7

19

Max.

(1)

19

12

2

4

11

1

1.5

11

Units

Bits

LSB

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Table 28-18.

ADC characteristics, differential channels. (Continued)

Symbol Parameter

Gain Error

Offset Error

Condition

Gain = 1×

V

CC

= 5V, V

REF

= 4V

ADC clock = 200kHz

Gain = 10×

V

CC

= 5V, V

REF

= 4V

ADC clock = 200kHz

Gain = 200×

V

CC

= 5V, V

REF

= 4V

ADC clock = 200kHz

Gain = 1×

V

CC

= 5V, V

REF

= 4V

ADC clock = 200kHz

Gain = 10×

V

CC

= 5V, V

REF

= 4V

ADC clock = 200kHz

Gain = 200×

V

CC

= 5V, V

REF

= 4V

ADC clock = 200kHz

AVCC

V

REF

V

IN

V

INT1

V

INT2

R

REF

Conversion Time

Clock Frequency

Analog Supply Voltage

Reference Voltage

Input Differential Voltage

ADC Conversion Output

Input Bandwidth

Internal Voltage Reference

Internal Voltage Reference

Reference Input Resistance

1.1V

2.56V

Note: 1. Values are guidelines only.

Min.

(1)

13

50

V

CC

- 0.3

2.0

0

-511

1.0

2.33

Typ.

(1)

18

19

1.5

-1

-1

1

4

1.1

2.56

32

Max.

(1)

Units

LSB

260

1000

V

CC

+ 0.3

AVCC - 0.5

AVCC

511

1.2

2.79

µs kHz

V

LSB kHz

V kΩ

343

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ATmega164A/PA/324A/PA/644A/PA/1284/P

29. Typical characteristics

The following charts show typical behavior. These figures are not tested during manufacturing.

All current consumption measurements are performed with all I/O pins configured as inputs and with internal pull-ups enabled. A sine wave generator with rail-to-rail output is used as clock source.

All Active- and Idle current consumption measurements are done with all bits in the PRR registers set and thus, the corresponding I/O modules are turned off. Also the Analog Comparator is disabled during these measurements. The power consumption in Power-down mode is independent of clock selection.

The current consumption is a function of several factors such as: operating voltage, operating frequency, loading of I/O pins, switching rate of I/O pins, code executed and ambient temperature. The dominating factors are operating voltage and frequency.

The current drawn from capacitive loaded pins may be estimated (for one pin) as C

L

×

V

CC

× f where C

L

= load capacitance, V

CC

= operating voltage and f = average switching frequency of I/O pin.

The parts are characterized at frequencies higher than test limits. Parts are not guaranteed to function properly at frequencies higher than the ordering code indicates.

The difference between current consumption in Power-down mode with Watchdog Timer enabled and Power-down mode with Watchdog Timer disabled represents the differential current drawn by the Watchdog Timer.

344

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29.1

Atmel ATmega164A typical characteristics

29.1.1

Active supply current

Figure 29-1.

ATmega164A: Active supply current vs. low frequency (0.1 - 1.0MHz).

1.2

1.0

0.8

0.6

0.4

0.2

5.5V

5.0V

4.5V

4.0V

3

.3V

2.7V

1.8V

0

0 0.1

0.2

0.3

0.4

0.5

0.6

Frequency [MHz]

0.7

0.8

0.9

1.0

Figure 29-2.

ATmega164A: Active supply current vs. frequency (1 - 20MHz).

12

10

8

6

4

2

0

0 2 4

1.8V

6

2.7V

8 10 12

Frequency [MHz]

3

.3V

14 16

4.0V

18 20

5.5V

5.0V

4.5V

345

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ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-3.

Atmel ATmega164A: Active supply current vs. V

CC

(internal RC oscillator, 8MHz).

6

5

8 5°C

25°C

-40°C

4

3

2

1

0

1.5

2.0

2.5

3

.0

3

.5

V

CC

[V]

4.0

4.5

5.0

5.5

Figure 29-4.

Atmel ATmega164A: Active supply current vs. V

CC

(internal RC oscillator, 1MHz).

1.2

1.0

8 5°C

25°C

-40°C

0.8

0.6

0.4

0.2

0

1.5

2.0

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

5.0

5.5

346

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-5.

Atmel ATmega164A: Active supply current vs. V

CC

128kHz).

(internal RC oscillator,

0.25

0.20

-40°C

25°C

8 5°C

0.15

0.10

0.05

0

1.5

2.0

2.5

3

.0

3

.5

V

CC

[V]

4.0

4.5

5.0

5.5

29.1.2

Idle supply current

Figure 29-6.

Atmel ATmega164A: Idle supply current vs. V

CC

(0.1 - 1.0MHz).

0.20

0.15

0.10

5.5V

5.0V

4.5V

4.0V

3

.3V

2.7V

1.8V

0.05

0

0 0.1

0.2

0.3

0.4

0.5

0.6

Frequency [MHz]

0.7

0.8

0.9

1.0

347

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Figure 29-7.

Atmel ATmega164A: Idle supply current vs. V

CC

(1 - 20MHz).

3

.0

2.5

2.0

1.5

1.0

0.5

0

0 2 4

1.8V

6

2.7V

8

10 12

Frequency [MHz]

3

.3V

14 16

4.0V

18 20

5.5V

5.0V

4.5V

Figure 29-8.

Atmel ATmega164A: Idle supply current vs. V

CC

(internal RC oscillator, 8MHz).

1.2

1.0

8

5°C

25°C

-40°C

0.8

0.6

0.4

0.2

0

1.5

2.0

2.5

4.0

4.5

5.0

5.5

3

.0

3

.5

V

CC

[V]

348

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Figure 29-9.

Atmel ATmega164A: Idle supply current vs. V

CC

(internal RC oscillator, 1MHz).

0.35

0.30

-40°C

25°C

8 5°C

0.25

0.20

0.15

0.10

0.05

0

1.5

2.0

2.5

3

.0

4.0

4.5

5.0

5.5

3

.5

V

CC

[V]

Figure 29-10.

Atmel ATmega164A: Idle supply current vs. V

CC

(internal RC oscillator, 128kHz).

0.12

0.10

-40°C

25°C

8

5°C

0.08

0.06

0.04

0.02

0

1.5

2.0

2.5

4.5

5.0

5.5

3 .0

3 .5

V

CC

[V]

4.0

349

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.1.3

Example

Supply current of I/O modules

The tables and formulas below can be used to calculate the additional current consumption for the different I/O modules in Active and Idle mode. The enabling or disabling of the I/O modules are controlled by the Power Reduction Register. See

”PRR0 – Power Reduction Register 0” on page 48 for details.

Table 29-1.

Additional current consumption for the different I/O modules (absolute values).

PRR bit

PRUSART1

PRUSART0

PRTWI

PRTIM2

PRTIM1

PRTIM0

PRADC

PRSPI

Typical numbers

V

CC

= 2V, F = 1MHz

3.1µA

2.9µA

6.1µA

5.9µA

3.7µA

1.4µA

11.7µA

5.1µA

V

CC

= 3V, F = 4MHz

20.9µA

21.6µA

44µA

40.1µA

26.1µA

9.4µA

55.5µA

37.9µA

V

CC

= 5V, F = 8MHz

96.7µA

101µA

205.8µA

182µA

113.2µA

38.8µA

249.5µA

195.5µA

Table 29-2.

Additional current consumption (percentage) in Active and Idle mode.

PRR bit

PRUSART1

PRUSART0

PRTWI

PRTIM2

PRTIM1

PRTIM0

PRADC

PRSPI

Additional current consumption compared to Active with external

clock (see Figure 29-50 on page

371

and

Figure 29-51 on page

371

)

1.5

%

1.5

%

3.2

%

2.9

%

1.8

%

0.7

%

4.4

%

2.9

%

Additional current consumption compared to Idle with external clock (see

Figure 29-55 on page

373 and

Figure 29-56 on page

374 )

7.4

%

7.5

%

15.4

%

14.0

%

8.8

%

3.1

%

20.9

%

13.8

%

It is possible to calculate the typical current consumption based on the numbers from

Table 29-4 on page 376 for other V

CC

and frequency settings than listed in

Table 29-3 on page 376 .

Calculate the expected current consumption in idle mode with TIMER1, ADC, and SPI enabled at V

CC

= 2.0V and F = 1MHz. From

Table 29-4 on page 376 , third column, we see that we need

to add 8.8% for the TIMER1, 20.9% for the ADC, and 13.8% for the SPI module. Reading from

Figure 29-55 on page 373 , we find that the idle current consumption is ~0.073mA at V

CC

= 2.0V

and F = 1MHz. The total current consumption in idle mode with TIMER1, ADC, and SPI enabled, gives:

I

CC total

0.073 mA (1+ 0.088 + 0.209 + 0.138)

0.10 mA

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29.1.4

Power-down supply current

Figure 29-11.

Atmel ATmega164A: Power-down supply current vs. V

CC disabled).

(watchdog timer

1.6

8 5°C

1.4

1.2

1.0

0.8

0.6

0.4

0.2

0

1.5

2.0

2.5

3 .0

4.0

4.5

5.0

25°C

-40°C

5.5

3 .5

V

CC

[V]

Figure 29-12.

Atmel ATmega164A: Power-down supply current vs. V

CC

(watchdog timer enabled).

10

8

-40°C

25°C

8 5°C

6

4

2

0

1.5

2.0

2.5

3

.0

3

.5

V

CC

[V]

4.0

4.5

5.0

5.5

351

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ATmega164A/PA/324A/PA/644A/PA/1284/P

29.1.5

Power-save supply current

Figure 29-13.

Atmel ATmega164A: Power-save supply current vs. V

CC abled and 32kHz crystal oscillator running).

(watchdog timer dis-

1.8

1.5

25°C

1.2

0.9

0.6

0.3

0

1.5

2.0

2.5

4.5

5.0

5.5

3

.0

3

.5

V

CC

[V]

4.0

29.1.6

Standby supply current

Figure 29-14.

Atmel ATmega164A: Standby supply current vs. V

CC

(watchdog timer disabled).

0.20

0.18

0.16

0.14

0.12

0.10

0.08

0.06

0.04

0.02

0

1.5

2.0

2.5

3

.0

3

.5

4.0

4.5

5.0

6MHz_xtal

6MHz_res

4MHz_res

4MHz_xtal

2MHz_res

2MHz_xtal

1MHz_res

450kHz_res

5.5

V

CC

[V]

352

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.1.7

Pin pull-up

Figure 29-15.

Atmel ATmega164A: I/O pin pull-up resistor current vs. Input voltage (V

CC

1.8V).

=

50

45

40

3 5

3 0

25

20

15

10

5

0

0 0.2

0.4

0.6

1.4

1.6

1.8

2.0

25°C

8 5°C

-40°C

0.8

1.0

V

OP

[V]

1.2

Figure 29-16.

Atmel ATmega164A: I/O pin pull-up resistor current vs. input voltage (V

CC

2.7V).

=

8 0

70

60

50

40

3 0

20

10

0

0 0.5

1.0

2.0

2.5

3 .0

25°C

8

5°C

-40°C

1.5

V

OP

[V]

353

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-17.

Atmel ATmega164A: I/O pin pull-up resistor current vs. input voltage (V

CC

= 5V).

140

120

100

8

0

60

40

20

0

0 1 2

3

V

OP

[V]

4 5 6

25°C

8 5°C

-40°C

Figure 29-18.

Atmel ATmega164A: Reset pull-up resistor current vs. reset pin voltage

(V

CC

= 1.8V).

3

5

3

0

25

20

15

10

5

0

0 0.5

1.5

2.0

25°C

-40°C

8 5°C

1.0

V

RESET

[V]

354

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-19.

Atmel ATmega164A: Reset pull-up resistor current vs. reset pin voltage

(V

CC

= 2.7V).

60

50

40

3

0

20

10

0

0 0.5

1.0

1.5

V

RESET

[V]

2.0

2.5

3 .0

25°C

-40°C

8

5°C

Figure 29-20.

Atmel ATmega164A: Reset pull-up resistor current vs. reset pin voltage

(V

CC

= 5V).

120

100

8

0

60

40

20

0

0 1 2 3

V

RESET

[V]

4 5 6

25°C

-40°C

8

5°C

355

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.1.8

Pin driver strength

Figure 29-21.

Atmel ATmega164A: I/O pin output voltage vs. sink current (V

CC

= 3V).

1.0

8

5°C

0.8

0.6

25°C

-40°C

0.4

0.2

0

0 4

8

I

OL

[mA]

12 16 20

Figure 29-22.

Atmel ATmega164A: I/O pin output voltage vs. sink current (V

CC

= 5V).

0.6

8 5°C

0.5

0.4

25°C

-40°C

0.3

0.2

0.1

0

0 4 8

I

OL

[mA]

12 16 20

356

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-23.

Atmel ATmega164A: I/O pin output voltage vs. source current (V

CC

= 3V).

3

.5

3

.0

2.5

-40°C

25°C

8

5°C

2.0

1.5

1.0

0.5

0

0 4 8 12 16 20

I

OH

[mA]

Figure 29-24.

Atmel ATmega164A: I/O pin output voltage vs. source current (V

CC

= 5V).

4.7

4.6

4.5

4.4

4.3

0

5.1

5.0

4.9

4.8

4

8

12 16 20

-40°C

25°C

8

5°C

I

OH

[mA]

357

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.1.9

Pin threshold and hysteresis

Figure 29-25.

Atmel ATmega164A: I/O pin input threshold vs. V

CC

(V

IH

, I/O pin read as ‘1’).

3 .0

2.5

8

5°C

25°C

-40°C

2.0

1.5

1.0

0.5

0

1.5

2.0

2.5

4.5

5.0

5.5

3 .0

3 .5

V

CC

[V]

4.0

Figure 29-26.

Atmel ATmega164A: I/O pin input threshold vs. V

CC

(V

IL

, I/O pin read as ‘0’).

2.5

2.0

8

5°C

25°C

-40°C

1.5

1.0

0.5

0

1.5

2.0

5.5

2.5

3

.0

3

.5

V

CC

[V]

4.0

4.5

5.0

358

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-27.

Atmel ATmega164A: I/O pin input hysteresis vs. V

CC

.

0.6

0.5

0.4

0.3

0.2

0.1

0

1.5

2.0

2.5

4.5

3 .0

3 .5

V

CC

[V]

4.0

5.0

5.5

-40°C

25°C

8 5°C

Figure 29-28.

Atmel ATmega164A: Reset pin input threshold vs. V

CC

(V

IH

, I/O pin read as ‘1’).

2.5

2.0

-40°C

25°C

8

5°C

1.5

1.0

0.5

0

1.5

2.0

5.0

5.5

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

359

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-29.

Atmel ATmega164A: Reset pin input threshold vs. V

CC

(V

IL

, I/O pin read as ‘0’).

2.5

2.0

8

5°C

25°C

-40°C

1.5

1.0

0.5

0

1.5

2.0

5.5

2.5

3

.0

3

.5

V

CC

[V]

4.0

4.5

5.0

Figure 29-30.

Atmel ATmega164A: Reset pin input hysteresis vs. V

CC

.

0.7

0.6

0.5

0.4

0.3

0.2

0.1

0

1.5

2.0

2.5

3

.0

4.0

4.5

3

.5

V

CC

[V]

5.0

5.5

-40°C

25°C

8

5°C

360

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.1.10

BOD threshold

Figure 29-31.

Atmel ATmega164A: BOD threshold vs. temperature (V

BOT

= 4.3V).

4.34

4.32

Rising Vcc

4.30

4.28

4.26

Falling Vcc

4.24

4.22

4.20

-50 -40 -30 -20 -10 0 10 20 3 0 40 50 60 70 8 0 90

Temperature [°C]

Figure 29-32.

Atmel ATmega164A: BOD threshold vs. temperature (V

BOT

= 2.7V).

2.78

Rising Vcc

2.76

2.74

2.72

2.70

2.68

Falling Vcc

2.66

-50 -40 -30 -20 -10 0 10 20

3

0 40 50 60 70

8

0 90

Temperature [°C]

361

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-33.

Atmel ATmega164A: BOD threshold vs. temperature (V

BOT

= 1.8V).

1.850

Rising Vcc

1.845

1.840

1.835

1.830

1.825

1.820

1.815

1.810

1.805

Falling Vcc

1.80

-50 -40 -30 -20 -10 0 10 20

3

0 40 50 60 70

8

0 90

Temperature [°C]

Figure 29-34.

Atmel ATmega164A: Calibrated bandgap voltage vs. V

CC

.

1.109

1.107

1.105

1.103

1.101

1.099

1.097

1.095

1.093

1.091

1.5

2.0

2.5

3

.0

4.0

4.5

5.0

3

.5

V

CC

[V]

25°C

8

5°C

-40°C

5.5

362

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-35.

Atmel ATmega164A: Bandgap voltage vs. temperature.

1.087

1.085

1.083

1.081

1.079

1.077

1.075

1.073

1.071

1.069

1.067

-40 -30 -20 -10 0 10 20

3

0

Temperature [°C]

40 50 60 70

8

0 90

1.8V

3

.6V

2.7V

4.5V

5.5V

29.1.11

Internal oscillator speed

Figure 29-36.

Atmel ATmega164A: Watchdog oscillator frequency vs. temperature.

134

132

130

128

126

124

122

120

-50 -40 -30 -20 -10 0 10 20 3 0 40 50 60 70 8 0 90

Temperature [°C]

2.1V

2.7V

3 .3V

4.0V

5.5V

363

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-37.

Atmel ATmega164A: Watchdog oscillator frequency vs. V

CC

.

135

132

129

126

123

120

1.5

2.0

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

5.0

-40°C

25°C

5.5

8 5°C

Figure 29-38.

Atmel ATmega164A: Calibrated 8MHz RC oscillator vs. V

CC

.

8 .4

8 .2

8

.0

7.8

7.6

7.4

7.2

1.5

2.0

2.5

4.5

5.0

3 .0

3 .5

V

CC

[V]

4.0

5.5

8 5°C

25°C

-40°C

364

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-39.

Atmel ATmega164A: Calibrated 8MHz RC oscillator vs. temperature.

8

.3

5.0V

3

.0V

8 .2

8 .1

8

.0

7.9

7.8

7.7

-50 -40 -30 -20 -10 0 10 20

3

0 40 50 60 70

8

0 90

Temperature [°C]

Figure 29-40.

Atmel ATmega164A: Calibrated 8MHz RC oscillator vs. OSCCAL value.

10

8

6

4

16

14

12

2

0

0 16

3

2 48 64

8

0 96 112 128 144 160 176 192 208 224 240 256

OSCCAL [X1]

8

5°C

25°C

-40°C

365

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.1.12

Current consumption of peripheral units

Figure 29-41.

Atmel ATmega164A: ADC current vs. V

CC

(AREF = AV

CC

).

3

20

280

240

200

160

120

8 0

40

0

1.5

2.0

2.5

3 .0

4.0

4.5

5.0

3 .5

V

CC

[V]

5.5

-40°C

8

5°C

25°C

Figure 29-42.

Atmel ATmega164A: Analog comparator current vs. V

CC

.

100

90

8

0

70

60

50

40

3

0

20

10

0

1.5

2.0

2.5

3 .0

3 .5

4.0

4.5

5.0

V

CC

[V]

5.5

-40°C

25°C

8

5°C

366

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-43.

Atmel ATmega164A: AREF external reference current vs. V

CC

.

200

25°C

8 5°C

-40°C

160

120

8 0

40

0

1.5

2.0

2.5

4.5

5.0

5.5

3

.0

3

.5

V

CC

[V]

4.0

Figure 29-44.

Atmel ATmega164A: Brownout detector current vs. V

CC

.

27

24

21

18

15

12

9

6

3

0

1.5

2.0

2.5

3 .0

4.0

4.5

3 .5

V

CC

[V]

5.0

5.5

8

5°C

25°C

-40°C

367

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-45.

Atmel ATmega164A: Programming current vs. V

CC

.

12

10

8

6

4

2

0

1.5

2.0

2.5

4.5

3

.0

3

.5

V

CC

[V]

4.0

5.0

5.5

-40°C

25°C

8

5°C

Figure 29-46.

Atmel ATmega164A: Watchdog timer current vs. V

CC

.

9

8

7

6

5

4

3

2

1

0

1.5

2.0

2.5

3 .0

4.0

4.5

3 .5

V

CC

[V]

5.0

5.5

-40°C

25°C

8

5°C

368

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.1.13

Current consumption in reset and reset pulsewidth

Figure 29-47.

Atmel ATmega164A: Reset supply current vs. low frequency (0.1 - 1.0MHz).

0.10

0.08

0.06

5.5V

5.0V

4.5V

4.0V

0.04

0.02

3 .3V

2.7V

1.8V

0

0 0.2

0.8

1.0

0.4

0.6

Frequency [MHz]

Figure 29-48.

Atmel ATmega164A: Reset supply current vs. frequency (1 - 20MHz).

1.8

5.5V

1.5

1.2

5.0V

4.5V

0.9

4.0V

0.6

0.3

2.7V

3

.3V

0

0 2 4

1.8V

6 8 10 12

Frequency [MHz]

14 16 18 20

369

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-49.

Atmel ATmega164A: Minimum reset pulsewidth vs. V

CC

.

1600

1400

1200

1000

8

00

600

400

200

0

1.5

2.0

2.5

3

.0

4.0

4.5

3

.5

V

CC

[V]

5.0

8 5°C

25°C

-40°C

5.5

370

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.2

Atmel ATmega164PA typical characteristics

29.2.1

Active supply current

Figure 29-50.

Atmel ATmega164PA: Active supply current vs. low frequency (0.1 - 1.0MHz).

1.2

1.0

0.8

0.6

0.4

0.2

5.5V

5.0V

4.5V

4.0V

3

.3V

2.7V

1.8V

0

0 0.1

0.2

0.3

0.4

0.5

0.6

Frequency [MHz]

0.7

0.8

0.9

1.0

Figure 29-51.

Atmel ATmega164PA: Active supply current vs. frequency (1 - 20MHz).

12

10

5.5V

5.0V

4.5V

8

4.0V

6

4

2.7V

3

.3V

2

0

0 2 4

1.8V

6 8 10 12

Frequency [MHz]

14 16 18 20

371

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-52.

Atmel ATmega164PA: Active supply current vs. V

CC

8MHz).

(internal RC oscillator,

6

5

8 5°C

25°C

-40°C

4

3

2

1

0

1.5

2.0

2.5

3

.0

3

.5

V

CC

[V]

4.0

4.5

5.0

5.5

Figure 29-53.

Atmel ATmega164PA: Active supply current vs. V

CC

(internal RC oscillator,

1MHz).

1.2

1.0

8 5°C

25°C

-40°C

0.8

0.6

0.4

0.2

0

1.5

2.0

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

5.0

5.5

372

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-54.

Atmel ATmega164PA: Active supply current vs. V

CC

128kHz).

(internal RC oscillator,

0.25

0.20

-40°C

25°C

8 5°C

0.15

0.10

0.05

0

1.5

2.0

2.5

3

.0

3

.5

V

CC

[V]

4.0

4.5

5.0

5.5

29.2.2

Idle supply current

Figure 29-55.

Atmel ATmega164PA: Idle supply current vs. V

CC

(0.1 - 1.0MHz).

0.20

0.15

0.10

5.5V

5.0V

4.5V

4.0V

3

.3V

2.7V

1.8V

0.05

0

0 0.1

0.2

0.3

0.4

0.5

0.6

Frequency [MHz]

0.7

0.8

0.9

1.0

373

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-56.

Atmel ATmega164PA: Idle supply current vs. V

CC

(1 - 20MHz).

3

.0

2.5

2.0

1.5

1.0

0.5

0

0 2 4

1.8V

6

2.7V

8

10 12

Frequency [MHz]

3

.3V

14 16

4.0V

18 20

5.5V

5.0V

4.5V

Figure 29-57.

Atmel ATmega164PA: Idle supply current vs. V

CC

(internal RC oscillator, 8MHz).

1.2

1.0

8

5°C

25°C

-40°C

0.8

0.6

0.4

0.2

0

1.5

2.0

2.5

4.0

4.5

5.0

5.5

3

.0

3

.5

V

CC

[V]

374

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-58.

Atmel ATmega164PA: Idle supply current vs. V

CC

(internal RC oscillator, 1MHz).

0.35

0.30

-40°C

25°C

8 5°C

0.25

0.20

0.15

0.10

0.05

0

1.5

2.0

2.5

3

.0

4.0

4.5

5.0

5.5

3

.5

V

CC

[V]

Figure 29-59.

Atmel ATmega164PA: Idle supply current vs. V

CC

128kHz).

(internal RC oscillator,

0.12

0.10

0.08

0.06

0.04

0.02

0

1.5

2.0

2.5

4.5

5.0

5.5

-40°C

25°C

8

5°C

3 .0

3 .5

V

CC

[V]

4.0

375

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.2.3

Example

Supply current of I/O modules

The tables and formulas below can be used to calculate the additional current consumption for the different I/O modules in Active and Idle mode. The enabling or disabling of the I/O modules are controlled by the Power Reduction Register. See

”PRR0 – Power Reduction Register 0” on page 48 for details.

Table 29-3.

Additional current consumption for the different I/O modules (absolute values).

PRR bit

PRUSART1

PRUSART0

PRTWI

PRTIM2

PRTIM1

PRTIM0

PRADC

PRSPI

Typical numbers

V

CC

= 2V, F = 1MHz

3.1µA

2.9µA

6.1µA

5.9µA

3.7µA

1.4µA

11.7µA

5.1µA

V

CC

= 3V, F = 4MHz

20.9µA

21.6µA

44µA

40.1µA

26.1µA

9.4µA

55.5µA

37.9µA

V

CC

= 5V, F = 8MHz

96.7µA

101µA

205.8µA

182µA

113.2µA

38.8µA

249.5µA

195.5µA

Table 29-4.

Additional current consumption (percentage) in Active and Idle mode.

PRR bit

PRUSART1

PRUSART0

PRTWI

PRTIM2

PRTIM1

PRTIM0

PRADC

PRSPI

Additional current consumption compared to Active with external

clock (see Figure 29-50 on page

371

and

Figure 29-51 on page

371

)

1.5

%

1.5

%

3.2

%

2.9

%

1.8

%

0.7

%

4.4

%

2.9

%

Additional current consumption compared to Idle with external clock (see

Figure 29-55 on page

373 and

Figure 29-56 on page

374 )

7.4

%

7.5

%

15.4

%

14.0

%

8.8

%

3.1

%

20.9

%

13.8

%

It is possible to calculate the typical current consumption based on the numbers from

Table 29-4 on page 376 for other V

CC

and frequency settings than listed in

Table 29-3 on page 376 .

Calculate the expected current consumption in idle mode with TIMER1, ADC, and SPI enabled at V

CC

= 2.0V and F = 1MHz. From

Table 29-4 on page 376 , third column, we see that we need

to add 8.8% for the TIMER1, 20.9% for the ADC, and 13.8% for the SPI module. Reading from

Figure 29-55 on page 373 , we find that the idle current consumption is ~0.073mA at V

CC

= 2.0V

and F = 1MHz. The total current consumption in idle mode with TIMER1, ADC, and SPI enabled, gives:

I

CC total

0.073mA (1+ 0.088 + 0.209 + 0.138)

0.105mA

376

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.2.4

Power-down supply current

Figure 29-60.

Atmel ATmega164PA: Power-down supply current vs. V

CC disabled).

(watchdog timer

1.6

8 5°C

1.4

1.2

1.0

0.8

0.6

0.4

0.2

0

1.5

2.0

2.5

3 .0

4.0

4.5

5.0

25°C

-40°C

5.5

3 .5

V

CC

[V]

Figure 29-61.

Atmel ATmega164PA: Power-down supply current vs. V

CC

(watchdog timer enabled).

10

8

-40°C

25°C

8 5°C

6

4

2

0

1.5

2.0

2.5

3

.0

3

.5

V

CC

[V]

4.0

4.5

5.0

5.5

377

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.2.5

Power-save supply current

Figure 29-62.

Atmel ATmega164PA: Power-save supply current vs. V

CC abled and 32kHz crystal oscillator running).

(watchdog timer dis-

1.8

1.5

25°C

1.2

0.9

0.6

0.3

0

1.5

2.0

2.5

4.5

5.0

5.5

3

.0

3

.5

V

CC

[V]

4.0

29.2.6

Standby supply current

Figure 29-63.

Atmel ATmega164PA: Standby supply current vs. V

CC

(watchdog timer disabled).

0.20

0.18

0.16

0.14

0.12

0.10

0.08

0.06

0.04

0.02

0

1.5

2.0

2.5

3

.0

3

.5

4.0

4.5

5.0

6MHz_xtal

6MHz_res

4MHz_res

4MHz_xtal

2MHz_res

2MHz_xtal

1MHz_res

450kHz_res

5.5

V

CC

[V]

378

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.2.7

Pin pull-up

Figure 29-64.

Atmel ATmega164PA: I/O pin pull-up resistor current vs. input voltage (V

CC

1.8V).

=

50

45

40

3 5

3 0

25

20

15

10

5

0

0 0.2

0.4

0.6

1.4

1.6

1.8

2.0

25°C

8 5°C

-40°C

0.8

1.0

V

OP

[V]

1.2

Figure 29-65.

Atmel ATmega164PA: I/O pin pull-up resistor current vs. input voltage (V

CC

2.7V).

=

8 0

70

60

50

40

3 0

20

10

0

0 0.5

1.0

2.0

2.5

3 .0

25°C

8 5°C

-40°C

1.5

V

OP

[V]

379

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-66.

Atmel ATmega164PA: I/O pin pull-up resistor current vs. input voltage (V

CC

= 5V).

140

120

100

8

0

60

40

20

0

0 1 2

3

V

OP

[V]

4 5 6

25°C

8 5°C

-40°C

Figure 29-67.

Atmel ATmega164PA: Reset pull-up resistor current vs. reset pin voltage

(V

CC

= 1.8V).

3

5

3

0

25

20

15

10

5

0

0 0.5

1.5

2.0

25°C

-40°C

8 5°C

1.0

V

RESET

[V]

380

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-68.

Atmel ATmega164PA: Reset pull-up resistor current vs. reset pin voltage

(V

CC

= 2.7V).

60

50

40

3

0

20

10

0

0 0.5

1.0

1.5

V

RESET

[V]

2.0

2.5

3 .0

25°C

-40°C

8

5°C

Figure 29-69.

Atmel ATmega164PA: Reset pull-up resistor current vs. reset pin voltage (V

CC

5V).

=

120

100

8

0

60

40

20

0

0 1 2 3

V

RESET

[V]

4 5 6

25°C

-40°C

8

5°C

381

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.2.8

Pin driver strength

Figure 29-70.

Atmel ATmega164PA: I/O pin output voltage vs. sink current (V

CC

= 3V).

1.0

8

5°C

0.8

0.6

25°C

-40°C

0.4

0.2

0

0 4

8

I

OL

[mA]

12 16 20

Figure 29-71.

Atmel ATmega164PA: I/O pin output voltage vs. sink current (V

CC

= 5V).

0.6

8 5°C

0.5

0.4

25°C

-40°C

0.3

0.2

0.1

0

0 4 8

I

OL

[mA]

12 16 20

382

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-72.

Atmel ATmega164PA: I/O pin output voltage vs. source current (V

CC

= 3V).

3

.5

3

.0

2.5

-40°C

25°C

8

5°C

2.0

1.5

1.0

0.5

0

0 4 8 12 16 20

I

OH

[mA]

Figure 29-73.

Atmel ATmega164PA: I/O pin output voltage vs. source current (V

CC

= 5V).

4.7

4.6

4.5

4.4

4.3

0

5.1

5.0

4.9

4.8

4

8

12 16 20

-40°C

25°C

8

5°C

I

OH

[mA]

383

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.2.9

Pin threshold and hysteresis

Figure 29-74.

Atmel ATmega164PA: I/O pin input threshold vs. V

CC

(V

IH

, I/O pin read as ‘1’).

3 .0

2.5

8

5°C

25°C

-40°C

2.0

1.5

1.0

0.5

0

1.5

2.0

2.5

4.5

5.0

5.5

3 .0

3 .5

V

CC

[V]

4.0

Figure 29-75.

Atmel ATmega164PA: I/O pin input threshold vs. V

CC

(V

IL

, I/O pin read as ‘0’).

2.5

2.0

8

5°C

25°C

-40°C

1.5

1.0

0.5

0

1.5

2.0

5.5

2.5

3

.0

3

.5

V

CC

[V]

4.0

4.5

5.0

384

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-76.

Atmel ATmega164PA: I/O pin input hysteresis vs. V

CC

.

0.6

0.5

0.4

0.3

0.2

0.1

0

1.5

2.0

2.5

4.5

3 .0

3 .5

V

CC

[V]

4.0

5.0

5.5

-40°C

25°C

8 5°C

Figure 29-77.

Atmel ATmega164PA: Reset pin input threshold vs. V

CC

(V

IH

, I/O pin read as ‘1’).

2.5

2.0

-40°C

25°C

8

5°C

1.5

1.0

0.5

0

1.5

2.0

5.0

5.5

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

385

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-78.

Atmel ATmega164PA: Reset pin input threshold vs. V

CC

(V

IL

, I/O pin read as ‘0’).

2.5

2.0

8

5°C

25°C

-40°C

1.5

1.0

0.5

0

1.5

2.0

5.5

2.5

3

.0

3

.5

V

CC

[V]

4.0

4.5

5.0

Figure 29-79.

Atmel ATmega164PA: Reset pin input hysteresis vs. V

CC

.

0.7

0.6

0.5

0.4

0.3

0.2

0.1

0

1.5

2.0

2.5

3

.0

4.0

4.5

3

.5

V

CC

[V]

5.0

5.5

-40°C

25°C

8

5°C

386

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.2.10

BOD threshold

Figure 29-80.

Atmel ATmega164PA: BOD threshold vs. temperature (V

BOT

= 4.3V).

4.34

4.32

Rising Vcc

4.30

4.28

4.26

Falling Vcc

4.24

4.22

4.20

-50 -40 -30 -20 -10 0 10 20 3 0 40 50 60 70 8 0 90

Temperature [°C]

Figure 29-81.

Atmel ATmega164PA: BOD threshold vs. temperature (V

BOT

= 2.7V).

2.78

Rising Vcc

2.76

2.74

2.72

2.70

2.68

Falling Vcc

2.66

-50 -40 -30 -20 -10 0 10 20

3

0 40 50 60 70

8

0 90

Temperature [°C]

387

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-82.

Atmel ATmega164PA: BOD threshold vs. temperature (V

BOT

= 1.8V).

1.850

Rising Vcc

1.845

1.840

1.835

1.830

1.825

1.820

1.815

1.810

1.805

Falling Vcc

1.80

-50 -40 -30 -20 -10 0 10 20 3 0 40 50 60 70 8 0 90

Temperature [°C]

Figure 29-83.

Atmel ATmega164PA: Calibrated bandgap voltage vs. V

CC

.

1.109

1.107

1.105

1.103

1.101

1.099

1.097

1.095

1.093

1.091

1.5

2.0

2.5

3 .0

4.0

4.5

5.0

3 .5

V

CC

[V]

25°C

8

5°C

-40°C

5.5

388

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-84.

Atmel ATmega164PA: Bandgap voltage vs. temperature.

1.087

1.085

1.083

1.081

1.079

1.077

1.075

1.073

1.071

1.069

1.067

-40 -30 -20 -10 0 10 20

3

0

Temperature [°C]

40 50 60 70

8

0 90

1.8V

3

.6V

2.7V

4.5V

5.5V

29.2.11

Internal oscillator speed

Figure 29-85.

Atmel ATmega164PA: Watchdog oscillator frequency vs. temperature.

134

132

130

128

126

124

122

120

-50 -40 -30 -20 -10 0 10 20 3 0 40 50 60 70 8 0 90

Temperature [°C]

2.1V

2.7V

3 .3V

4.0V

5.5V

389

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-86.

Atmel ATmega164PA: Watchdog oscillator frequency vs. V

CC

.

135

132

129

126

123

120

1.5

2.0

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

5.0

-40°C

25°C

5.5

8 5°C

Figure 29-87.

Atmel ATmega164PA: Calibrated 8MHz RC oscillator vs. V

CC

.

8 .4

8 .2

8

.0

7.8

7.6

7.4

7.2

1.5

2.0

2.5

4.5

5.0

3 .0

3 .5

V

CC

[V]

4.0

5.5

8 5°C

25°C

-40°C

390

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-88.

Atmel ATmega164PA: Calibrated 8MHz RC oscillator vs. temperature.

8

.3

5.0V

3

.0V

8 .2

8 .1

8

.0

7.9

7.8

7.7

-50 -40 -30 -20 -10 0 10 20

3

0 40 50 60 70

8

0 90

Temperature [°C]

Figure 29-89.

Atmel ATmega164PA: Calibrated 8MHz RC oscillator vs. OSCCAL value.

10

8

6

4

16

14

12

2

0

0 16

3

2 48 64

8

0 96 112 128 144 160 176 192 208 224 240 256

OSCCAL [X1]

8

5°C

25°C

-40°C

391

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.2.12

Current consumption of peripheral units

Figure 29-90.

Atmel ATmega164PA: ADC current vs. V

CC

(AREF = AV

CC

).

3

20

280

240

200

160

120

8 0

40

0

1.5

2.0

2.5

3 .0

4.0

4.5

5.0

3 .5

V

CC

[V]

5.5

-40°C

8

5°C

25°C

Figure 29-91.

Atmel ATmega164PA: Analog comparator current vs. V

CC

.

100

90

8

0

70

60

50

40

3

0

20

10

0

1.5

2.0

2.5

3 .0

3 .5

4.0

4.5

5.0

V

CC

[V]

5.5

-40°C

25°C

8

5°C

392

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-92.

Atmel ATmega164PA: AREF external reference current vs. V

CC

.

200

25°C

8 5°C

-40°C

160

120

8 0

40

0

1.5

2.0

2.5

4.5

5.0

5.5

3

.0

3

.5

V

CC

[V]

4.0

Figure 29-93.

Atmel ATmega164PA: Brownout detector current vs. V

CC

.

27

24

21

18

15

12

9

6

3

0

1.5

2.0

2.5

3 .0

4.0

4.5

5.0

3 .5

V

CC

[V]

5.5

8

5°C

25°C

-40°C

393

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-94.

Atmel ATmega164PA: Programming current vs. V

CC

.

12

10

8

6

4

2

0

1.5

2.0

2.5

4.5

3

.0

3

.5

V

CC

[V]

4.0

5.0

5.5

-40°C

25°C

8

5°C

Figure 29-95.

Atmel ATmega164PA: Watchdog timer current vs. V

CC

.

9

8

7

6

5

4

3

2

1

0

1.5

2.0

2.5

3 .0

4.0

4.5

3 .5

V

CC

[V]

5.0

5.5

-40°C

25°C

8

5°C

394

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.2.13

Current consumption in reset and reset pulsewidth

Figure 29-96.

Atmel ATmega164PA: Reset supply current vs. low frequency (0.1 - 1.0MHz).

0.10

0.08

0.06

5.5V

5.0V

4.5V

4.0V

0.04

0.02

3 .3V

2.7V

1.8V

0

0 0.2

0.8

1.0

0.4

0.6

Frequency [MHz]

Figure 29-97.

Atmel ATmega164PA: Reset supply current vs. frequency (1 - 20MHz).

1.8

5.5V

1.5

1.2

5.0V

4.5V

0.9

4.0V

0.6

0.3

2.7V

3

.3V

0

0 2 4

1.8V

6 8 10 12

Frequency [MHz]

14 16 18 20

395

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-98.

Atmel ATmega164PA: Minimum reset pulsewidth vs. V

CC

.

1600

1400

1200

1000

8 00

600

400

200

0

1.5

2.0

2.5

3 .0

4.0

4.5

5.0

3 .5

V

CC

[V]

8

5°C

25°C

-40°C

5.5

396

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.3

Atmel ATmega324A typical characteristics

29.3.1

Active supply current

Figure 29-99.

Atmel ATmega324A: Active supply current vs. low frequency (0.1 - 1.0MHz).

1.2

5.5V

1.0

0.8

5.0V

4.5V

4.0V

0.6

0.4

3 .3V

2.7V

1.8V

0.2

0

0 0.1

0.2

0.3

0.4

0.5

0.6

Frequency [MHz]

0.7

0.8

0.9

1.0

Figure 29-100.

Atmel ATmega324A: Active supply current vs. frequency (1 - 20MHz).

14

5.5V

12

10

5.0V

4.5V

8

4.0V

6

4

3

.3V

2.7V

2

0

0 2 4

1.8V

6 8 10

Frequency [MHz]

12 14 16 18 20

397

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-101.

Atmel ATmega324A: Active supply current vs. V

CC

8MHz).

(internal RC oscillator,

7

6

8

5°C

25°C

-40°C

5

4

3

2

1

0

1.5

2.0

2.5

3

.0

4.0

4.5

5.0

5.5

3

.5

V

CC

[V]

Figure 29-102.

Atmel ATmega324A: Active supply current vs. V

CC

1MHz).

(internal RC oscillator,

1.6

8

5°C

25°C

-40°C

1.2

0.8

0.4

0

1.5

2.0

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

5.0

5.5

398

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-103.

Atmel ATmega324A: Active supply current vs. V

CC

128kHz).

(internal RC oscillator,

0.25

0.20

-40°C

25°C

8

5°C

0.15

0.10

0.05

29.3.2

0

1.5

2.0

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

5.0

Idle supply current

Figure 29-104.

Atmel ATmega324A: Idle supply current vs. V

CC

(0.1 - 1.0MHz).

0.25

5.5

0.20

0.15

0.10

5.5V

5.0V

4.5V

4.0V

3 .3V

2.7V

1.8V

0.05

0

0 0.1

0.2

0.3

0.4

0.5

Frequency [MHz]

0.6

0.7

0.8

0.9

1.0

399

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-105.

Atmel ATmega324A: Idle supply current vs. V

CC

(1 - 20MHz).

4

3

2

4.0V

3 .3V

1

2.7V

0

0 2 4

1.8V

6

8

10

Frequency [MHz]

12 14 16 18 20

5.5V

5.0V

4.5V

Figure 29-106.

Atmel ATmega324A: Idle supply current vs. V

CC

(internal RC oscillator, 8MHz).

1.8

1.5

8 5°C

25°C

-40°C

1.2

0.9

0.6

0.3

0

1.5

2.0

2.5

4.0

4.5

5.0

5.5

3

.0

3

.5

V

CC

[V]

400

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-107.

Atmel ATmega324A: Idle supply current vs. V

CC

(internal RC oscillator, 1MHz).

0.6

8

5°C

25°C

-40°C

0.5

0.4

0.3

0.2

0.1

0

1.5

2.0

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

5.0

5.5

Figure 29-108.

Atmel ATmega324A: Idle supply current vs. V

CC

(internal RC oscillator, 128kHz).

0.12

0.10

-40°C

25°C

8 5°C

0.08

0.06

0.04

0.02

0

1.5

2.0

2.5

4.0

4.5

5.0

5.5

3

.0

3

.5

V

CC

[V]

401

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.3.3

Example

Supply current of I/O modules

The tables and formulas below can be used to calculate the additional current consumption for the different I/O modules in Active and Idle mode. The enabling or disabling of the I/O modules are controlled by the Power Reduction Register. See

”PRR0 – Power Reduction Register 0” on page 48 for details.

Table 29-5.

Additional current consumption for the different I/O modules (absolute values).

PRR bit

PRUSART1

PRUSART0

PRTWI

PRTIM2

PRTIM1

PRTIM0

PRADC

PRSPI

Typical numbers in

V

CC

= 2V, F = 1MHz

3.1µA

3.0µA

6.4µA

5.6µA

3.6µA

1.7µA

11.8µA

5.3µA

V

CC

= 3V, F = 4MHz

21.5µA

21.0µA

45.7µA

37.7µA

24.8µA

10.4µA

59.2µA

40.1µA

V

CC

= 5V, F = 8MHz

100.0µA

98.2µA

214.5µA

165.8µA

107.0µA

43.2µA

257.0µA

206.8µA

Table 29-6.

Additional current consumption (percentage) in Active and Idle mode.

PRR bit

PRUSART1

PRUSART0

PRTWI

PRTIM2

PRTIM1

PRTIM0

PRADC

PRSPI

Additional current consumption compared to Active with external clock (see Figure 29-148 on page

423 and

Figure 29-149 on page

423

)

1.4%

1.4%

3.0%

2.5%

1.6%

0.7%

4.2%

2.7%

Additional current consumption compared to Idle with external clock (see

Figure 29-153 on page

425 and

Figure 29-154 on page

426 )

5.3%

5.2%

11.3%

9.1%

6.0%

2.5%

14.8%

10.3%

It is possible to calculate the typical current consumption based on the numbers from Table 29-8 on page 428 for other V

CC

and frequency settings than listed in Table 29-7 on page 428 .

Calculate the expected current consumption in idle mode with TIMER1, ADC, and SPI enabled at V

CC

= 2.0V and F = 1MHz. From Table 29-8 on page 428 , third column, we see that we need to add 6.0% for the TIMER1, 14.8% for the ADC, and 10.3% for the SPI module. Reading from

Figure 29-153 on page 425

, we find that the idle current consumption is ~0.078mA at V

CC

= 2.0V

and F = 1MHz. The total current consumption in idle mode with TIMER1, ADC, and SPI enabled, gives:

I

CC total

0.078mA (1+ 0.060 + 0.148 + 0.103)

0.102mA

402

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.3.4

Power-down supply current

Figure 29-109.

Atmel ATmega324A: Power-down supply current vs. V

CC disabled).

(watchdog timer

1.2

8

5°C

1.0

0.8

0.6

0.4

0.2

0

1.5

2.0

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

5.0

25°C

-40°C

5.5

Figure 29-110.

Atmel ATmega324A: Power-down supply current vs. V

CC

(watchdog timer enabled).

10

8

-40°C

8

5°C

25°C

6

4

2

0

1.5

2.0

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

5.0

5.5

403

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.3.5

Power-save supply current

Figure 29-111.

Atmel ATmega324A: Power-save supply current vs. V

CC

(watchdog timer dis-

2.50

2.00

1.50

1.00

0.50

8 5°C

25°C

-40°C

0

1.5

2.0

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

5.0

5.5

29.3.6

Standby supply current

Figure 29-112.

Atmel ATmega324A: Standby supply current vs. V

CC

(watchdog timer disabled).

0.18

0.16

0.14

0.12

0.10

0.08

0.06

0.04

0.02

0

1.5

2.0

2.5

3

.0

4.0

4.5

5.0

6MHz_res

6MHz_xtal

5.5

3

.5

V

CC

[V]

4MHz_res

4MHz_xtal

2MHz_res

2MHz_xtal

450kHz_res

404

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.3.7

Pin pull-up

Figure 29-113.

Atmel ATmega324A: I/O pin pull-up resistor current vs. input voltage (V

CC

1.8V).

=

50

40

3 0

20

10

0

0 0.2

0.4

0.6

0.8

1.0

V

OP

[V]

1.2

1.4

1.6

1.8

2.0

25°C

-40°C

8

5°C

Figure 29-114.

Atmel ATmega324A: I/O pin pull-up resistor current vs. input voltage (V

CC

=

2.7V).

60

50

40

3 0

20

8 0

70

10

0

0 0.5

1.0

2.0

2.5

1.5

V

OP

[V]

3 .0

25°C

8 5°C

-40°C

405

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-115.

Atmel ATmega324A: I/O pin pull-up resistor current vs. input voltage (V

CC

= 5V).

140

40

20

0

0

120

100

8

0

60

1 2 3

V

OP

[V]

4 5 6

25°C

8 5°C

-40°C

Figure 29-116.

Atmel ATmega324A: Reset pull-up resistor current vs. reset pin voltage

(V

CC

= 1.8V).

3

5

3 0

25

20

15

10

5

0

0 0.2

0.4

0.6

0.8

1.0

V

RESET

[V]

1.2

1.4

1.6

1.8

25°C

-40°C

8 5°C

2.0

406

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-117.

Atmel ATmega324A: Reset pull-up resistor current vs. reset pin voltage

(V

CC

= 2.7V).

60

50

40

3 0

20

10

0

0 0.5

1.0

1.5

V

RESET

[V]

2.0

2.5

3

.0

25°C

-40°C

8

5°C

Figure 29-118.

Atmel ATmega324A: Reset pull-up resistor current vs. reset pin voltage (V

CC

=

5V).

120

100

8 0

60

40

20

0

0 1 2

3

V

RESET

[V]

4 5 6

25°C

-40°C

8

5°C

407

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.3.8

Pin driver strength

Figure 29-119.

Atmel ATmega324A: I/O pin output voltage vs. sink current (V

CC

= 3V).

1.0

8

5°C

0.8

25°C

0.6

-40°C

0.4

0.2

0

5 8 11

I

OL

[mA]

14 17 20

Figure 29-120.

Atmel ATmega324A: I/O pin output voltage vs. sink current (V

CC

= 5V).

0.6

8 5°C

0.5

25°C

0.4

-40°C

0.3

0.2

0.1

0

5

8

11

I

OL

[mA]

14 17 20

408

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-121.

Atmel ATmega324A: I/O pin output voltage vs. source current (V

CC

= 3V).

3

.0

2.5

2.0

1.5

1.0

0.5

0

5

8

11

I

OH

[mA]

14 17 20

-40°C

25°C

8 5°C

Figure 29-122.

Atmel ATmega324A: I/O pin output voltage vs. source current (V

CC

= 5V).

4.9

4.8

4.7

4.6

4.5

4.4

4.3

5

8

11

I

OH

[mA]

14 17 20

-40°C

25°C

8

5°C

409

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.3.9

Pin threshold and hysteresis

Figure 29-123.

Atmel ATmega324A: I/O pin input threshold vs. V

CC

(V

IH

, I/O pin read as ‘1’).

3

.0

2.5

8 5°C

-40°C

25°C

2.0

1.5

1.0

0.5

0

1.5

2.0

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

5.0

5.5

Figure 29-124.

Atmel ATmega324A: I/O pin input threshold vs. V

CC

(V

IL

, I/O pin read as ‘0’).

2.5

-40°C

8 5°C

25°C

2.0

1.5

1.0

0.5

0

1.5

2.0

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

5.0

5.5

410

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-125.

Atmel ATmega324A: I/O pin input hysteresis vs. V

CC

.

0.6

0.3

0.2

0.1

0.5

0.4

0

1.5

2.0

2.5

4.0

4.5

3

.0

3

.5

V

CC

[V]

5.0

5.5

8

5°C

25°C

-40°C

Figure 29-126.

Atmel ATmega324A: Reset pin input threshold vs. V

CC

(V

IH

, I/O pin read as ‘1’).

2.5

-40°C

8 5°C

25°C

2.0

1.5

1.0

0.5

0

1.5

2.0

2.5

3

.0

3

.5

V

CC

[V]

4.0

4.5

5.0

5.5

411

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-127.

Atmel ATmega324A: Reset pin input threshold vs. V

CC

(V

IL

, I/O pin read as ‘0’).

2.5

-40°C

25°C

8

5°C

2.0

1.5

1.0

0.5

0

1.5

2.0

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

5.0

5.5

Figure 29-128.

Atmel ATmega324A: Reset pin input hysteresis vs. V

CC

.

0.7

0.6

0.5

0.4

0.3

0.2

0.1

0

1.5

2.0

2.5

3

.0

4.0

4.5

3

.5

V

CC

[V]

5.0

-40°C

25°C

5.5

8

5°C

412

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.3.10

BOD threshold

Figure 29-129.

Atmel ATmega324A: BOD threshold vs. temperature (V

BOT

= 4.3V).

4.40

Rising Vcc

4.38

4.36

4.34

4.32

4.30

Falling Vcc

4.28

-40 -20 0 20 40

Temperature [°C]

60

8

0

Figure 29-130.

Atmel ATmega324A: BOD threshold vs. temperature (V

BOT

= 2.7V).

2.80

Rising Vcc

2.78

100

2.76

2.74

2.72

2.70

2.68

2.66

-40 -20 0 20 40

Temperature [°C]

60

Falling Vcc

8

0 100

413

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-131.

Atmel ATmega324A: BOD threshold vs. temperature (V

BOT

= 1.8V).

1.86

Rising Vcc

1.84

1.82

1.80

1.78

1.76

-40 -20 0 20 40

Temperature [°C]

60

Falling Vcc

8

0 100

Figure 29-132.

Atmel ATmega324A: Calibrated bandgap voltage vs. V

CC

.

1.098

1.096

1.094

1.092

1.090

1.088

1.086

1.084

1.082

1.080

1.078

1.076

1.5

2.0

2.5

3 .0

3 .5

Vcc [V]

4.0

4.5

5.0

8 5°C

25°C

-40°C

5.5

414

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-133.

Atmel ATmega324A: Bandgap voltage vs. temperature.

1.097

1.095

1.093

1.091

1.089

1.087

1.085

1.083

1.081

1.079

1.077

-40 -30 -20 -10 0 10 20

3

0 40 50 60 70

8

0 90

Temperature [°C]

1.8V

3 .6V

2.7V

4.5V

5.5V

29.3.11

Internal oscillator speed

Figure 29-134.

Atmel ATmega324A: Watchdog oscillator frequency vs. temperature.

122

119

116

113

110

-40 -20

2.1V

2.7V

3 .3V

4.0V

5.5V

0 20 40

Temperature [°C]

60 8 0 100

415

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-135.

Atmel ATmega324A: Watchdog oscillator frequency vs. V

CC

.

123

120

117

-40°C

25°C

114

111

1.5

2.0

2.5

3

.0

3

.5

V

CC

[V]

4.0

4.5

5.0

5.5

8

5°C

Figure 29-136.

Atmel ATmega324A: Calibrated 8MHz RC oscillator vs. V

CC

.

8 .6

8

.2

8

5°C

25°C

7.8

-40°C

7.4

7.0

1.5

2.0

2.5

3

.0

3

.5

V

CC

[V]

4.0

4.5

5.0

5.5

416

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-137.

Atmel ATmega324A: Calibrated 8MHz RC oscillator vs. temperature.

8 .6

5.0V

3 .0V

8 .3

8

.0

7.7

7.4

-40 -20 0 20 40

Temperature [°C]

60 8 0 100

Figure 29-138.

Atmel ATmega324A: Calibrated 8MHz RC oscillator vs. OSCCAL value.

12

10

8

6

16

14

4

2

0

0 16 3 2 48 64 8 0 96 112 128 144 160 176 192 208 224 240 256

OSCCAL (X1)

8 5°C

25°C

-40°C

417

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.3.12

Current consumption of peripheral units

Figure 29-139.

Atmel ATmega324A: ADC current vs. V

CC

(AREF = AV

CC

).

3 00

250

200

150

100

50

0

1.5

2.0

2.5

4.0

4.5

5.0

3

.0

3

.5

V

CC

[V]

5.5

25°C

8 5°C

-40°C

Figure 29-140.

Atmel ATmega324A: Analog comparator current vs. V

CC

.

90

8

0

70

60

50

40

3

0

20

10

0

1.5

2.0

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

5.0

5.5

-40°C

25°C

8

5°C

418

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-141.

Atmel ATmega324A: AREF external reference current vs. V

CC

.

200

25°C

8 5°C

-40°C

160

120

8

0

40

0

1.5

2.0

2.5

3

.0

3

.5

V

CC

[V]

4.0

4.5

5.0

5.5

Figure 29-142.

Atmel ATmega324A: Brownout detector current vs. V

CC

.

25

20

15

10

5

0

1.5

2.0

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

5.0

5.5

8 5°C

25°C

-40°C

419

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-143.

Atmel ATmega324A: Programming current vs. V

CC

.

14

12

10

8

6

4

2

0

1.5

2.0

2.5

3 .0

4.0

4.5

3 .5

V

CC

[V]

5.0

Figure 29-144.

Atmel ATmega324A: Watchdog timer current vs. V

CC

.

9

5.5

25°C

-40°C

8 5°C

7

-40°C

25°C

8

5°C

5

3

1

1.5

2.0

2.5

3

.0

3

.5

V

CC

[V]

4.0

4.5

5.0

5.5

420

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.3.13

Current consumption in reset and reset pulsewidth

Figure 29-145.

Atmel ATmega324A: Reset supply current vs. low frequency (0.1 - 1.0MHz).

0.14

0.12

0.10

0.08

0.06

0.04

0.02

5.5V

5.0V

4.5V

4.0V

3

.3V

2.7V

1.8V

0

0 0.1

0.2

0.3

0.4

0.5

0.6

Frequency [MHz]

0.7

0.8

0.9

1.0

Figure 29-146.

Atmel ATmega324A: Reset supply current vs. frequency (1 - 20MHz).

2.5

2.0

5.5V

5.0V

4.5V

1.5

4.0V

1.0

3

.3V

0.5

2.7V

0

0 2 4

1.8V

6

8

10

Frequency [MHz]

12 14 16 18 20

421

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-147.

Atmel ATmega324A: Minimum reset pulsewidth vs. V

CC

.

1800

1500

1200

900

600

3

00

0

1.5

2.0

2.5

4.5

3

.0

3

.5

V

CC

[V]

4.0

5.0

5.5

8 5°C

25°C

-40°C

422

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.4

Atmel ATmega324PA typical characteristics

29.4.1

Active supply current

Figure 29-148.

Atmel ATmega324PA: Active supply current vs. low frequency (0.1 - 1.0MHz).

1.2

5.5V

1.0

0.8

5.0V

4.5V

4.0V

0.6

0.4

3 .3V

2.7V

1.8V

0.2

0

0 0.1

0.2

0.3

0.4

0.5

0.6

Frequency [MHz]

0.7

0.8

0.9

1.0

Figure 29-149.

Atmel ATmega324PA: Active supply current vs. frequency (1 - 20MHz).

14

5.5V

12

10

5.0V

4.5V

8

4.0V

6

4

3

.3V

2.7V

2

0

0 2 4

1.8V

6 8 10

Frequency [MHz]

12 14 16 18 20

423

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-150.

Atmel ATmega324PA: Active supply current vs. V

CC

8MHz).

(internal RC oscillator,

7

6

8

5°C

25°C

-40°C

5

4

3

2

1

0

1.5

2.0

2.5

3

.0

4.0

4.5

5.0

5.5

3

.5

V

CC

[V]

Figure 29-151.

Atmel ATmega324PA: Active supply current vs. V

CC

1MHz).

(internal RC oscillator,

1.6

8

5°C

25°C

-40°C

1.2

0.8

0.4

0

1.5

2.0

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

5.0

5.5

424

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-152.

Atmel ATmega324PA: Active supply current vs. V

CC

128kHz).

(internal RC oscillator,

0.25

0.20

-40°C

25°C

8

5°C

0.15

0.10

0.05

29.4.2

0

1.5

2.0

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

5.0

5.5

Idle supply current

Figure 29-153.

Atmel ATmega324PA: Idle supply current vs. V

CC

(0.1 - 1.0MHz).

0.25

0.20

0.15

0.10

5.5V

5.0V

4.5V

4.0V

3 .3V

2.7V

1.8V

0.05

0

0 0.1

0.2

0.3

0.4

0.5

Frequency [MHz]

0.6

0.7

0.8

0.9

1.0

425

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-154.

Atmel ATmega324PA: Idle supply current vs. V

CC

(1 - 20MHz).

4

3

2

4.0V

3 .3V

1

2.7V

0

0 2 4

1.8V

6

8

10

Frequency [MHz]

12 14 16 18 20

5.5V

5.0V

4.5V

Figure 29-155.

Atmel ATmega324PA: Idle supply current vs. V

CC

(internal RC oscillator, 8MHz).

1.8

1.5

8 5°C

25°C

-40°C

1.2

0.9

0.6

0.3

0

1.5

2.0

2.5

4.0

4.5

5.0

5.5

3

.0

3

.5

V

CC

[V]

426

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-156.

Atmel ATmega324PA: Idle supply current vs. V

CC

(internal RC oscillator, 1MHz).

0.6

8

5°C

25°C

-40°C

0.5

0.4

0.3

0.2

0.1

0

1.5

2.0

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

5.0

5.5

Figure 29-157.

Atmel ATmega324PA: Idle supply current vs. V

CC

(internal RC oscillator,

128kHz).

0.12

0.10

-40°C

25°C

8 5°C

0.08

0.06

0.04

0.02

0

1.5

2.0

2.5

4.0

4.5

5.0

5.5

3

.0

3

.5

V

CC

[V]

427

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.4.3

Example

Supply current of I/O modules

The tables and formulas below can be used to calculate the additional current consumption for the different I/O modules in Active and Idle mode. The enabling or disabling of the I/O modules are controlled by the Power Reduction Register. See

”PRR0 – Power Reduction Register 0” on page 48 for details.

Table 29-7.

Additional current consumption for the different I/O modules (absolute values).

PRR bit

PRUSART1

PRUSART0

PRTWI

PRTIM2

PRTIM1

PRTIM0

PRADC

PRSPI

Typical numbers in

V

CC

= 2V, F = 1MHz

3.1µA

3.0µA

6.4µA

5.6µA

3.6µA

1.7µA

11.8µA

5.3µA

V

CC

= 3V, F = 4MHz

21.5µA

21.0µA

45.7µA

37.7µA

24.8µA

10.4µA

59.2µA

40.1µA

V

CC

= 5V, F = 8MHz

100.0µA

98.2µA

214.5µA

165.8µA

107.0µA

43.2µA

257.0µA

206.8µA

Table 29-8.

Additional current consumption (percentage) in Active and Idle mode.

PRR bit

PRUSART1

PRUSART0

PRTWI

PRTIM2

PRTIM1

PRTIM0

PRADC

PRSPI

Additional current consumption compared to Active with external clock (see Figure 29-148 on page

423 and

Figure 29-149 on page

423

)

1.4%

1.4%

3.0%

2.5%

1.6%

0.7%

4.2%

2.7%

Additional current consumption compared to Idle with external clock (see

Figure 29-153 on page

425 and

Figure 29-154 on page

426 )

5.3%

5.2%

11.3%

9.1%

6.0%

2.5%

14.8%

10.3%

It is possible to calculate the typical current consumption based on the numbers from Table 29-8 on page 428 for other V

CC

and frequency settings than listed in Table 29-7 on page 428 .

Calculate the expected current consumption in idle mode with TIMER1, ADC, and SPI enabled at V

CC

= 2.0V and F = 1MHz. From Table 29-8 on page 428 , third column, we see that we need to add 6.0% for the TIMER1, 14.8% for the ADC, and 10.3% for the SPI module. Reading from

Figure 29-153 on page 425

, we find that the idle current consumption is ~0.078mA at V

CC

= 2.0V

and F = 1MHz. The total current consumption in idle mode with TIMER1, ADC, and SPI enabled, gives:

I

CC total

0.078mA (1+ 0.060 + 0.148 + 0.103)

0.102mA

428

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.4.4

Power-down Supply Current

Figure 29-158.

Atmel ATmega324PA: Power-down supply current vs. V

CC disabled).

(watchdog timer

1.2

8

5°C

1.0

0.8

0.6

0.4

0.2

0

1.5

2.0

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

5.0

25°C

-40°C

5.5

Figure 29-159.

Atmel ATmega324PA: Power-down supply current vs. V

CC

(watchdog timer enabled).

10

8

-40°C

8

5°C

25°C

6

4

2

0

1.5

2.0

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

5.0

5.5

429

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.4.5

Power-save supply current

Figure 29-160.

Atmel ATmega324PA: Power-save supply current vs. V

CC

(watchdog timer dis-

2.50

2.00

1.50

1.00

0.50

8 5°C

25°C

-40°C

0

1.5

2.0

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

5.0

5.5

29.4.6

Standby supply current

Figure 29-161.

Atmel ATmega324PA: Standby supply current vs. V

CC

(watchdog timer disabled).

0.18

0.16

0.14

0.12

0.10

0.08

0.06

0.04

0.02

0

1.5

2.0

2.5

3

.0

4.0

4.5

5.0

6MHz_res

6MHz_xtal

5.5

3

.5

V

CC

[V]

4MHz_res

4MHz_xtal

2MHz_res

2MHz_xtal

450kHz_res

430

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.4.7

Pin pull-up

Figure 29-162.

Atmel ATmega324PA: I/O pin pull-up resistor current vs. input voltage (V

CC

=

1.8V).

50

40

3 0

20

10

0

0 0.2

0.4

0.6

0.8

1.0

V

OP

[V]

1.2

1.4

1.6

1.8

2.0

25°C

-40°C

8

5°C

Figure 29-163.

Atmel ATmega324PA: I/O pin pull-up resistor current vs. input voltage (V

CC

=

2.7V).

60

50

40

3 0

20

8 0

70

10

0

0 0.5

1.0

2.0

2.5

1.5

V

OP

[V]

3 .0

25°C

8 5°C

-40°C

431

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-164.

Atmel ATmega324PA: I/O pin pull-up resistor current vs. input voltage (V

CC

=

5V).

140

40

20

0

0

120

100

8

0

60

1 2 3

V

OP

[V]

4 5 6

25°C

8 5°C

-40°C

Figure 29-165.

Atmel ATmega324PA: Reset pull-up resistor current vs. reset pin voltage

(V

CC

= 1.8V).

3

5

3 0

25

20

15

10

5

0

0 0.2

0.4

0.6

0.8

1.0

V

RESET

[V]

1.2

1.4

1.6

1.8

25°C

-40°C

8 5°C

2.0

432

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-166.

Atmel ATmega324PA: Reset pull-up resistor current vs. reset pin voltage

(V

CC

= 2.7V).

60

50

40

3 0

20

10

0

0 0.5

1.0

1.5

V

RESET

[V]

2.0

2.5

3

.0

25°C

-40°C

8

5°C

Figure 29-167.

Atmel ATmega324PA: Reset pull-up resistor current vs. reset pin voltage (V

CC

=

5V).

120

100

8 0

60

40

20

0

0 1 2

3

V

RESET

[V]

4 5 6

25°C

-40°C

8

5°C

433

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.4.8

Pin driver strength

Figure 29-168.

Atmel ATmega324PA: I/O pin output voltage vs. sink current (V

CC

= 3V).

1.0

8

5°C

0.8

25°C

0.6

-40°C

0.4

0.2

0

5 8 11

I

OL

[mA]

14 17 20

Figure 29-169.

Atmel ATmega324PA: I/O pin output voltage vs. sink current (V

CC

= 5V).

0.6

8 5°C

0.5

25°C

0.4

-40°C

0.3

0.2

0.1

0

5

8

11

I

OL

[mA]

14 17 20

434

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-170.

Atmel ATmega324PA: I/O pin output voltage vs. source current (V

CC

= 3V).

3

.0

2.5

2.0

1.5

1.0

0.5

0

5

8

11

I

OH

[mA]

14 17 20

-40°C

25°C

8 5°C

Figure 29-171.

Atmel ATmega324PA: I/O pin output voltage vs. source current (V

CC

= 5V).

4.9

4.8

4.7

4.6

4.5

4.4

4.3

5

8

11

I

OH

[mA]

14 17 20

-40°C

25°C

8

5°C

435

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.4.9

Pin threshold and hysteresis

Figure 29-172.

Atmel ATmega324PA: I/O pin input threshold vs. V

CC

(V

IH

, I/O pin read as ‘1’).

3

.0

2.5

8 5°C

-40°C

25°C

2.0

1.5

1.0

0.5

0

1.5

2.0

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

5.0

5.5

Figure 29-173.

Atmel ATmega324PA: I/O pin input threshold vs. V

CC

(V

IL

, I/O pin read as ‘0’).

2.5

-40°C

8 5°C

25°C

2.0

1.5

1.0

0.5

0

1.5

2.0

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

5.0

5.5

436

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-174.

Atmel ATmega324PA: I/O pin input hysteresis vs. V

CC

.

0.6

0.3

0.2

0.1

0.5

0.4

0

1.5

2.0

2.5

4.0

4.5

3

.0

3

.5

V

CC

[V]

5.0

5.5

8

5°C

25°C

-40°C

Figure 29-175.

Atmel ATmega324PA: Reset pin input threshold vs. V

CC

(V

IH

, I/O pin read as ‘1’).

2.5

-40°C

8 5°C

25°C

2.0

1.5

1.0

0.5

0

1.5

2.0

2.5

3

.0

3

.5

V

CC

[V]

4.0

4.5

5.0

5.5

437

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-176.

Atmel ATmega324PA: Reset pin input threshold vs. V

CC

(V

IL

, I/O pin read as ‘0’).

2.5

-40°C

25°C

8

5°C

2.0

1.5

1.0

0.5

0

1.5

2.0

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

5.0

5.5

Figure 29-177.

Atmel ATmega324PA: Reset pin input hysteresis vs. V

CC

.

0.7

0.6

0.5

0.4

0.3

0.2

0.1

0

1.5

2.0

2.5

3

.0

4.0

4.5

5.0

3

.5

V

CC

[V]

-40°C

25°C

5.5

8

5°C

438

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.4.10

BOD threshold

Figure 29-178.

Atmel ATmega324PA: BOD threshold vs. temperature (V

BOT

= 4.3V).

4.40

Rising Vcc

4.38

4.36

4.34

4.32

4.30

4.28

-40 -20 0 20 40

Temperature [°C]

60

Falling Vcc

8

0 100

Figure 29-179.

Atmel ATmega324PA: BOD threshold vs. temperature (V

BOT

= 2.7V).

2.80

Rising Vcc

2.78

2.76

2.74

2.72

2.70

2.68

2.66

-40 -20 0 20 40

Temperature [°C]

60

Falling Vcc

8 0 100

439

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-180.

Atmel ATmega324PA: BOD threshold vs. temperature (V

BOT

= 1.8V).

1.86

Rising Vcc

1.84

1.82

1.80

1.78

1.76

-40 -20 0 20 40

Temperature [°C]

60

Falling Vcc

8

0 100

Figure 29-181.

Atmel ATmega324PA: Calibrated bandgap voltage vs. V

CC

.

1.098

1.096

1.094

1.092

1.090

1.088

1.086

1.084

1.082

1.080

1.078

1.076

1.5

2.0

2.5

3 .0

3 .5

Vcc [V]

4.0

4.5

5.0

8 5°C

25°C

-40°C

5.5

440

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-182.

Atmel ATmega324PA: Bandgap voltage vs. temperature.

1.097

1.095

1.093

1.091

1.089

1.087

1.085

1.083

1.081

1.079

1.077

-40 -30 -20 -10 0 10 20

3

0 40 50 60 70

8

0 90

Temperature [°C]

1.8V

3 .6V

2.7V

4.5V

5.5V

29.4.11

Internal oscillator speed

Figure 29-183.

Atmel ATmega324PA: Watchdog oscillator frequency vs. temperature.

122

119

116

113

110

-40 -20

2.1V

2.7V

3 .3V

4.0V

5.5V

0 20 40

Temperature [°C]

60 8 0 100

441

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-184.

Atmel ATmega324PA: Watchdog oscillator frequency vs. V

CC

.

123

120

117

-40°C

25°C

114

111

1.5

2.0

2.5

3

.0

3

.5

V

CC

[V]

4.0

4.5

5.0

5.5

8

5°C

Figure 29-185.

Atmel ATmega324PA: Calibrated 8MHz RC oscillator vs. V

CC

.

8 .6

8

.2

8

5°C

25°C

7.8

-40°C

7.4

7.0

1.5

2.0

2.5

3

.0

3

.5

V

CC

[V]

4.0

4.5

5.0

5.5

442

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-186.

Atmel ATmega324PA: Calibrated 8MHz RC oscillator vs. temperature.

8 .6

5.0V

3 .0V

8 .3

8

.0

7.7

7.4

-40 -20 0 20 40

Temperature [°C]

60 8 0 100

Figure 29-187.

Atmel ATmega324PA: Calibrated 8MHz RC oscillator vs. OSCCAL value.

12

10

8

6

16

14

4

2

0

0 16 3 2 48 64 8 0 96 112 128 144 160 176 192 208 224 240 256

OSCCAL (X1)

8 5°C

25°C

-40°C

443

ATmega164A/PA/324A/PA/644A/PA/1284/P

29.4.12

Current consumption of peripheral units

Figure 29-188.

Atmel ATmega324PA: ADC current vs. V

CC

(AREF = AV

CC

).

3 00

250

200

150

100

50

0

1.5

2.0

2.5

4.0

4.5

5.0

3

.0

3

.5

V

CC

[V]

5.5

25°C

8 5°C

-40°C

Figure 29-189.

Atmel ATmega324PA: Analog comparator current vs. V

CC

.

90

8

0

70

60

50

40

3

0

20

10

0

1.5

2.0

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

5.0

5.5

-40°C

25°C

8

5°C

444

8272D–AVR–05/12

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-190.

Atmel ATmega324PA: AREF external reference current vs. V

CC

.

200

25°C

8 5°C

-40°C

160

120

8

0

40

0

1.5

2.0

2.5

3

.0

3

.5

V

CC

[V]

4.0

4.5

5.0

5.5

Figure 29-191.

Atmel ATmega324PA: Brownout detector current vs. V

CC

.

25

20

15

10

5

0

1.5

2.0

2.5

3 .0

3 .5

V

CC

[V]

4.0

4.5

5.0

5.5

8 5°C

25°C

-40°C

445

8272D–AVR–05/12

ATmega164A/PA/324A/PA/644A/PA/1284/P

Figure 29-192.

Atmel ATmega324PA: Programming current vs. V

CC

.

14

12

10

8

6

4

2

0

1.5

2.0

2.5

3 .0