DIY Micromitter Stereo FM Transmitter

DIY Micromitter Stereo FM Transmitter
DIY Micromitter Stereo FM
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At last!- a stereo FM transmitter that's a snack to align.
This new stereo FM Micromitter is capable of broadcasting good quality signals over a range of about 20 metres. It's ideal for
broadcasting music from a CD player or from any other source so that it can be picked up in another location.
For example, if you don't have a CD player in you car, you can use the Micromitter to broadcast signals from a portable CD
player to your car's radio. Alternatively, you might want to use the Micromitter to broadcast signals from your lounge-room CD
player to an FM receiver located in another part of the house or by the pool.
Because it's based on a single IC, this unit is a snack to build and fits easily into a small plastic utility box. It broadcasts on the
FM band (ie, 88-108MHz) so that its signal can be received on any standard FM tuner or portable radio.
However, unlike previous FM transmitters published in SILICON CHIP, this new design is not continuously variable over the FM
broadcast band. Instead, a 4-way DIP switch is used to select one of 14 preset frequencies. These are available in two ranges
covering from 87.7-88.9MHz and 106.7-107.9MHz in 0.2MHz steps.
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No tuning coils
Fig.1: block diagram of the Rohm BH1417F stereo FM transmitter IC. The text explains how it works.
We first published an FM stereo transmitter in SILICON CHIP in October 1988 and followed this up with a new
version in April 2001. Dubbed the Minimitter, these earlier versions were based on the popular Rohm BA1404
IC which is not being produced any more.
On both these earlier units, the alignment procedure requires careful adjustment of the ferrite tuning slugs within two coils (an
oscillator coil and a filter coil), so that the RF output matched the frequency selected on the FM receiver. However, some
constructors had difficulty with this because the adjustment was quite sensitive.
In particular, if you had a digital (ie, synthesised) FM receiver, you had to set the receiver to a particular frequency and then
carefully tune the transmitter frequency "through" it. In addition, there was some interaction between the oscillator and filter
coil adjustments and this confused some people.
That problem doesn't exist on this new design, since there is no frequency alignment procedure. Instead, all you have to do is
set the transmitter frequency using the 4-way DIP switch and then dial-up the programmed frequency on your FM tuner.
After that, it's just a matter of adjusting a single coil when setting up the transmitter, to set for correct RF operation.
Improved specifications
The new FM Stereo Micromitter is now crystal-locked which means that the unit does not drift off frequency over time. In
addition, the distortion, stereo separation, signal-to-noise ratio and stereo locking are much improved on this new unit
compared to the earlier designs. The specifications panel has further details.
BH1417F transmitter IC
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Fig.2: this frequency versus output level plot shows the composite level (pin 5). The 50ms pre-emphasis at around 3kHz causes
the rise in response, while the 15kHz low pass roll off produces the fall in response above 10kHz.
At the heart of the new design is the BH1417F FM stereo transmitter IC made by the Rhom Corporation. As
already mentioned, it replaces the now hard to find BA1404 that has been used in the previous designs.
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Fig.1 shows the internal features of the BH1417F. It includes all the processing circuitry required for stereo FM transmission and
also the crystal control section which provides precise frequency locking.
As shown, the BH1417F includes two separate audio processing sections, for the left and right channels. The left-channel audio
signal is applied to pin 22 of the chip, while the right channel signal is applied to pin 1. These audio signals are then applied to
a pre-emphasis circuit which boosts those frequencies above a 50ms time constant (ie, those frequencies above 3.183kHz)
prior to transmission.
Basically, pre-emphasis is used to improve the signal-to-noise ratio of the received FM signal. It works by using a
complementary de-emphasis circuit in the receiver to attenuate the boosted treble frequencies after demodulation, so that the
frequency response is restored to normal. At the same time, this also significantly reduces the hiss that would otherwise be
evident in the signal.
The amount of pre-emphasis is set by the value of the capacitors connected to pins 2 & 21 (note: the value of the time
constant = 22.7kΩ x the capacitance value). In our case, we use 2.2nF capacitors to set the pre-emphasis to 50μs which is the
Australian FM standard.
Signal limiting is also provided within the pre-emphasis section. This involves attenuating signals above a certain threshold, to
prevent overloading the following stages. That in turn prevents over-modulation and reduces distortion.
The pre-emphasised signals for the left and right channels are then processed through two low-pass filter (LPF) stages, which
roll off the response above 15kHz. This rolloff is necessary to restrict the bandwidth of the FM signal and is the same frequency
limit used by commercial broadcast FM transmitters.
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Fig.3: the frequency spectrum of the composite stereo FM signal. Note the spike of the pilot tone at 19kHz.
The outputs from the left and right LPFs are in turn applied to a multiplex (MPX) block. This is used to
effectively produce sum (left plus right) and difference (left - right) signals which are then modulated onto a
38kHz carrier. The carrier is then suppressed (or removed) to provide a double-sideband suppressed carrier
signal. It is then mixed in a summing (+) block with a 19kHz pilot tone to give a composite signal output (with
full stereo encoding) at pin 5.
The phase and level of the 19kHz pilot tone are set using a capacitor at pin 19.
Fig.3 shows the spectrum of the composite stereo signal. The (L+R) signal occupies the frequency range from 0-15kHz. By
contrast, the double sideband suppressed carrier signal (L-R) has a lower sideband which extends from 23-38kHz and an upper
sideband from 38-53kHz. As noted, the 38kHz carrier is not present.
The 19kHz pilot tone is present, however, and this is used in the FM receiver to reconstruct the 38kHz subcarrier so that the
stereo signal can be decoded.
The 38kHz multiplex signal and 19kHz pilot tone are derived by dividing down the 7.6MHz crystal oscillator located at pins 13 &
14. The frequency is first divided by four to obtain 1.9MHz and then divided by 50 to obtain 38kHz. This is then divided by two
to derive the 19kHz pilot tone.
In addition, the 1.9MHz signal is divided by 19 to give a 100kHz signal. This signal is then applied to the phase detector which
also monitors the program counter output. This program counter is actually a programmable divider which outputs a divided
down value of the RF signal.
The division ratio of this counter is set by the voltage levels at inputs D0-D3 (pins 15-18). For example, when D0-D3 are all
low, the programmable counter divides by 877. Thus, if the RF oscillator is running at 87.7MHz, the divided output from the
counter will be 100kHz and this matches the frequency divided down from the 7.6MHz crystal oscillator (ie, 7.6MHz divided by 4
divided by 19).
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Fig.4: the complete circuit of the Stereo FM Micromitter. DIP switches S1-S4 set the RF oscillator frequency and this is
controlled by the PLL output at pin 7 of IC1. This output drives Q1 which in turn applies a control voltage to VC1 to vary its
capacitance. The composite audio output at pin 5 provides the frequency modulation.
In practice, the phase detector output at pin 7 produces an error signal to control the voltage applied to a
varicap diode. This varicap diode (VC1) is shown on the main circuit diagram (Fig.4) and forms part of the RF
oscillator at pin 9. Its frequency of oscillation is determined by the value of the inductance and the total parallel
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Since the varicap diode forms part of this capacitance, we can alter the RF oscillator frequency by varying its value. In
operation, the varicap diode's capacitance varies in proportion to the DC voltage applied to it by the output of the PLL phase
In practice, the phase detector adjusts the varicap voltage so that the divided RF oscillator frequency is 100kHz at the program
counter output. If the RF frequency drifts high, the frequency output from the programmable divider rises and the phase
detector will "see" an error between this and the 100kHz provided by the crystal division.
As a result, the phase detector reduces the DC voltage applied to the varicap diode, thereby increasing its capacitance. And this
in turn decreases the oscillator frequency to bring it back into "lock".
Conversely, if the RF frequency drifts low, the programmable divider output will be lower than 100kHz. This means that the
phase detector now increases the applied DC voltage to the varicap to decrease its capacitance and raise the RF frequency. As a
result, this PLL feedback arrangement ensures that the programmable divider output remains fixed at 100kHz and thus ensures
stability of the RF oscillator.
By changing the programmable divider we can change the RF frequency. So, for example, if we set the divider to 1079, the RF
oscillator must operate at 107.9MHz for the programmable divider output to remain at 100kHz.
Frequency modulation
Of course, in order to transmit audio information, we need to frequency modulate the RF oscillator. We do that by modulating
the voltage applied to the varicap diode using the composite signal output at pin 5.
Note, however, that the average frequency of the RF oscillator (ie, the carrier frequency) remains fixed, as set by the
programmable divider (or program counter). As a result, the transmitted FM signal varies either side of the carrier frequency
according to the composite signal level - ie, it is frequency modulated.
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Bandpass Filter Option
We've designed the PC board so that it can accept a different bandpass filter at the pin 11 RF output of IC1. This filter is made
by Soshin Electronics Co. and is labelled GFWB3. It is a small 3-terminal printed bandpass filter and operates in the 76108MHz frequency band.
The advantage of using this filter is that it has much steeper rolloff above and below the FM band. This results in less
sideband interference at other frequencies. The drawback is the filter is very difficult to obtain.
In practice, the filter replaces the 39pF capacitor, with the central earth terminal of the filter connecting to the PC board
earth. That is why there is a hole between the 39pF capacitor leads. The 39pF and 3.3pF capacitors and the 68nH and 680nH
inductors are then not required, while the 68nH inductor is replaced with a wire link.
Circuit details
Fig.5(a): this diagram shows how the four surface-mount parts are installed on the copper side of the PC board. Make sure that
IC1 & VC1 are correctly oriented.
Refer now to Fig.4 for the full circuit of the Stereo FM Micromitter. As expected, IC1 forms the main part of the
circuitry with a handful of other components added to complete the FM stereo transmitter.
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The left and right audio input signals are fed in via 1μF bipolar capacitors and then applied to attenuator circuits consisting of
10kΩ fixed resistors and 10kΩ trimpots (VR1 & VR2). From there, the signals are coupled into pins 1 & 22 of IC1 via 1μF
electrolytic capacitors.
Note that the 1μF bipolar capacitors are included to prevent DC current flow due to any DC offsets at the signal source outputs.
Similarly, the 1μF capacitors on pins 1 & 22 are necessary to prevent DC current in the trimpots, since these two input pins are
biased at half-supply. This half-supply rail is decoupled using a 10μF capacitor at pin 4 of IC1.
The 2.2nF pre-emphasis capacitors are at pins 2 & 21, while the 150pF capacitors at pins 3 & 20 set the low-pass filter rolloff
point. The pilot level can be set with a capacitor at pin 19 - however, this is not usually necessary as the level is generally quite
suitable without adding the capacitor.
In fact, adding a capacitor here only reduces the stereo separation because the pilot tone phase is altered compared to the
38kHz multiplex rate.
The 7.6MHz oscillator is formed by connecting a 7.6MHz crystal between pins 13 & 14. In practice, this crystal is connected in
parallel with an internal inverter stage. The crystal sets the frequency of oscillation, while the 27pF capacitors provide the
correct loading.
Fig.5(b): here's how to install the parts on the top of the PC board to build the plugpack-powered version. Note that IC1, VC1
and the 68nH & 680nH inductors are surface mount devices and are mounted on the copper side of the board as shown in
The programmable divider (or program counter) is set using switches at pins 15, 16, 17 & 18 (D0-D3). These
inputs are normally held high via 10kΩ resistors and pulled low when the switches are closed. Table 1 shows
how the switches are set to select one of 14 different transmission frequencies.
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The RF oscillator output is at pin 9. This is a Colpitts oscillator and is tuned using inductor L1, the 33pF & 22pF fixed capacitors
and varicap diode VC1.
The 33pF fixed capacitor performs two functions. First, it blocks the DC voltage applied to VC1 to prevent current from flowing
into L1. And second, because it is in series with VC1, it reduces the effect of changes in the varicap capacitance, as "seen" by
pin 9.
This, in turn, reduces the overall frequency range of the RF oscillator due to changes in the varicap control voltage and allows
better phase lock loop control.
Similarly, the 10pF capacitor prevents DC current flow into L1 from pin 9. Its low value also means that the tuned circuit is only
loosely coupled and this allows a higher Q factor for the tuned circuit and easier starting of the oscillator.
Modulating the oscillator
Fig.6: here's how to modify the board for the battery-powered version. It's just a matter of leaving out D1, ZD1 & REG1 and
installing a couple of wire links.
The composite output signal appears at pin 5 and is fed via a 10μF capacitor to trimpot VR3. This trimpot sets
the modulation depth. From there, the attenuated signal is fed via another 10μF capacitor and two 10kΩ
resistors to varicap diode VC1.
As mentioned previously, the phase lock loop control (PLL) output at pin 7 is used to control the carrier frequency. This output
drives high-gain Darlington transistor Q1 and this, in turn, applies a control voltage to VC1 via two 3.3kΩ series resistors and
the 10kΩ isolating resistor.
The 2.2nF capacitor at the junction of the two 3.3kΩ resistors provides high-frequency filtering.
Additional filtering is provided by the 100μF capacitor and 100Ω resistor connected in series between Q1's base and collector.
The 100Ω resistor allows the transistor to respond to transient changes, while the 100μF capacitor provides low-frequency
filtering. Further high-frequency filtering is provided by the 47nF capacitor connected directly between Q1's base and collector.
The 5.1kΩ resistor connected to the 5V rail provides the collector load. This resistor pulls Q1's collector high when the transistor
is off.
FM output
The modulated RF output appears at pin 11 and is fed to a passive LC bandpass filter. Its job is to remove any harmonics
produced by the modulation and in the RF oscillator output. Basically, the filter passes frequencies in the 88-108MHz band but
rolls off signal frequencies above and below this.
The filter has a nominal impedance of 75Ω and this matches both IC1's pin 11 output and the following attenuator circuit.
Two 39Ω series resistors and a 56W shunt resistor form the attenuator and this reduces the signal level into the antenna. This
attenuator is necessary to ensure that the transmitter operates at the legal allowable limit of 10μW.
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Power supply
Fig.7: this diagram shows the winding details for coil L1. The former will have to be trimmed so that it sits no more than 13mm
above the board surface. Use silicone sealant to holder the former in place, if necessary.
Power for the circuit is derived from either a 9-16V DC plugpack or a 6V battery.
In the case of a plugpack supply, the power is fed in via on/off switch S5 and diode D1 which provides reverse polarity
protection. ZD1 protects the circuit against high-voltage transients, while regulator REG1 provides a steady +5V rail to power
the circuit.
Alternatively, for battery operation, ZD1, D1 and REG1 are not used and the through connections for D1 and REG1 are shorted.
The absolute maximum supply for IC1 is 7V, so 6V battery operation is suitable; eg 4 x AAA cells in a 4 x AAA holder.
A single PC board coded 06112021 and measuring just 78 x 50mm holds all the parts for the Micromitter. This is housed into a
plastic case measuring 83 x 54 x 30mm.
First, check that the PC board fits neatly into the case. The corners may need to be shaped to fit over the corner pillars on the
box. That done, check that the holes for the DC socket and RCA socket pins are the correct size. If L1's former doesn't have a
base (see below), it is mounted by pushing it into a hole that is just sufficiently tight to hold it in place. Check that this hole has
the correct diameter.
Fig.5(a) & Fig.5(b) show how the parts are mounted on the PC board. The first job is to install several surface-mount
components on the copper side of the PC board. These parts include IC1, VC1 and two inductors.
You will need a fine-tipped soldering iron, tweezers, a strong light and a magnifying glass for this job. In particular, the
soldering iron tip will have to be modified by filing it to a narrow screwdriver shape.
It's best to install the four surface-mount parts first (including the IC), before installing the remaining parts on the top of the PC
board. Note how the body of the crystal lies across the two adjacent 10kΩ resistors (left photo).
IC1 and the varicap diode (VC1) are polarised devices, so be sure to orient them as shown on the overlay. Each part is installed
by holding it in place with the tweezers and then soldering one lead (or pin) first. That done, check that the component is
correctly positioned before carefully soldering the remaining lead(s).
In the case of the IC, it's best to first lightly tin the underside of each of its pins before placing it onto the PC board. It's then
just a matter of heating each lead with the soldering iron tip to solder it in place.
Be sure to use a strong light and a magnifying glass for this work. This will not only make the job easier but will also allow you
to check each connection as it is made. In particular, make sure that there are no shorts between adjacent tracks or IC pins.
Finally, use your multimeter to check that each pin is indeed connected to its respective track on the PC board.
The remaining parts are all mounted on the top side of the PC board in the usual manner. If you are building the plugpackpowered version, follow the overlay diagram shown in Fig.5. Alternatively, for the battery powered version, leave out ZD1 and
the DC socket and replace D1 & REG1 with wire links as shown in Fig.6.
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Top assembly
Begin the top assembly by installing the resistors and wire links. Table 3 shows the resistor colour codes but
we also recommend that you use a digital multimeter to check the values. Note that most of the resistors are
mounted end-on to save space.
Once the resistors are in, install PC stakes at the antenna output and the TP GND and TP1 test points. This will make it much
easier to connect to these points later on.
Next, install trimpots VR1-VR3 and the PC-mount RCA sockets. The DC socket, diode D1 and ZD1 can then be inserted for the
plugpack-powered version.
The capacitors can go in next, taking care to install the electrolytic types with the correct polarity. The NP (non-polarised) or
bipolar (BP) electrolytic types can be installed either way. Push them all the way down into their mounting holes, so that they
sit no more than 13mm above the PC board (this is to allow the lid to fit correctly when the AAA batteries are mounted under
the PC board inside the box).
The ceramic capacitors can also be installed at this stage. Table 2 shows their marking codes, to make it easy for you to
identify the values.
Coil L1
Fig.7 shows the winding details for coil L1. It comprises 2.5 turns of 0.5 - 1mm enamelled copper wire (ECW) wound onto a
tapped coil former fitted with an F29 ferrite slug. Alternatively, you may also use any commercially made 2.5 turns variable
Two types of formers are available - one with a 2-pin base (which can be soldered directly to the PC board) and one that comes
without a base. If the former has a base, it will first have to be shortened by about 2mm, so that its overall height (including
the base) is 13mm. This can be done using a fine-toothed hacksaw.
That done, wind the coil, terminate the ends directly on the pins and solder the coil into position. Note that the turns are
adjacent to each other (ie, the coil is close wound).
This photo shows how the case is drilled to take the RCA sockets, the power socket and the antenna lead.
Alternatively, if the former doesn't have a base, cut off the collar at one end, then drill a hole in the PC board at the L1 position
so that the former is a tight fit. That done, push the former into its hole, then wind the coil so that the lowest winding sits on
the top surface of board.
Be sure to strip away the insulation from the wire ends before soldering the leads to the PC board. A few dabs of silicone
sealant can then be used to ensure that the coil former stays in place.
Finally, the ferrite slug can be inserted into the former and screwed in so that its top is about flush with the top of the former.
Use a suitable plastic or brass alignment tool to screw in the slug - an ordinary screwdriver may crack the ferrite.
Crystal X1 can now be installed. This is mounted by first bending its leads by 90 degrees, so that it sits horizontally across the
two adjacent 10kΩ resistors (see photo). The board assembly can now be completed by installing the DIP switch, transistor Q1,
regulator (REG1) and the antenna lead.
The antenna is simply a half-wave dipole type. It consists of a 1.5m length of insulated hookup wire, with one end soldered to
the antenna terminal. This should give good results as far as transmission range is concerned.
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the case
Attention can now be turned to the plastic case. This requires holes at one end to accommodate the RCA
sockets, plus holes at the other end for the antenna lead and the DC power socket (if used).
In addition, a hole must be drilled in the lid for the power switch.
The circuit can be powered from 4 x 1.5V AAA cells if you wish to make the unit portable. Note that the battery holder requires
some modification in order to fit everything inside the case (see text).
It's also necessary to remove the internal side mouldings along the walls of the case to a depth of 15mm below the top edge of
the box, in order to fit the PC board. We used a sharp chisel to remove these but a small grinder could be used instead. That
done, you also need to remove the end ribs under the lid in order to clear the tops of the RCA and DC sockets. The front-panel
label can then be attached to the lid.
The battery-powered version has a AAA cell-holder mounted upside down in the box, with the base of the holder in contact with
the copper side of the PC board. There is just sufficient room for this holder and the PC board to mount inside the case with the
following provisos:
(1). All parts except for power switch S5 must not protrude above the surface of the PC board by more than 13mm. This means
that the electrolytic capacitors must sit close to the PC board and that L1's former must be cut to the correct length.
(2). The AAA cell holder is about 1mm too thick and should be filed down at each end, so that the cells protrude slightly over
the top of the holder.
(3). The tops of the RCA sockets may also require shaving slightly, so that there is no gap between the box and the lid after
ACA Compliance
This FM broadcast band stereo transmitter is required to comply with the Radiocommunications Low Interference Potential
Devices (LIPD) Class Licence 2000, as issued by the Australian Communications Authority.
In particular, the frequency of transmission must be within the 88-108MHz band at a EIRP (Equivalent Isotropically Radiated
Power) of 10mW and with FM modulation no greater than 180kHz bandwidth. The transmission must not be on the same
frequency as a radio broadcasting station (or repeater or translator station) operating within the licence area.
Further information can be found on the web site.
The class licence information for LIPDs can be downloaded from:
Test & adjustment
This part is a real snack. The first job is to tune L1 so that the RF oscillator operates over the correct range. To do that, follow
this the step-by-step procedure:
(1). Set the transmission frequency using the DIP switches, as shown in Table 1. Note that you need to select a frequency that
is not used as a commercial station in your area, otherwise interference will be a problem.
(2). Connect your multimeter's common lead to TP GND and its positive lead of to pin 8 of IC1. Select a DC volts range on the
meter, apply power to the Micromitter and check that you get a reading that's close to 5V if you're using a DC plugpack.
Alternatively, the meter should show the battery voltage if you're using AAA cells.
(3). Move the positive multimeter lead to TP1 and adjust the slug in L1 for a reading of about 2V.
The battery holder sits in the bottom of the case, beneath the PC board.
The oscillator is now correctly tuned. No further adjustments to L1 should be required if you subsequently switch to another
frequency within the selected band. However, if you change to a frequency that's in the other band, L1 will have to be
readjusted for a reading of 2V at TP1.
Setting the trimpots
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Fig.8: the full-size front-panel artwork.
All that remains now is to adjust trimpots VR1-VR3 to set the signal level and modulation depth. The step-bystep procedure is as follows:
(1). Set VR1, VR2 & VR3 to their centre positions. VR1 and VR2 can be adjusted by passing a screwdriver through the centres
of the RCA μ sockets, while VR3 can be adjusted by moving the μF capacitor in front of it to one side.
(2). Tune a stereo FM tuner or radio to the transmitter frequency. The FM tuner and transmitter should initially be placed about
two metres apart.
(3). Connect a stereo signal source (eg, a CD player) to the RCA socket inputs and check that this is received by the tuner or
Fig.9: full-size etching pattern for the PC board.
(4). Adjust VR3 anticlockwise until the stereo indicator goes out on the receiver, then adjust VR3 clockwise
from this position by 1/8th of a turn.
(5). Adjust VR1 and VR2 for best sound from the tuner - you will have to temporarily disconnect the signal source to make each
adjustment. There should be sufficient signal to "eliminate" any background noise but without any noticeable distortion.
Note particularly that VR1 and VR2 must each be set to the same position, to maintain the left and right channel balance.
That's it - your new Stereo FM Micromitter is ready for action.
Table 2: Capacitor Codes
Table 3: Resistor
IEC Code
Colour Codes
4-Band Code (1%)
red red orange brown
brown black orange brown
green brown red brown
orange orange red brown
brown black brown brown
green blue black brown
orange white black brown
Parts List
1 PC board, code 06112021, 78 x 50mm.
1 plastic utility box, 83 x 54 x 31mm
EIA Code
5-Band Code (1%)
red red black red brown
brown black black red brown
green brown black brown brown
orange orange black brown brown
brown black black black brown
green blue black gold brown
orange white black gold brown
front panel label, 79 x 49mm
7.6MHz or 7.68MHz crystal
SPDT subminiature switch (Jaycar ST-0300, Altronics S 1415 or equiv.) (S5)
PC-mount RCA sockets (switched) (Altronics P 0209, Jaycar PS 0279)
2.5mm PC-mount DC power socket
4-way DIP switch
2.5 turns variable coil (L1)
4mm F29 ferrite slug
680nH (0.68μH) surface mount inductor (1210A case) (Farnell 608-282 or similar)
68nH surface mount inductor (0603 case) (Farnell 323-7886 or similar)
100mm length of 1mm enamelled copper wire
50mm length of 0.8mm tinned copper wire
1.6m length of hookup wire
PC stakes
4 x AAA cell holder (required for battery operation)
AAA cells (required for battery operation)
10kΩ vertical trimpots (VR1-VR3)
BH1417F Rohm surface-mount FM stereo transmitter (IC1)
78L05 low-power regulator (REG1)
MPSA13 Darlington transistor (Q1)
ZMV833ATA or MV2109 (VC1)
24V 1W zener diode (ZD1)
1N914, 1N4148 diode (D1)
100μF 16VW PC electrolytic
10μF 25VW PC electrolytic
1μF bipolar electrolytic
1μF 16VW electrolytic
47nF (.047μF) MKT polyester
10nF (.01μF) ceramic
2.2nF (.0022μF) MKT polyester
330pF ceramic
150pF ceramic
39pF ceramic
33pF ceramic
27pF ceramic
22pF ceramic
10pF ceramic
3.3pF ceramic
Resistors (0.25W, 1%)
22kΩ 1 100Ω
10kΩ 1 56Ω
5.1kΩ 2 39Ω
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Transmission frequencies
Total Harmonic Distortion (THD)
Low Pass Filter
Channel separation
Channel balance
Pilot modulation
RF Output power (EIRP)
Supply voltage
Supply current
Audio input level
87.7MHz to 88.9MHz in 0.2MHz steps
106.7MHz to 107.9MHz in 0.2MHz steps (14 total)
typically 0.1%
typically 50ms
typically 40dB
within ?2dB (can be adjusted with trimpots)
typically 10μW when using inbuilt attenuator
28mA at 5V
220mV RMS maximum at 400Hz and 1dB compression limiting
You can buy products mentioned in this article here :
The following downloads are available for this article:
Micromitter Front Panel (PDF)
Micromitter PCB (PDF)
Micromitter Front Panel (ZIP)
Micromitter PCB (ZIP)
Click here to buy Our DIY 5W PLL Digital LCD Stereo FM
Transmitter PCB Kit Suite
List all Question
zakaria(176.17.14.*) Post:10/31/2011 2:31:32 AM
please provide me with your products
Reply to:you can visit our website www.fmuser.orgMany products, let me know which models you are interested in.
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