B&K Precision 3010 User Manual

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TEST INSTRUMENT SAFETY
WARNING
Normal use of test equipment exposes you to a certain amount of danger from electrical shock
because testing must often be performed where exposed voltage is present. An electrical shock
causing 10 miliamps of current to pass through the heart will stop most human heartbeats. Voltage
as low as 35 volts dc or ac rms should be considered dangerous and hazardous since it can produce
a lethal current under certain conditions. Higher voltages pose an even greater threat because such
voltage can more easily produce a lethal current. Your normal work habitis should include all ac-
cepted practices that will prevent contact with exposed high voltage, and that will steer current
away from your heart is case of accidental contact with a high voltage. You will significantly
reduce the risk factor is you know and observe the following safety precautions:
1.
Don’t expose high voltage needlessly. Remove housings and covers only when necessary.
Turn off equipment while making test connections in high-voltage circuits. Discharge high-
voltage capacitors after removing power.
Use an insulated floor material or a large, insulated floor mat to stand on, and an insulated
work surface on which to place equipment; and make certain such surfaces are not damp or
wet. Where insulated floor surface is not available, wear heavy gloves.
Use the time-proven ‘‘one hand in the pocket’ technique while handling an instrument
probe. Be particularly careful to avoid contacting a nearby metal object that could provide a
good ground return path.
Always use an isolation transformer to power transformerless ‘‘hot chassis’ equipment,
where one side of the ac power line is connected directly to the chassis. This includes most re-
cent television sets and audio equipment. Without an isolation transformer, the chassis of
such equipment may be floating at line voltage (120 VAC, 60 Hz in USA), depending upon
which way the 2-wire ac power plug is inserted. Not only does this present a dangerous shock
hazard if the chassis is touched, but damage to test instruments or the equipment under test
may result from connecting the ground lead of some test instruments to a ‘‘hot’’ chassis. The
ground lead of this function generator and most other test instruments with 3-wire power
plugs is at earth ground.
On test instruments or any equipment with a 3-wire ac power plug, use only a 3-wire outlet.
This is a safety feature to keep the housing or other exposed elements at earth ground.
If possible, familiarize yourself with the equipment being tested and the location of its high
votage points. However, remember that high voltage may appear at unexpected points in
defective equipment.
Also remember that ac line voltage is present on some power input current points such as on-
off switches, fuses, power transformers, etc., even when the equipment is turned off.
Never work alone. Someone should be nearby to render aid if necessary. Training on CPR
(cardo-pulmonary resuscitation) first aid is highly recommended.
INSTRUCTION MANUAL
FOR
MODEL 3010
FUNCTION GENERATOR
» 'DYNASCAN
ОДЕН CORPORATION
6460 W. Cortland Street
Chicago, Hlinois 60635
TABLE OF CONTENTS
PAGE
INTRODUCTION .........eeeereorercroerrererrrreerarerer 3
SPECIFICATIONS .......eooeeoeooorvorerrerecreeao rare reee. 3
PANEL CONTROLS AND FEATURES ......eo_.reoecsroerecrnereces 5
OPERATING INSTRUCTIONS
A. Frequency and Waveform Selection, Manual Operation ............. 8
B. DC Output ............ eee Cee 9
C. Voltage-Controlled Operation ..............eeereríevacoreeeos 10
D. TTL Output ........eoeoreescdocecrerererereríerecareree. 12
APPLICATIONS
A. Amplifier Frequency Response ........ee_eeceeereeccrreooercere 13
В. Tone Control Test 022440800000 04e 008 0 0 a as 0e 0 10000 13
C. Amplifier Overload Characteristic ..........e—eeeeeseroereoeaore. 13
D. Amplifier Performance Evaluation Using Square Waves ............. 16
E. Speaker System Testing ........... coi, 18
F. AM Receiver Alignment .......o_.ecrceororeccrosrerervrrerees 18
G. Using the 3010 As A Bias and Signal Source ...................... 20
H. Preset Frequency Selection ...........eeesesrerererererereene. 21
I. Digital Frequency Selection .........._..—ereererereorveecrare. 22
J. Communications Receiver Alignment ............. cc. inn. 23
К. Additional Applications ..........._reeeosrereroreerecrren. 23
THEORY OF OPERATION
General Circuit Description .........00400000000 000 HERE 25
Detailed Circuit Description .............re-reeecexererorern 27
MAINTENANCE AND CALIBRATION |
Removal of Rear Case ......reeereocorvovrrerrrrrorerrr erre. 31
Calibration Procedure ..........er_ewcococceoorerorreeerecereA. 32
Line Voltage Conversion .......0.0.000000000000 00 Kr ern EEE 36
WARRANTY SERVICE INSTRUCTIONS ...........eerrerererecceo: 37
ONE-YEAR LIMITED WARRANTY ..........eorerecoroveroreerer.. 38
2
INTRODUCTION
The B & K-PRECISION Model 3010 Function Generator is a versatile signal
source that can be used in a variety of engineering, industrial, educational and
hobbyist applications. The wide frequency range (.1 Hz to 1 MHz) for all functions
(sine, square, triangle and TTL output) encompasses subaudible, audio, ultrasonic
and RF applications. The continuously variable DC offset control and provision for
external VCO control further enhance the versatility of this instrument. The
human-engineered case lends itself to bench use as well as easy portability.
SPECIFICATIONS
GENERAL
Basic Outputs Square, sine, triangle, DC and TTL Square Wave
(separate output jack).
Frequency Range 0.1 Hz to 1 MHz in six ranges.
External Frequency
Control VCO; greater than 100:1 on any frequency range
(linear). With FREQUENCY dial set at .1, a
0-t0-5.5V ramp input will produce a 100:1 fre-
quency change. Frequency increases with positive
voltage.
Maximum Input +20 V peak.
Input Impedance 1000 ohms, nominal.
SPECIFICATIONS (All specifications apply with dial scale between 1 and 10)
Dial Accuracy 5% of full scale to 500 kHz, 8% of full scale from
500 kHz to 1 MHz (includes dial scale accuracy and
range-to-range accuracy). Unit calibrated at full scale.
Dial Range Greater than 100:1.
Output Impedance 60092, +5%.
Output Amplitude 20 V p-p open circuit;
10 V p-p into 60002.
Amplitude Control Continuously variable, greater than 30 dB range.
DC Offset
- Max. Vac + DC offset without clipping, £10V
| open circuit; +5 Vinto 60082. ВЕ
Sine Wave
Distortion
Square Wave
Non-Symmetry
Triangle Wave
Non-Linearity
Square Wave
Rise/Fall Time
Sine Wave Amplitude
Flatness
TTL Square Wave
Response
Short-Term
Stability
Power Requirements
Dimensions (HWD)
Weight
Handle
Continuously variable, +10 V, open circuit; +5 V,
into 60082. 0222
) ‘ Less ‘than 1%, 1 Hz to 100 kHz: harmonics more
than 30 dB down from fundamental, 100 KHz to |
ME Ns
Less than 1%, to 100 KHz.
. Less than 17%, to 100 KHz.
Less than 100 nSEC at maximum output amplitude.
+3 dB to 1 MHz at maximum output amplitude.
‘ ) Less than 25 nSEC rise/fal time. Fixed TTL level:
LO less than .4 V; HI greater than 2.4 V. Will drive
20 TTL loads.
‚05% A
105 to.130 VAC, 60 Hz. 8 watts max. | |
(105- 130/210-260 VAC, 50/60 Hz export version
. ; available)
32x113x7.7"
— (8.13 х 28.70х 19.56 ст.)
2 1bs., 9 ох. (1.16 Kg.) without line cord.
2 165., 14 oz. (1.31 Kg.) with line cord.
Four positions: integral part of case.
10.
PANEL CONTROLS AND FEATURES
(See Fig. 1)
. POWER on-off switch. Depressing this button turns the 3010 on. To tum off,
push again and release.
. RANGE selectors. Decade frequency type. Multiplying the range selected times
the FREQUENCY dial (6) indication gives the output frequency, which applies
for all functions. For example, if the 100 K RANGE button is depressed and
the FREQUENCY dial is at 10, the output frequency is 1 MHz.
. FUNCTION selectors. Select square (nn), sine (AN), or triangle (AA)
output waveform which appears at 6002 OUTPUT jack (9).
. AMPLITUDE control. Controls the amplitude of the output signal, which
appears at 6000 jack (9). This control does not apply to the DC OFFSET
voltage or to the TTL output.
. DC OFFSET control. Adds positive or negative DC component to the signal
appearing at 6000 OUTPUT jack (9). Continuously variable for +5 У
(600 ohms) or +10 V (open circuit). The DC component added by this control
is dependent of the adjustment of AMPLITUDE control (4).
. FREQUENCY dial. Multiplying the setting of this dial times the frequency of
the RANGE switch (2) selected gives the output frequency of the waveforms at
the 60002 OUTPUT jack (9) and TTL jack (7).
. TTL jack. A TTL square wave is available at this jack. The frequency is
determined by the RANGE selected and the setting of the FREQUENCY dial.
This output is independent of the AMPLITUDE and DC OFFSET controls.
(Ground) jack. Common reference for the TTL and 60092 OUTPUT signals.
6002 OUTPUT jack. Waveforms selected by FUNCTION switches as well as
the superimposed DC OFFSET voltage are available at this jack.
HANDLE. Multiple-position design permits use as a tilt stand or carrying
handle.
— 1 11. VCO INPUT jack (rear panel). An external voltage input will vary the output
frequency. The change in frequency is directly proportional to input voltage;
therefore, the rate of change of frequency is proportional to that of the input
voltage.
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TS: 12. LINE CORD RECEPTACLE (rear panel). This receptacle accepts the
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Hz export version.)
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Fig. 2. Rear panel.
Fig. 1. Front panel controls and features.
OPERATING INSTRUCTIONS
FREQUENCY AND WAVEFORM SELECTION, MANUAL OPERATION
1. With the unit plugged into a power source, depress the POWER button (1).
2. Select the frequency range desired by depressing the appropriate RANGE
switch. The frequency range obtained as the FREQUENCY dial (6) is
varied will be from one-tenth the indicated RANGE value to 10 times this
value. For example, select the 10 K range. When the FREQUENCY dial is
at .1, the output frequency is 1 KHz; when at 1, it is 10 KHz and when at
10 the frequency is 100 KHz. The frequency obtained applies to the signal
at the TTL jack as well as the 6009 OUTPUT jack.
3. Select the waveform desired by depressing the appropriate FUNCTION
button. The phase relationships of the waveforms available are shown in
Fig. 3.
4. The amplitude of the selected output signal at the 60042 OUTPUT jack is
adjusted by AMPLITUDE control (4). The TTL output is not affected by
the AMPLITUDE control.
5. ADC component can be added to the signal at the 60082 OUTPUT jack by
use of the DC OFFSET control. The DC component introduced is
independent of the AMPLITUDE control and does not apply to the TTL
output. The level of DC can be varied +10 volts open circuited or +5 volts
across 600 ohms.
TTL PULSE OV | —
TRIANGLE
SINE
SQUARE OV
Fig. 3. Output waveform and phase relationships.
+5V
A. ZERO DC OFFSET
WITH MAXIMUM ov
SIGNAL.
+5 жд — — —
B.OFFSET LIMITS ov — I —
WITHOUT CLIPPING.
— \ же = == = = о —— — —
POSITIVE NEGATIVE
DC OFFSET DC OFFSET
— il —— —Í—] Tr ms —— че
C.EXCESSIVE OFFSET.
POSITIVE | NEGATIVE
DC OFFSET DC OFFSET
Fig. 4. Use of DC OFFSET control.
Remember that the output signal swing of the generator is limited to +10
volts (open circuit) or +5 volts into 600 ohms. This applies to the
combined signal and DC offset. Clipping occurs slightly above these levels.
Fig. 4 illustrates the various operating conditions encountered, when using
the DC offset. If the desired output signal is large or if a large DC offset is
used, an oscilloscope should be used to make sure that the desired
combination is obtained without undesirable clipping.
When using the higher output frequencies and when using the square wave
and TTL outputs, terminate the cable in 600 ohms to minimize ringing.
Keep the cables as short as possible.
В. DC OUTPUT
The DC OFFSET feature can be used to convert the Model 3010 to a bipolar
DC power supply with an internal impedance of about 600 ohms.
1.
Depress the FUNCTION switches slightly so that all switches are released
(all buttons out). This removes all signal components from the output.
The output now consists of a DC voltage which can be varied continuously
from -10 volts to +10 volts (open circuit) by use of the DC OFFSET
control.
10
3. A decoupling capacitor (20 mfd or more) can be connected across the
60092 OUTPUT and ground (<=) terminals to reduce the AC impedance
of the output. Always observe polarity when using polarized capacitors.
VOLTAGE-CONTROLLED OPERATION
The 3010 can be operated as a voltage-controlled oscillator (VCO) by using an
external control voltage applied to the VCO IN jack at the rear of the unit. A
male phono plug is provided for this purpose. The externally applied voltage
will vary the frequency which is preselected by the RANGE switches and the
FREQUENCY dial. A positive-going voltage will increase the frequency and a
negative-going voltage will decrease the frequency. Please note that the
frequency does not change without limit as the input control voltage is
increased. The upper dial frequency can be exceeded by about 10 per cent. If
the control voltage reduces the lowest frequency available below the frequency
corresponding to the low end of the frequency dial (.1), erratic operation
results.
The desired frequency, output waveforms, DC offset, and the output
amplitude adjustment are selectéd as for manual operation. The maximum
voltage-controlled sweep is over a 100:1 range.
1. SWEEP FREQUENCY OPERATION
a. Select frequency range and function.
b. Set DC offset, if required.
c. Set amplitude to desired level.
d. To obtain maximum sweep, set the FREQUENCY dial to either
extreme. For this example, set at low end (.1 on FREQUENCY dial).
e. Connect a positive-going voltage to the VCO IN jack. A 0 to +5.5 volt
ramp will provide a frequency increase corresponding to a FRE-
QUENCY dial setting of 10. This is a 100:1 ratio. The frequency
varies in direct proportion to the applied input voltage.
2. FREQUENCY MODULATION
If an alternating voltage with no DC component is applied to the VCO IN
jack, the preset frequency will vary above and bglow the frequency that
was preset by the RANGE switch and FREQUENCY dial. The DC
component of such an input signal can be removed by transformer or
capacitive coupling.
Select frequency and function.
Set DC offset, if required.
Set amplitude to desired level.
Adjust the VCO IN voltage to provide the desired frequency
modulation.
The approximate frequency deviation obtained for a given VCO signal
can be determined as follows:
(1) .055 volt will produce a change in frequency equal to one per
cent of the highest frequency obtainable on a given range. For
example, if the 1 K RANGE is selected and the FREQUENCY
dial is at 10, the output frequency is 10 KHz. One per cent of
10 KHz is 100 Hz. Therefore, for each .055 volt change in the
VCO voltage, a 100 Hz change in frequency is produced with the
1 K RANGE selected, regardless of FREQUENCY dial setting.
(2) As an example, assume the RANGE switch and FREQUENCY
dial are set for 5 KHz output. If an alternating signal having an
amplitude of +.55 volt is is applied to the VCO IN jack, a
frequency swing of + (555) 100 = +1 KHz is obtained. The table
below indicates the frequency change per .055 volt input to the
VCO IN jack for each range.
Range, Min. Frequency, Hz | Max. Frequency, Hz | 1% Frequency Change,
Hz (Dial at .1) (Dial at 10) Hz (For .055 V input)
1 1 10 1
10 1 100 1
100 10 1K 10
1K 100 10K 100
10K 1K 100 K 1K
100 К 10K 1M 10K
11
D.
12
TTL OUTPUT
This is a fast rise time square wave output, available at the front panel. Because
of the fast transition times of this output, cable termination should be
provided to minimize ringing. The output is always positive with respect to
ground. This signal can be used as an external sync pulse for oscilloscopes when
using the other generator outputs. It also can be used as a variable frequency
signal source for exercising logic circuits.
1. Select desired frequency (repetition rate).
2. Connect to TTL output.
3. The AMPLITUDE and DC OFFSET controls have no effect on the TTL
output signal.
APPLICATIONS
A. AMPLIFIER FREQUENCY RESPONSE (See Fig. 5)
1. Interconnect equipment as indicated Fig. SA. This use of either the oscil-
loscope or the AC voltmeter to measure output voltage is adequate. The
advantage of the oscilloscope is that waveform distortion can be
simultaneously monitored, particularly if a power response curve is being
run. The AC voltmeter, provided with decibel scales, is convenient for
converting the observed output variations into standard units of measure-
ment (dB). The amplifier under test may be anything from a single stage
transistor amplifier to a high fidelity component type. The dual trace
oscilloscope is convenient for this application because the input to the
amplifier as well as the output can be monitored simultaneously.
2. Vary the frequency of the 3010 as required, maintaining a constant
amplitude as observed on the oscilloscope. The amplifier input and output
waveforms can be monitored simultaneously as indicated in Fig. 5b. Using
two centimeters for amplitude references provides a convenient method of
determining percent of change in amplitude.
3. The results of response tests can be plotted on semi-log paper as indicated
in Fig. 6.
TONE CONTROL TEST
If the amplifier under test is provided with base and treble controls, the effects
of these controls on overall response can be determined by running consecutive
response curves with the controls at both extremes of adjustment. The results
can be plotted on semi-log graph paper, as indicated in Fig. 7.
AMPLIFIER OVERLOAD CHARACTERISTIC
1. The overload point for some amplifiers is difficult to determine exactly
because of the gradual overload characteristic. The exact point of which
signal compression begins is difficult to determine using sine-wave input.
The triangle wave form is ideal for this type of test because any departure
from absolute linearity is readily detectable.
2. Using the test set-up of Fig. SA and using the triangle output, the peak
overload condition for an amplifier can be readily determined. This
overload condition is shown in Fig. 8.
13
Select waveform Dual Trace
as required No DC Offset Oscilloscope preferred
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720150 100 1K 10K
FREQUENCY, Hz
AC Voltmeter |
inati tput Load | ;
6004 Termination Output Loa | Fig. 6. Plot of amplifier frequency response.
A. TEST SET-UP.
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`В. WAVE SHAPE AND AMPLITUDE. FREQUENCY, Hz
Fig. 7. Tone control effectiveness.
Fig. 5. Amplifier frequency response, manual frequency change.
14 15
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Fig. 8. Amplifier overload characteristics.
D. AMPLIFIER PERFORMANCE EVALUATION USING SQUARE WAVES
16
The standard sine-wave frequency response curves, such as those obtained in
Par. A, do not give a full evaluation of the amplifier transient response. The
square wave, because of the high harmonic content, yields much information
regarding amplifier performance, when used in conjunction with an oscillo-
scope.
I.
Use the test set-up of Fig. 9A. This is similar to that used in Fig. 5A except
that a termination is specified at the amplifier input. This is essential when
using square waves to eliminate the ringing effects generated by the fast
rise times.
Using the triangle output of the 3010, set the AMPLITUDE control so
that there is no signal clipping over the range of frequencies to be used.
Select the square wave output and adjust the frequency to several check
points within the passband of the amplifier, such as 20 Hz, 1000 Hz and
10 KHz.
At each frequency check point the wave form obtained at the amplifier
output provides information regarding amplifier performance with respect
to the frequency of the square wave input. Fig. 9B indicates the possible
wave forms obtained at the amplifier output and the causes.
Square wave evaluation is not practical for narrow band amplifiers. The
restricted band width of the amplifier cannot reproduce all frequency
components of the square wave in the proper phase and amplitude relation-
ships.
No DC Offset
Dual Trace
Oscilloscope preferred
Lsquare wave
selected
30 Ma OSCALOSCORE 747
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Amplifier under test
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600 Y Termination
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A. TEST SET-UP.
—
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Frequency distortion {amplitude
reduction of low frequency
component). No phase shift.
Low freguency boost
(accentuated fundamental).
High frequency loss , No
phase shift.
Low frequency phase shift.
Low frequency loss and
phase shift.
High frequency loss and low
frequency phase.
High frequency loss and
phase shift.
=
Damped oscillation.
voltage).
=
Low frequency phase shift
(trace thickened by hum-
B. TEST WAVEFORMS.
Fig. 9. Amplifier performance evaluation, using square waves.
17
E. SPEAKER SYSTEM TESTING
18
The 3010 can be used to provide information regarding the input impedance of
speaker systems vs. frequency. In addition, the low-frequency resonance of the
system can be determined. Because the Model 3010 output impedance is
600 ohms, which is much higher than the impedance of conventional speaker
systems, the 3010 can be used as a variable frequency current source to
evaluate the input impedance of.the speaker system. This is shown in Fig. 10B.
1.
Use the test set-up Fig. 10A. An oscilloscope could be used in this set-up
to verify that the 3010 is not being operated in a clipping condition.
Vary the frequency of the 3010 over the full range of interest and log the
voltage measured at the speaker terminals vs. frequency. The dB scales of
the AC voltmeter are convenient for converting this information to
standard response units.
It will be observed that at some low frequency, a pronounced increase in
voltage will occur. This is the resonance frequency of the low-frequency
driver in the speaker system. This test set-up is convenient when designing
speaker enclosures. It can help the designer to determine the effect on
system resonance of varying port sizes, damping materials and other basic
enclosure factors.
The measurements obtained in the above tests can be plotted on semi-log
graph paper as indicated in Fig. 10C.
AM RECEIVER ALIGNMENT
Use the test set-up of Fig. 11. Because of the linear relationship between
sweep voltage and frequency of the Model 3010, a linear frequency
presentation is obtained on the oscilloscope, regardless of whether the
sweep voltage is a triangle, sine wave or a ramp.
To minimize the number of set-up adjustments required, the sweep voltage
to the VCO IN jack of the 3010 should not have a DC component. This
can be removed by capacitor coupling.
If a precise center frequency is required, a frequency counter should be
used when setting the output frequency of the 3010. This is done without
sweep voltage input.
The sweep voltage to the oscilloscope can be supplied either to an external
horizontal input jack or, if the oscilloscope has front panel X-Y capability,
it can be applied to one of the two vertical input jacks.
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A. Test Set-up
Lsine Wave
selected
AC Voltmeter
|
Speaker Enclosure
———— 300 __ _ Speaker System
| é & |
| 6000 T E LC voltmeter T Speaker |
| or |
| | | Z | System
| | | Oscilloscope | Z Impedance |
| © © |
Le 0 J bE ——— —
A. EQUIVALENT CIRCUIT OF TEST SET-UP.
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e low-frequency driver |
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FREQUENCY, Hz
B. GRAPH OF RESULTS.
Fig. 10. Speaker system tests.
19
5. Because of the wide frequency range of the 3010, the signal can be
"injected either at the mixer (455 KHz) or at the antenna (1 MHz). When
injecting the 455 KHz signal at the mixer input, the local oscillator must
be disabled.
6. When the IF response is observed at the input to the AM detector, an RF
detector probe is required unless a demodulated point is specified by the
manufacturer.
7. The IF amplifier tuning adjustments can be performed as required to
obtain the desired IF response curve. Normally each tuned circuit is
adjusted for maximum amplitude at the IF center frequency.
Dual Trace
Oscilloscope preferred
No DC Offset To VCO In ETE 7 OEDLLOCSC 1
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Counter Source
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RF Detector Probe required
at this point, unless otherwise
Osc specified by the manufacturer.
20
Fig. 11. AM receiver alignment, RF and IF.
USING THE 3010 AS A BIAS AND SIGNAL SOURCE
In the test set-up of Fig. 12 the 3010 can be used to bias the transistor under
test as well as to fumish an AC signal. By observing the amplifier output on the
oscilloscope, the amplitude and bias of the transistor can be optimized for
maximum undistorted output. By use of the DC OFFSET control, the effects
of various types of bias (class A, B, and C) can be determined.
Dual Trace
-DC Offset Oscilloscope preferred
as required Scope Sync | FREE vr cree, coe 1474 o
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Fig. 12. Use of Model 3010 as a combined bias-supply and signal source.
H. PRESET FREQUENCY SELECTION
In test and design work where several frequencies are used repeatedly, it is
convenient to be able to preselect these frequencies with a minimum of
effort. As shown in Fig. 13, the VCO feature of the 3010 can be used together
with preset voltages and frequency selector switch.
1.
2.
Set the FREQUENCY DIAL to .1.
Connect the output of the 3010 to a frequency counter.
With the frequency selector switch in the F1 position, adjust the Ri for
the desired frequency as observed on the frequency counter. Repeat this
for the frequencies desired.
With the FREQUENCY dial set at .1, and a maximum available A+ voltage
of about 6 volts, frequencies encompassing a 100:1 range can be obtained
by this method on each frequency range.
21
& as = Bae A+
© tregulated)
R1 Leo R3
To VCO In Fl os >
— (rear panel) RP? | TY
* Output | E
> a
» A-
a
Dial to .1
[|]
Frequency o =
Counter ©
High Impedance
DC Voltmeter
Fig. 13. Preset frequency selection.
I. DIGITAL FREQUENCY SELECTION
Frequencies can be switched electronically by using the set-up shown in
Fig. 14. The preset voltages can be digitally selected and applied to the VCO IN
jack on the Model 3010. Although provisions for two frequencies are shown,
additional frequencies can be added using redundant circuits. This is
convenient in frequency shift keying (FSK) systems.
Adjust for
e VCO N Frequency 1
rear pane VW +6V
10K
10K
Dial to .1 ON
High>2.4
OFF
Low“ .4
10K
= = Adjust for
Frequency 2
ON
High>2.4
OFF
Low<.4
Fig. 14. Digitally programmed frequency selection.
22
COMMUNICATIONS RECEIVER ALIGNMENT
The test set-up of Fig. 15 can be used for alignment of communication receiver
IF’s and discriminators using the 455 KHz IF frequency. For accurate
frequency adjustments, a 455 KHz crystal control marker source should be
used.
1. The sweep voltage source is applied to the 3010 VCO IN jack and to the
oscilloscope X-axis input.
2. the IF response curve is indicated. In some receivers the IF selectivity is
“packaged” which means all adjustments are preset. In this case the
receiver alignment can only be evaluated and verified without adjustment.
Where the tuned circuits are adjustable, the manufacturer’s procedure
must be followed to insure that the proper overall response is obtained.
ADDITIONAL APPLICATIONS
The triangle output of the 3010 can be used at its lowest frequencies to
simulate a slowly varying DC source. This can be used to check threshold levels
of TTL and CMOS logic as well as voltage comparators. Chart recorders can be
checked by this method. Analog meter movements can be exercised from zero
to fuit scale to observe defects, such as sticky meter movements.
Dual Trace X-Y
Oscilloscope preferred
No DC Offset To VCO INPUT == LO ao
(rear panel) = |! © o
® WW
o 90
| E
L Sine wave e e | | O
selected e
| | т
0,0 61,9:
U
—
Direct or 10:1 --——.
Oscilloscope Probe Ва
4
A Sweep Voltage
| Source
(Sine wave or Ramp)
=
1st Ist Fly _ | 2nd 2nd iFk Y
RF |->
Demodulator | Audio
a
Mixer Amps | 4
455KHz
Osc
Marker
FM Receiver
435 455 475 435
Frequency , KHz
Mixer Amps Г Amps
| | RF Detector Probe required
| HH
at this point, unless otherwise
specified by the manufacturer.
455 475
Fig. 15. Alignment of communications IF’s and discriminators.
24
THEORY OF OPERATION
GENERAL CIRCUIT DESCRIPTION (See Block Diagram and Schematic)
The basic waveform generated in the Model 3010 is the triangle wave. This is
accomplished by charging and then discharging a capacitor by equal magnitude
currents. A dual comparator and flip flop determine whether the capacitor is being
charged or discharged. When the voltage on the capacitor reaches the positive limit,
the charging current is switched off and the capacitor discharges until the lower
limit is reached at which time the charging current is then reapplied. The output of
the dual comparator is a square wave.
To produce a sine wave, the triangle wave is shaped by a special amplifier.
Range switching is accomplished by changing the magnitude of the current sources
and the timing capacitor. Dial frequency tuning is done by changing the magnitude
of the current sources. A frequency. change of over a 100:1 is possible with the
frequency dial. Below is a table of the capacitors and currents used.
RANGE (100:1) CAPACITOR CURRENT
1H —10H 3.3 uF (C15) 1.65 uA — 165 uA
1 Hz —100Hz 3.3 uF (C15) 16.5 uA — 1.65 mA
10Hz —1KHz 033 uF (C16) 1.65 UA — 165 uA
100 Hz — 10 KHz 033 uF (C16) 16.5 pA — 1.65 mA
1 KHz — 100 KHz 325 pF (C17, 18) 1.65 HA — 165 UA
10 KHz — 1 MHz 300 pF (C18) 16.5 uA — 1.65 mA
The peak-to-peak voltage of the triangle wave generated is 2.5 V. The
frequency of operation is determined by the currents, the capacitor value and the
peak-to-peak voltage of the triangle wave.
25
Ho) TTL
6000
OUTPUT
Buffer
IC6B,IC6C
TTL
reine
Square
Wave Buffer
IC6A,IC6D
Dual Comparator
and Flip - Flop
IC5
Switch
09,010
Q11,.012,013
Function
Amplitude
Control
Output Amp
—
Ta
ym
DC Offset
Cy Buffer
07,08
—
1C7
al
À
Timing
Triangle to Sine
Wave Converter
»1 Capacitor
Fig. 16. Model 3010 block diagram.
iode
Gates
:
Source
IC4C ,Q3
D5,D6
+21 Current
—
IC4B
Frequency
Control
Frequency Control
Voltage Reference
-I Current
Source
ICI3A,06
+15V
— 15V
+5V
—5V
—
01,02
Tuning Amp
IC4A
Current
Summing Amp
¡C4D,03
Current
Source Driver
Power Supply
T1, D1,D2 ,D3,D4
IC1,1C2.IC3B
IC3D,04
VCO
iN
_ 1 _ (C) (pp).
f 57 and T —[ therefore,
I
(2) (C) (Vpp)
Thus for 1 = 1.65 mA, C = 3.3 uF and Vpp = 2.5 V
f=
fo 165x107
(2) (3.3 x 10-6) (2.5)
f= 100 Hz
DETAILED CIRCUIT DESCRIPTION
A. Frequency Control Voltage Reference (IC4B)
The Frequency Control Voltage Reference is composed of three trimpots
(R11, 12, 13), two resistors and [C4B, which divide the +15 volts supply and
provide a reference voltage of approximately +12 volts to the Frequency
Control Potentiometer. Each trimpot is adjusted to compensate for the
tolerance variations of the timing capacitors.
B. Tuning Amplifier (IC4A)
The tuning amplifier is provided to buffer the output of the Frequency Control
Pot. This assures that this voltage will be as linear as the frequency pot R101
itself. If not, R17 would be in parallel with frequency pot R101 and the action
of the frequency pot would be non-linear.
C. Current Summing Amplifier (IC4D, Q3)
The current Summing Amplifier sums the current from the tuning amp and the
VCO input. The current from the tuning amp is simply the voltage at its output
divided by the value of R17 (2K). The current from the VCO input is
normally zero. When a voltage is applied, the current into the summer is the
voltage divided by R18 (1KS€2). For a 100:1 sweep, the voltage has to be
approximately +5.5V. The output current (collector of Q3) creates a voltage
across R19 (1K) that tracks the voltage of the tuning amplifier by a factor of
—14,
D. Current Source Driver (IC3D, Q4)
IC3D is an operational amplifier and -Q4 is an emitter follower used in
27
28
conjunction with the operational amplifier. IC3D and Q4 are connected as a
voltage follower with a closed loop gain of +1. The voltage of the emitter of Q4
follows the input voltage of pin 12. The voltage at the collector of Q4 tracks
the voltage at the emitter but is of opposite polarity. In this way the current
source driver provides both current sources with equal voltages.
Positive & Negative Current Sources (IC3A, IC4C, Q5, Q6)
The current sources provide two switchable sets of currents. IC3A and Q6 are
connected as a voltage follower. The voltage at the emitter of Q6 is equal to
the voltage at the input to IC3A (pin 3). The current, produced, - I, is equal to
the ~ 15 volt supply minus the voltage at the emitter of Q6, divided by the total
resistance Ryy (which equals R22 + R23). The current - 101 is produced by the
same voltage but R24 has been switched in parallel to the sum of R22 + R23
and the total resistance is now the parallel combination Ry, q (R24 in parallel
with the sum of R22 + R23).
The voltage across R21 is equal and opposite to the voltage across R20. IC4C
and Q5 are connected as a voltage follower similar to IC3A and Q6. The
voltage at the emitter of Q5 is equal to the voltage at the input to IC4C (pin
10). The current produced is equal to the +15 volt supply minus the voltage at
the emitter of QS divided by the total resistance Ry, (which equals R25 +
R26). The value of Rp, is half the value of Ry,, therefore the current is 21.
Similarly, when the combination, R27 + R28, is switched in parallel to the
combination R25 + R26, the total resistance is Ryyp, which equals R25 +
R26, in parallel with R27 + R28. The total current with Ry, is 201.
Diode Gates (D5, D6)
The diode gates are silicon diodes D5 and D6. In the 1, 100 and 10K range, the
positive current source puts out 2I and the negative current source sinks -I
current. The purpose of the gates is to either switch the output of the positive
current source to the capacitors to charge them, or to shunt the current so that
the negative current source can discharge the capacitors. The gates work as
follows:
|. If the signal from the level detector is high-level TTL, +5V, it
reverse-biases diode D6 and cuts it off. Diode D5 now becomes
forward-biased and all the current (2I) flows through DS. Since the
negative current source can only sink -I current, a net positive current, I,
is seen by the capacitors and they are linearly charged to produce a
positive ramp.
2. If the signal from the level detector is low-level TTL, O V, it forward-biases
diode D6 and the level detector sinks all the current (2I), from the positive
current source. Diode DS now becomes reverse-biased and no current
flows thru it. The capacitors now see only the negative current source with
-1 current and are linearly discharged to produce a negative ramp. In the
10, 1K, and 100K ranges the gates work exactly the same except that the
currents are now 10 times greater.
G. C, (C15, 16, 17, 18)
The timing capacitors Ct are chosen for such highly desirable qualities as:
1. Low dissipation factor.
2. Low temperature coefficient.
3. Long-term capacitance stability.
Triangle Buffer (Q7, Q8)
The triangle buffer has a very high impedance to minimize leakage currents and
prevent loading of the timing capacitors. Q7 is a dual FET; one half is the high
impedance buffer to the capacitors while the other half provides temperature
compensation to the first half. Q8 is an emitter follower and is used to provide
the necessary current to drive the level detector, sine shaper, etc. The three
silicon diodes along with the base-emitter junction of Q8 shifts the triangle
waveform seen at the emitter of Q8 up to four diode drops (about 2.6V) so
that the diode dates can switch properly with a TTL level signal from the level
detector.
Dual Level Detector & Flip-Flop (1C5)
The level detector senses the level of the ramp input (either positive or
negative) and switches output states when the input reaches any one of two
voltage limit references. The device (75107) has a dual differential input
comparator stage and a dual three-input nand gate output stage connected as
an R-S flip-flop. The input limit voltage references are set by two voltage
dividers on the tracking +15 V and -15 V supplies. Resistors R32 and R33 set
+1.25 V for the minus input of one comparator. Resistors R34 and R35 set
-1.25 V for the plus input of the other comparator. C22 couples a small posi-
tive feedback from one output of the line receiver (pins 5 € 9) to the inputs
(pins 2 & 12) to speed up the switching.
TTL Buffer (IC6B, IC6C)
IC6B and 6C are half of a quad nand gate package. They are connected in
paraliel and provide a fan-out of 20 for the TTL square wave. This avoids any
loading on the level detector.
K. Square Wave Level Shifter (IC6A, IC6D) MAINTENANCE AND CALIBRATION
The square wave level shifter shifts the DC level of the TTL output of the level
detector so that it is approximately symmetrical aboút zero. IC 6A and 6D are
connected in parallel. One set of inputs (pins 2 and 12) are switched so that the WARNING
level shifter operates only when the square function button is pushed on.
Trimpot R42 provides an amplitude adjustment for the square wave.
1. The following instructions are for use by qualified personnel only. To
avoid electric shock, de not perform servicing other than contained in
L. Sine Wave Shaper (IC7
per (IC7) the operating instructions unless you are qualified to do so.
The sine wave shaper takes a triangle wave input and non-linearly shapes it to 2. A shock hazard is present when the case is removed once the line cord
produce a sine wave. The shaper utilizes the non-linear relationship of a is plugged into an AC outlet. Avoid touching the fuse or bottom of
differential pair of transistors. The output is taken from one collector of the the circuit board in the area of the fuse or power transformer. The
pair and buffered and level-shifted by the two other transistors in the package fuse has 120 VAC (240 VAC on export models) on it even when the
IC7. Trimpot R52 adjusts the amplitude of the sine wave and R59 adjusts its POWER switch is off.
DC level at the output. Trimpots R50 and R55 are adjusted to provide the |
lowest distortion of the sine wave.
Your Bé K-PRECISION Model 3010 Function Generator was carefully
checked and calibrated at the factory prior to shipment. Calibration of this
instrument should not be attempted unless you are experienced and qualified in the
use of precision laboratory equipment. Should any difficulty occur during repair or
calibration, refer to the warranty service instructions at the rear of this manual for
information or technical assistance.
M. Output Amplifier (Q9, 10, 11,12, 13)
The Output Amplifier consists of a differential input stage (Q9 and Q10)
followed by a common emitter transistor, Q11. The output from QI1 is
applied to a push-pull output stage (Q12 and Q13). Feedback is applied from
the output to the base of О10 by R70 and R69. The closed loop gain is
approximately 10. DC offset is obtained by applying the offset voltage to the
base of Q10 also.
N. Power Supply (IC1, IC2, IC3B, IC3C, Q1, Q2, 01, 2, 3, 4)
Power transformer T1, bridges diodes D1, 2, 3, 4 and filter capacitors Cl and
C3 generate +22 V and -22 V unregulated. The +22 V is applied to ICI, a
78L15A voltage regulator, which generates the +15 V supply. The +22 V is also
applied through RS to IC2, a 78LOSA regulator, which generates the +5 V.
IC3C and Q1 comprise a -15 V regulator which is referenced to the +15 V via
R1 and R2. In a similar manner, IC3B and Q2 comprise a - 5 V regulator which
is referenced to the +5 V supply via R7 and R8.
Fig. 17. Removal of rear case.
30
31
REMOVAL OF REAR CASE
To remove the rear case from the generator, proceed as follows:
1.
Use a coin (a quarter works best) to remove the two screws that hold the
handle to the case. Use caution to avoid losing the springs beneath the
screws that hold the handle on the case. Remove the handle. The handle
may be reversed if the user desires; refer to Fig. 17.
Remove the two Phillips head screws from the rear case.
Slide the rear case fromthe generator.
To re-install the rear case on the generator, follow the above procedure in
reverse. When re-installing the rear case, be sure the printed circuit board
properly engages the slots inside the case.
CALIBRATION PROCEDURE
A. Equipment Required:
1.
2.
3.
4,
Tektronix Model 465 Oscilloscope.
Hewlett-Packard Model 333 A Distortion Analyzer.
B & K-PRECISION Model 1820 Universal Frequency Counter.
6002 Terminating Resistor.
B. Procedure:
I.
2.
Remove 3010 rear case Refer to Fig. 17.
Place the 3010 on an insulated surface. Plug the line cord into the
receptacle on the 3010 rear bracket, then plug the other end into a
120 VAC outlet.
Set up the 3010 controls as follows:
POWER ...... KG ON
RANGE ......... coin. 100
FUNCTION .............. Cee TRIANGLE
DC OFFSET .............. 5.0... Centered
AMPLITUDE ................... Fully Counterclockwise
FREQUENCY ........ covet 10
Refer to Fig. 18 for trimpot location and Table 1 for trimpot function.
32
R52
+ RSS
—Érso
8 R50
pros
Fig. 18. Trimpot location.
Trimpot No. Function
R26 1 KHz Symmetry
R28 10 KHz Symmetry
R42 Square Wave Amplitude
R50 Sine Distortion 1
R55 Sine Distortion 2
R52 Sine Wave Amplitude
R59 Sine Wave DC Level
R13 10 K Range Frequency
R12 1 K & 100 Range Frequency
R11 10 & 1 Range Frequency
Table I. Trimpot Function
34
Symmetry Adjustments (Refer to Fig. 18 for location of Trimpots R26
and R28).
Terminate the 3010 TTL OUTPUT with 600% and connect both channel
1 and channel 2 scope probes to it. Set the scope controls as follows:
CH1VOLTS/DIV ............... 1V
CH1COUPLING ................ DC
CH2VOLTS/DIV ............... 1V
CH2 COUPLING ................ DC
CH2INVERT .................. INVERT
VERT MODE ..........e........ ALT
A TIME BASE .................. .1 mS/DIV
LOCK
HORIZ DISPLAY ............... Men OBS
A TRIG MODE ...........e..... AUTO
A COUPLING ..............e... DC
ASOURCE «viii. NORM (Important)
A TRIGGER SCOPE ............. +
BCOUPLING .................. DC
BSOURCE .............e ee... STARTS AFTER DELAY
Adjust CH 1 and CH 2 position controls to center each trace and adjust A
TRIGGER level for a stable trigger. The display should appear to be two
squares in phase but since CH 2 is inverted and NORM source triggering is
used, what appears to be falling edge of CH 2 is actually the leading edge
of the TTL OUTPUT.
Change HORIZ DISPLAY to A INTEN.
Use the B TIME/DIV KNOB (pull to unlock) and the DELAY TIME
POSITION CONTROL to center the intensified trace to the trailing edges
of the square waves. Continue until the B TIME/DIV setting is 1 uS/DIV.
Now change HORIZ DISPLAY TO B DLY’D and the display should show
an expanded view of the falling edges of the square waves.
Adjust Trimpot R26 so that the edges coincide.
Change the 3010 RANGE setting to 1 K and repeat the above procedure
but change A TIME/DIV to 10 uS/DIV and B TIME/DIV to .1 uS/DIV
and adjust Trimpot R28 so that the trailing edges of the two square waves
coincide.
5.
Amplitude Correlation and Sine Distortion Adjustments. Terminate the
3010 6002 OUTPUT with 600£2 and connect channel 1 scope probe to it.
Change the scope controls to the new settings as follows:
CH ! VOLTS/DIV ............... 2V
CH1 COUPLING ................ GND
VERT MODE ............e.e.... CH 1
TIME BASE .................... 1 mS/DIV
LOCK
HORIZ DISPLAY ............... A KNOBS
Adjust CH 1 POSITION control to center the trace on the scope grid. Flip
CH 1 COUPLING to AC. Push in the 3010 100 RANGE button and rotate
the 3010 AMPLITUDE knob clockwise until the triangle wave just touches
the O and 100 dotted lines on the scope grid. Flip CH 1 COUPLING to
DC. Rotate the 3010 DC OFFSET knob until the triangle wave just
touches the 0 to 100 dotted lines on the scope grid.
Push in the 3010 SQUARE FUNCTION button. Flip CH 1 COUPLING to
AC. Adjust Trimpot R42 until the square wave just touches the 0 and 100
dotted lines on the scope grid.
Push in the 3010 SINE FUNCTION button. Connect the distortion
analyzer to the 3010 600£2 OUTPUT. Manipulate the distortion analyzer
for a minimum distortion reading. Adjust Trimpot R50 first, then Trimpot
R55, for a minimum distortion reading. Readjust both Trimpots R50 and
R55 for a minimum distortion reading (must be less than or equal to
0.5%). Disconnect the distortion analyzer.
Adjust Trimpot R52 until the sine wave just touches the O and 100 dotted
lines on the scope grid. Flip CH 1 COUPLING to DC. Adjust Trimpot R59
until the sine wave just touches the 0 and 100 dotted lines on the scope
grid.
Frequency Adjustments.
Connect the counter to the 3010 6002 OUTPUT. Set the counter to
PERIOD FUNCTION. Push in the 3010 10 K RANGE button and be sure
that the 3010 FREQUENCY dial is set to 10. Adjust Trimpot R13 for a
counter reading of 10.000 uS. OK if counter reading is between 9.980 uS
and 10.020 us:
Push in the 3010 100 RANGE button. Adjust Trimpot R12 for a counter
reading of 1000.00 uS. OK if counter reading is between 998.000 uS and
1002.00 uS.
35
Push in the 3010 10 RANGE button. Adjust Trimpot R11 for a counter
reading of 10.0000 mS. OK if counter reading is between 9980.00 uS and
10.0200 mS.
8. Disconnect the scope probe and counter from the 3010 60022 OUTPUT.
Carefully re-install the rear case (refer to Fig. 17)
LINE VOLTAGE CONVERSION
The 105-130 volt, 60 Hz power transformer (065-137-9-001) used in the stand-
ard 3010 is replaced by a 105-130/210-260 volt, 50/60 Hz power transformer
(065-137-9-002) in the export version. The line cord in the export version uses
standard DIN color codes. The power transformer is normally prewired to
match the power source used in the country of original sale. The instrument
may be easily coverted to the alternate line voltage. To convert from 210-260
volt operation to 105-130 volt operation, or vice versa, use the following pro-
cedure:
1. Remove case (Fig. 17).
2. Rewire power tansformer for desired line voltage (Fig. 19).
3. Change fuse F1 (see Fig. 18 for location). Use A A, 3AG slow blow for
105-130 volt operation, or 7s A, 3AG slow blow for 210-260 volt opera-
tion.
4, Change line voltage label.
HO
=) | (©) === = (9) —
210-260 VAC 105-130 VAC
36
Fig. 19. Transformer wiring, export version.
SERVICE INSTRUCTIONS
a 1. Refer to the ‘MAINTENANCE - “section ‘of your В & К-
Jared instruction’ manual” for adjustments 1 that may | be
2. If the above-mentioned does not correct the problem you
- are: ‘experiencing with your unit, pack it securely (preferably
in the original carton or double-packed). Enclose a letter
~~ describing the problem and include your name and address.
~~ Deliver to, or ship PREPAID (UPS preferred) ‘to the nearest
B & K-Precision authorized service agency (see list enclosed
with unit).
If your . list of authorized B& K-Precision service agencies
“has been misplaced, contact your distributor for the name of your
nearest service agency, or write to:
B & K-Precision D: mascan Corporation.
Factory Service Operations.
6460 West Cortland Street.
Chicago, Illinois 60635
.. Tel (312) 889-8870
_ Telex: 25-3475 В "
Also à use this adress for technical inquiries and replacement
parts orders.
37
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